JPH09266677A - Noise reducer for power converter - Google Patents
Noise reducer for power converterInfo
- Publication number
- JPH09266677A JPH09266677A JP8099254A JP9925496A JPH09266677A JP H09266677 A JPH09266677 A JP H09266677A JP 8099254 A JP8099254 A JP 8099254A JP 9925496 A JP9925496 A JP 9925496A JP H09266677 A JPH09266677 A JP H09266677A
- Authority
- JP
- Japan
- Prior art keywords
- noise
- current
- circuit
- smoothing capacitor
- power
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Abstract
Description
【０００１】[0001]
【産業上の利用分野】本発明はインバ−タ装置等のスイ
ッチング素子を含む電力変換装置におけるノイズ低減装
置に関する。BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a noise reduction device in a power conversion device including a switching element such as an inverter device.
【０００２】[0002]
【従来の技術】図１に示す従来のインバ−タ装置は、交
流電源１にラインフィルタ２を介して接続された整流回
路３と、整流回路３の一対の出力端子間に接続された平
滑用コンデンサ４と、平滑用コンデンサ４に接続された
インバ−タ回路５とから成る。ラインフィルタ２は３相
交流電源１と整流回路３との間の３本の電力ラインにそ
れぞれ直列に接続されたリアクトルＬから成り、高周波
ノイズ成分を除去する。インバ−タ回路５はＩＧＢＴ
（絶縁ゲ−トバイポ−ラトランジスタ）等のスイッチン
グ素子Ｑを含み、このオン・オフによってパルス幅変調
（ＰＷＭ）された出力電圧Ｖ0 を発生する。図１ではイ
ンバ−タ回路５の負荷として三相誘導電動機６が接続さ
れている。2. Description of the Related Art A conventional inverter device shown in FIG. 1 has a rectifying circuit 3 connected to an AC power source 1 via a line filter 2 and a smoothing circuit connected between a pair of output terminals of the rectifying circuit 3. It comprises a capacitor 4 and an inverter circuit 5 connected to the smoothing capacitor 4. The line filter 2 includes a reactor L connected in series to each of three power lines between the three-phase AC power supply 1 and the rectifier circuit 3, and removes high frequency noise components. The inverter circuit 5 is an IGBT
A switching element Q such as an (insulation gate bipolar transistor) is included, and the ON / OFF switching generates a pulse width modulated (PWM) output voltage V0. In FIG. 1, a three-phase induction motor 6 is connected as a load of the inverter circuit 5.
【０００３】[0003]
【発明が解決しようとする課題】ところでインバ−タ回
路５の出力電圧Ｖ0 はパルス的電圧であるので、誘導電
動機６の各巻線とグランドとの間の静電容量即ちストレ
−トキャパシタンスＣに洩れ電流Ｉc がＣ・ｄｖ／ｄｔ
で流れる。スイッチング素子Ｑが第三世代ＩＧＢＴの場
合、ｄｖ／ｄｔは３０００ｖ／μｓ程度なので、静電容
量を１０００ｐＦとすれば約３Ａのパルス電流が流れ
る。このパルス電流は高周波のコモンモ−ドノイズとし
て交流電源１と誘導電動機６とグランドから成る回路を
流れる。ラインフィルタ２はノイズ除去の作用を有する
が、スイッチング素子Ｑのオン・オフ周波数の上昇にと
もないノイズ除去効果を十分に得ることができなくな
る。図１の電源１は三相であるが、単相の場合において
も同様にコモンモ−ドのノイズが発生する。また、三相
誘導電動機６の中点が接地されている場合にも洩れ電流
即ち零相電流がコモンモ−ドノイズとして流れる。上述
のようなコモンモ−ドノイズは感電の発生や、地絡ブレ
−カの動作の原因になる。なお、スイッチング素子を含
む電力変換装置においては、電源１から負荷としての電
動機６に至る回路を循還して流れるノ−マルモ−ドも問
題になる。ノイズはリアクトルまたはリアクトルとコン
デンサの組み合せから成るフィルタによってある程度除
去することができるが、ノイズ除去効果を高めるために
は大きなリアクトルを使うことが必要になり、ノイズフ
ィルタが大型且つ高価になる。Since the output voltage V0 of the inverter circuit 5 is a pulse voltage, it leaks to the electrostatic capacitance between each winding of the induction motor 6 and the ground, that is, the straight capacitance C. Current Ic is C · dv / dt
Flowing in. When the switching element Q is a third-generation IGBT, dv / dt is about 3000 v / μs, so if the capacitance is 1000 pF, a pulse current of about 3 A flows. This pulse current flows as a high frequency common mode noise through a circuit composed of the AC power supply 1, the induction motor 6 and the ground. Although the line filter 2 has a function of removing noise, the noise removing effect cannot be sufficiently obtained as the ON / OFF frequency of the switching element Q increases. Although the power source 1 in FIG. 1 has three phases, common mode noise is also generated in the case of a single phase. Further, even when the middle point of the three-phase induction motor 6 is grounded, a leakage current, that is, a zero-phase current flows as common mode noise. The common mode noise as described above causes an electric shock and an operation of the ground fault breaker. In a power converter including a switching element, a normal mode that circulates through a circuit from the power source 1 to the electric motor 6 as a load also poses a problem. The noise can be removed to some extent by a filter composed of a reactor or a combination of a reactor and a capacitor, but in order to enhance the noise removal effect, it is necessary to use a large reactor, and the noise filter becomes large and expensive.
【０００４】そこで、本発明の目的は、電力変換装置の
ノイズ低減装置の小型化、低コスト化及び高性能化を図
ることにある。Therefore, an object of the present invention is to reduce the size, cost and performance of a noise reduction device for a power conversion device.
【０００５】[0005]
【課題を解決するための手段】上記目的を達成するため
の本発明は、スイッチング素子のオン・オフに基づいて
電力を変換する電力変換装置におけるノイズ低減装置で
あって、電力ラインのノイズ電流を検出するノイズ検出
手段と、前記ノイズ検出手段で検出されたノイズ電流に
応答して前記ノイズ電流と逆向きのノイズ補償電流を形
成し、このノイズ補償電流を前記電力変換装置のノイズ
電流の流れているラインに供給するノイズ補償電流供給
回路とを備えていることを特徴とするノイズ低減装置に
係わるものである。なお、請求項２に示すように、コモ
ンモ−ドノイズを低減するように構成することができ
る。また、請求項３に示すようにノ−マルモ−ドノイズ
を低減するように構成することができる。SUMMARY OF THE INVENTION The present invention for achieving the above object is a noise reducing device in a power conversion device for converting electric power based on ON / OFF of a switching element. Noise detecting means for detecting, and in response to the noise current detected by the noise detecting means, forms a noise compensating current in the opposite direction to the noise current, and this noise compensating current is passed through the noise current of the power converter. The present invention relates to a noise reduction device characterized in that it is provided with a noise compensation current supply circuit for supplying the current to a line. It is possible to reduce the common mode noise as described in claim 2. Further, as described in claim 3, it can be configured to reduce the normal mode noise.
【０００６】[0006]
【発明の作用効果】各請求項の発明によれば、第１及び
第２の電流制御素子の一方又は両方の働きによってノイ
ズ成分を打ち消すための補償電流を注入することができ
る。即ちアクテイブフィルタ動作によってノイズを低減
することができる。従って、各請求項の発明によれば、
リアクトル等の受動素子に基づくフィルタに比べて、ノ
イズ低減装置の小型化、低コスト化及び高性能化が可能
になる。また、請求項２の発明によれば、コモンモ−ド
ノイズの低減を容易且つ良好に達成することができる。
また、請求項３の発明によれば、ノ−マルモ−ドノイズ
の低減を容易且つ良好に達成することができる。According to the invention of each claim, the compensation current for canceling the noise component can be injected by the action of one or both of the first and second current control elements. That is, noise can be reduced by the active filter operation. Therefore, according to the invention of each claim,
As compared with a filter based on a passive element such as a reactor, it is possible to reduce the size, cost, and performance of the noise reduction device. According to the second aspect of the invention, it is possible to easily and satisfactorily reduce the common mode noise.
According to the third aspect of the invention, reduction of normal mode noise can be achieved easily and satisfactorily.
【０００７】[0007]
【第１の実施例】次に、図２及び図３を参照して第１の
実施例のインバ−タ装置を説明する。図２に示すインバ
−タ装置は、交流電源１にラインフィルタ２を介して接
続されたブリッジ型全波整流回路３と、この整流回路３
の一対の出力端子間に接続された平滑用コンデンサ４
と、この平滑用コンデンサ４に接続された三相インバ−
タ回路５とから成る。ラインフィルタ２は一対の交流電
源ライン間に接続され且つ互いに直列に接続された第１
及び第２のラインフィルタ用コンデンサＣ1 、Ｃ2 と一
対の交流電源ラインにそれぞれ直列に接続された第１及
び第２のリアクトルＬ1 、Ｌ2 とから成る。なお、コン
デンサＣ1 、Ｃ2 は比較的低容量の高周波コンデンサで
あり、リアクトルＬ1 、Ｌ2 は比較的インダクタンスが
小さいものである。[First Embodiment] Next, the inverter device of the first embodiment will be described with reference to FIGS. The inverter device shown in FIG. 2 includes a bridge-type full-wave rectifier circuit 3 connected to an AC power source 1 via a line filter 2, and the rectifier circuit 3
Smoothing capacitor 4 connected between a pair of output terminals
And a three-phase inverter connected to this smoothing capacitor 4.
Circuit circuit 5. The line filter 2 is a first filter connected between a pair of AC power supply lines and connected in series with each other.
And a second line filter capacitors C1 and C2, and first and second reactors L1 and L2 connected in series to a pair of AC power supply lines, respectively. The capacitors C1 and C2 are high frequency capacitors having a relatively low capacity, and the reactors L1 and L2 have a relatively small inductance.
【０００８】インバ−タ回路５は、ソ−スがサブストレ
−トに接続された構造の絶縁ゲ−ト型電界効果トランジ
スタから成る第１及び第２のスイッチング素子Ｑ1 、Ｑ
2 の直列回路を一対の直流電源ライン間に接続し、更に
第３及び第４のスイッチング素子Ｑ3 、Ｑ4 の直列回路
と第５及び第６のスイッチング素子Ｑ5 、Ｑ6 の直列回
路とを一対の直流電源ライン間に接続した周知の三相ブ
リッジ型インバ−タである。第１〜第６のスイッチング
素子Ｑ1 〜Ｑ6 は制御回路７から供給されたＰＷＭパル
スによって周知の方法でオン・オフ制御される。The inverter circuit 5 includes first and second switching elements Q1 and Q which are insulated gate type field effect transistors having a structure in which the source is connected to the substratum.
The series circuit of 2 is connected between a pair of DC power supply lines, and the series circuit of the third and fourth switching elements Q3 and Q4 and the series circuit of the fifth and sixth switching elements Q5 and Q6 are paired with a direct current. It is a well-known three-phase bridge type inverter connected between power lines. The first to sixth switching elements Q1 to Q6 are on / off controlled by a well-known method by the PWM pulse supplied from the control circuit 7.
【０００９】インバ−タ回路５の三相出力ラインは図２
で概略的に示されている１．５ｋＷの三相誘導電動機６
の各相巻線に接続されている。電動機６はグランドとの
間に静電容量Ｃを有している。従って、インバ−タ回路
５から出力されるパルス状電圧を電動機６に印加する
と、グランドに洩れ電流即ちコモンモ−ドのノイズ電流
が流れる。なお、電源１側における洩れ電流の経路は、
電源１の接地ライン（図示せず）、ラインフィルタ用コ
ンデンサＣ1 、Ｃ2 の接続点とグランドとの間、及び交
流電源ラインのストレ−トキャパシタンスである。The three-phase output line of the inverter circuit 5 is shown in FIG.
1.5 kW three-phase induction motor 6 shown schematically in
Is connected to each phase winding. The electric motor 6 has an electrostatic capacitance C with the ground. Therefore, when the pulsed voltage output from the inverter circuit 5 is applied to the electric motor 6, a leak current, that is, a noise current in common mode flows to the ground. The path of the leakage current on the power supply 1 side is
These are the ground capacitance (not shown) of the power supply 1, the connection point between the line filter capacitors C1 and C2 and the ground, and the straight capacitance of the AC power supply line.
【００１０】図２のインバ−タ装置は、ノイズ検出手段
としての洩れ電流検出器８と、ノイズ補償電流供給回路
９とから成るノイズ低減装置を有する。洩れ電流検出器
８はフエライトから成る環状コア１３と２つの１次巻線
ｎ1a、ｎ1bと１つの２次巻線ｎ2 とから成る零相ＣＴで
あって、一対の電源ラインの電流の差から成る洩れ電流
（零相電流成分）Ｉseを検出する。このため。２つの１
次巻線ｎ1a、ｎ1bは交流電源１と整流回路３との間の一
対の電源ラインにそれぞれ直列に接続されている。な
お、コア１３の断面積は５０mm2 であり、１次巻線ｎ1
a、ｎ1b及び２次巻線ｎ2 のタ−ン数は１０である。The inverter device of FIG. 2 has a noise reduction device comprising a leakage current detector 8 as noise detection means and a noise compensation current supply circuit 9. The leakage current detector 8 is a zero-phase CT composed of an annular core 13 made of ferrite, two primary windings n1a and n1b and one secondary winding n2, and is composed of a difference in current between a pair of power supply lines. The leak current (zero-phase current component) Ise is detected. For this reason. Two one
The secondary windings n1a and n1b are respectively connected in series to a pair of power supply lines between the AC power supply 1 and the rectifier circuit 3. The cross-sectional area of the core 13 is 50 mm 2 , and the primary winding n1
The number of turns of a, n1b and the secondary winding n2 is 10.
【００１１】ノイズ補償電流供給回路９は、第１及び第
２の電流制御素子としての第１及び第２のトランジスタ
Ｔr1、Ｔr2と、第１及び第２のダイオ−ドＤ1 、Ｄ2
と、結合コンデンサＣb とから成る。ＮＰＮ型の第１の
トランジスタはＴr1は平滑用コンデンサ４の一端と電動
機６の鉄心又はフレ−ム又はカバ−との間に静電容量が
１０００ｐＦ、耐圧１ｖＫの結合コンデンサＣb を介し
て接続されている。ＰＮＰ型の第２のトランジスタＴr2
は平滑用コンデンサ４の他端と電動機６の鉄心又はフレ
−ム又はカバ−との間に結合用コンデンサＣb を介して
接続されている。第１のトランジスタＴr1はＮＰＮ型で
あり、第２のトランジスタＴr2はＰＮＰ型であり、第１
及び第２のトランジスタＴr1、Ｔr2は互いに逆の極性を
有する。第１及び第２のトランジスタＴr1、Ｔr2のベ−
ス（制御端子）は零相電流検出器８の一方の出力ライン
に接続され、第１及び第２のトランジスタＴr1、Ｔr2の
相互接続点は零相電流検出器８の他方の出力ラインに接
続されている。従って、第１及び第２のトランジスタＴ
r1、Ｔr2は互いに逆に動作する。第１及び第２のダイオ
−ドＤ1 、Ｄ2 は第１及び第２のトランジスタＴr1、Ｔ
r2を保護するためにこれ等に逆並列に接続されている。
なお、第１及び第２のトランジスタＴr1、Ｔr2は高電流
増幅率、高周波、高耐圧であることが要求され、ｈfe＝
２００、ｆT ＝１４０μＨz 、ＶCEO ＝±１６０Ｖのも
のである。また電動機６のカバ−はア−ス線によってグ
ランドに接続されている。The noise compensating current supply circuit 9 includes first and second transistors Tr1 and Tr2 as first and second current control elements, and first and second diodes D1 and D2.
And a coupling capacitor Cb. In the NPN type first transistor, Tr1 is connected between one end of the smoothing capacitor 4 and the iron core of the electric motor 6, the frame or the cover via a coupling capacitor Cb having an electrostatic capacity of 1000 pF and a withstand voltage of 1 vK. There is. PNP type second transistor Tr2
Is connected between the other end of the smoothing capacitor 4 and the iron core, frame or cover of the electric motor 6 via a coupling capacitor Cb. The first transistor Tr1 is of NPN type and the second transistor Tr2 is of PNP type.
The second transistors Tr1 and Tr2 have opposite polarities. Bases of the first and second transistors Tr1 and Tr2
Is connected to one output line of the zero-phase current detector 8, and the interconnection point of the first and second transistors Tr1 and Tr2 is connected to the other output line of the zero-phase current detector 8. ing. Therefore, the first and second transistors T
r1 and Tr2 operate in reverse. The first and second diodes D1 and D2 are connected to the first and second transistors Tr1 and T2.
Connected to these in anti-parallel to protect r2.
The first and second transistors Tr1 and Tr2 are required to have a high current amplification factor, a high frequency, and a high breakdown voltage, and h fe =
200, f T = 140 μHz, V CEO = ± 160 V. Further, the cover of the electric motor 6 is connected to the ground by an earth line.
【００１２】次に、図２のインバ−タ装置の動作を説明
する。電源１の交流電圧は整流回路３で整流される。整
流回路３の出力電圧は平滑用コンデンサ４で平滑されて
インバ−タ回路５の入力電圧となる。三相インバ−タ回
路５の第１〜第６のスイッチグ素子Ｑ1 〜Ｑ6 は周知の
ＰＷＭパルスでオン・オフ制御される。三相誘導電動機
６はインバ−タ回路５の出力電圧で駆動される。Next, the operation of the inverter device shown in FIG. 2 will be described. The AC voltage of the power supply 1 is rectified by the rectifier circuit 3. The output voltage of the rectifier circuit 3 is smoothed by the smoothing capacitor 4 and becomes the input voltage of the inverter circuit 5. The first to sixth switching elements Q1 to Q6 of the three-phase inverter circuit 5 are on / off controlled by a well-known PWM pulse. The three-phase induction motor 6 is driven by the output voltage of the inverter circuit 5.
【００１３】図１で説明したように負荷としての電動機
６とグランドとの間には静電容量Ｃがある。従って、イ
ンバ−タ回路５からパルス的に電圧が印加される毎に静
電容量Ｃを通って洩れ電流即ち零相電流Ｉc が流れる。
洩れ電流検出器８は整流回路３の入力ラインにおいて洩
れ電流を検出し、第１及び第２のトランジスタＴr1、Ｔ
r2を駆動する。洩れ電流検出器８即ちＣＴの巻数比Ｎは
小さい方がよい。実際の零相電流の値Ｉ01と洩れ電流検
出器８の出力電流Ｉ02との間にはＩ01＝ＮＩ02の関係が
ある。洩れ電流検出器８の出力電流Ｉ02が第１及び第２
のトランジスタＴr1、Ｔr2のベ−スに流入すると、これ
がトランジスタＴr1、Ｔr2で増幅される。第１のトラン
ジスタＴr1がオンの時には、平滑用コンデンサ４と第１
のトランジスタＴr1と結合コンデンサＣb と電動機６の
静電容量Ｃとインバ−タ回路５の下側のスイッチング素
子Ｑ2 、Ｑ4 、Ｑ6 のいずれかとから成る閉回路にノイ
ズ補償電流が流れ、電動機６の洩れ電流即ち零相電流を
打ち消す。第１のトランジスタＴr1の電流増幅率をｈfe
とすれば、第１のトランジスタＴr1を通して供給される
補償電流Ｉc1はｈfeＩ02である。Ｉ02はＮＩ01であるの
で、Ｉc1は次式で示される。 Ｉc1＝ｈfeＩ02 ＝ｈfe（ＮＩ01） 洩れ電流検出器８の１次側の電流Ｉ01は次式で示され
る。 Ｉ01＝Ｉc −Ｉc1 ＝Ｉc −ｈfe（ＮＩ01） 従って、Ｉ01の値は次式で決定される。 Ｉ01＝Ｉc ／（１＋Ｎｈfe） この式から明らかなようにＮｈfeの値を大きくすると、
交流電源ラインにおける電流（洩れ電流成分）Ｉ01は小
さく成る。今、Ｎ＝１、ｈfe＝１００とすれば Ｉ01＝Ｉc ／１０１ となり、電動機６の洩れ電流を１／１００以下にするこ
とができる。As described with reference to FIG. 1, there is a capacitance C between the electric motor 6 as a load and the ground. Therefore, every time a voltage is applied in a pulsed manner from the inverter circuit 5, a leakage current, that is, a zero-phase current Ic flows through the electrostatic capacitance C.
The leakage current detector 8 detects the leakage current in the input line of the rectifier circuit 3 and detects the first and second transistors Tr1 and T1.
Drive r2. The leakage current detector 8, that is, the CT turn ratio N is preferably small. There is a relation of I01 = NI02 between the actual value I01 of the zero-phase current and the output current I02 of the leakage current detector 8. The output current I02 of the leakage current detector 8 is the first and second
When it flows into the bases of the transistors Tr1 and Tr2, the transistors Tr1 and Tr2 amplify it. When the first transistor Tr1 is on, the smoothing capacitor 4 and the first
Of the transistor Tr1, the coupling capacitor Cb, the electrostatic capacity C of the motor 6 and any one of the switching elements Q2, Q4 and Q6 on the lower side of the inverter circuit 5 causes a noise compensation current to flow and the motor 6 to leak. The current, that is, the zero-phase current is canceled. The current amplification factor of the first transistor Tr1 is set to h fe
Then, the compensation current Ic1 supplied through the first transistor Tr1 is h fe I 02 . Since I 02 is NI 01 , I c1 is represented by the following equation. Ic1 = h fe I 02 = h fe (NI 01 ) The current I 01 on the primary side of the leakage current detector 8 is expressed by the following equation. I 01 = Ic −Ic 1 = Ic −h fe (NI 01 ) Therefore, the value of I 01 is determined by the following equation. I 01 = Ic / (1 + Nh fe ) As is clear from this equation, when the value of Nh fe is increased,
The current (leakage current component) I 01 in the AC power supply line becomes small. Now, if N = 1 and h fe = 100, then I 01 = Ic / 101, and the leakage current of the electric motor 6 can be reduced to 1/100 or less.
【００１４】第２のトランジスタＴr2がオンの時には、
平滑用コンデンサ４とインバ−タ回路５の上側のスイッ
チング素子Ｑ1 、Ｑ3 、Ｑ5 のいずれかと電動機６の静
電容量Ｃと結合コンデンサＣb と第２のトランジスタＴ
r2の閉回路でノイズ補償電流Ｉc1が流れる。このノイズ
補償電流によるノイズ低減効果は第１のトランジスタＴ
r1がオンの時と同様に生じる。図２のノイズ低減制御系
は、比例制御フィ−ドバック系となっており、アクテイ
ブ的に洩れ電流を補償する。なお、結合コンデンサＣb
はＤＣカット用であり、耐圧試験の時に必要になる。When the second transistor Tr2 is on,
The smoothing capacitor 4, any one of the switching elements Q1, Q3 and Q5 on the upper side of the inverter circuit 5, the electrostatic capacitance C of the electric motor 6, the coupling capacitor Cb, and the second transistor T.
The noise compensation current Ic1 flows in the closed circuit of r2. The noise reduction effect of this noise compensation current is the first transistor T
Same as when r1 is on. The noise reduction control system of FIG. 2 is a proportional control feedback system, and actively compensates for leakage current. The coupling capacitor Cb
Is for DC cut, and is required for the withstand voltage test.
【００１５】図３は図２の洩れ電流Ｉc と補償電流Ｉc1
とア−ス線の電流Ｉ0 の測定波形を示す。これから明ら
かなように洩れ電流を補償前の２％以下にすることがで
きる。また、図２の回路では第１及び第２のトランジス
タのＴr1、Ｔr2が互いに逆極性であるから、１つの２次
巻線ｎ2 の出力で２つのトランジスタＴr1、Ｔr2の制御
が可能になり、回路構成が簡単になる。FIG. 3 shows the leakage current Ic and the compensation current Ic1 of FIG.
And the measured waveform of the ground line current I0. As is apparent from this, the leakage current can be reduced to 2% or less before compensation. Also, in the circuit of FIG. 2, since Tr1 and Tr2 of the first and second transistors have opposite polarities, the output of one secondary winding n2 enables control of the two transistors Tr1 and Tr2. Simpler configuration.
【００１６】[0016]
【第２の実施例】次に、図４を参照して第２の実施例の
インバ−タ装置を説明する。但し、図４において図２と
実質的に同一の部分には同一の符号を付してその説明を
省略する。図４のインバ−タ装置は、ノ−マルモ−ドノ
イズ検出器８ａ及びノ−マルノイズを低減するためのノ
イズ補償電流供給回路９ａを有する。ノ−マルモ−ドノ
イズ検出器８ａは、電源１とラインフィルタ２との間に
設けられたトランス即ちＣＴ１１とノイズ成分抽出用フ
ィルタ１２とから成る。ＣＴ１１は、一対の交流電源ラ
インに直列に接続された第１及び第２の１次巻線ｎ1a、
n1b と出力巻線ｎ2とを環状磁性体コア１３に巻回すこ
とににって構成されている。ＣＴ１１の出力巻線ｎ2 に
は１次巻線ｎ1a、ｎ1bの電流の和が得られる。ノ−マル
モ−ドノイズは正常な電流と同様に流れるので、ノイズ
電流と正常電流は周波数によって区別する。電源１は商
用交流電源であって例えば５０Ｈｚの低周波であるの
で、２次巻線ｎ2 に接続されたフィルタ１２は、電源１
の交流電圧の周波数よりも高い周波数成分を抽出するよ
うに構成する。[Second Embodiment] Next, an inverter device according to a second embodiment will be described with reference to FIG. However, in FIG. 4, parts that are substantially the same as those in FIG. 2 are given the same reference numerals, and descriptions thereof will be omitted. The inverter device of FIG. 4 has a normal mode noise detector 8a and a noise compensation current supply circuit 9a for reducing the normal noise. The normal mode noise detector 8a comprises a transformer or CT11 provided between the power source 1 and the line filter 2 and a noise component extracting filter 12. CT11 is a first and a second primary winding n1a connected in series to a pair of AC power supply lines,
It is configured by winding n1b and the output winding n2 around the annular magnetic core 13. The sum of the currents of the primary windings n1a and n1b is obtained in the output winding n2 of CT11. Since normal mode noise flows in the same manner as normal current, noise current and normal current are distinguished by frequency. Since the power supply 1 is a commercial AC power supply and has a low frequency of, for example, 50 Hz, the filter 12 connected to the secondary winding n2 is
The frequency component higher than the frequency of the AC voltage is extracted.
【００１７】フィルタ１２の一方の出力ラインはＮＰＮ
型の第１のトランジスタＴr1のベ−スとＰＮＰ型の第２
のトランジスタＴr2のベ−スとに接続され、他方の出力
ラインは第１及び第２のトランジスタＴr1、Ｔr2の相互
接続点に接続されている。One output line of the filter 12 is an NPN
Type first transistor Tr1 base and PNP type second transistor
Of the transistor Tr2, and the other output line is connected to the interconnection point of the first and second transistors Tr1 and Tr2.
【００１８】第１のトランジスタＴr1のコレクタは図２
と同様に平滑用コンデンサ４の上側端子に接続され、第
２のトランジスタＴr2のコレクタは平滑用コンデンサ４
の下側端子に接続されている。第１及び第２のトランジ
スタＴr1、Ｔr2の相互接続点はラインフィルタ２の２つ
のコンデンサＣ1 、Ｃ2 の相互接続点に接続されてい
る。The collector of the first transistor Tr1 is shown in FIG.
Is connected to the upper terminal of the smoothing capacitor 4, and the collector of the second transistor Tr2 is the smoothing capacitor 4
Is connected to the lower terminal of. The interconnection point of the first and second transistors Tr1 and Tr2 is connected to the interconnection point of the two capacitors C1 and C2 of the line filter 2.
【００１９】図４のインバ−タ回路５のスイッチング素
子Ｑ1 〜Ｑ6 は図２と同様に例えば２０ｋＨｚ程度の高
い周波数でオン・オフされる。図４の回路において、第
１及び第２のトランジスタＴr1、Ｔr2によるノイズ補償
電流の供給が行われない場合には、第１〜第６のスイッ
チング素子Ｑ1 〜Ｑ6 のオン・オフによってノ−マルモ
−ドのノイズが発生する。ノ−マルモ−ドのノイズは、
例えば電源１とリアクトルＬ1 と整流回路３の上側ダイ
オ−ドとインバ−タ回路５の上側のスイッチング素子と
電動機６とインバ−タ回路５の下側のスイッチング素子
と整流回路３の下側のダイオ−ドとリアクトルＬ2 との
閉回路に流れる。リアクトルＬ1 及びＬ2 は高周波ノイ
ズを抑制する作用を有するが、ノイズの全部を除去する
ことはできない。従って、電源１にノイズ電流が流れ
る。そこで、図４の回路ではノ−マルモ−ドノイズ検出
器８ａによって高周波のノ−マルモ−ドノイズを検出
し、これによって第１及び第２のトランジスタＴr1、Ｔ
r2を駆動する。第１のトランジスタＴr1がオンの時に
は、これによってノイズ成分を打ち消すための補償電流
が供給される。The switching elements Q1 to Q6 of the inverter circuit 5 of FIG. 4 are turned on / off at a high frequency of about 20 kHz, as in FIG. In the circuit of FIG. 4, when the noise compensation current is not supplied by the first and second transistors Tr1 and Tr2, the first to sixth switching elements Q1 to Q6 are turned on / off to cause normal noise. Noise is generated. The noise of normal mode is
For example, the power source 1, the reactor L1, the upper diode of the rectifier circuit 3, the upper switching element of the inverter circuit 5, the motor 6, the lower switching element of the inverter circuit 5, and the lower diode of the rectifier circuit 3. -It flows into the closed circuit of the reactor and the reactor L2. Reactors L1 and L2 have a function of suppressing high frequency noise, but cannot completely remove the noise. Therefore, a noise current flows through the power supply 1. Therefore, in the circuit of FIG. 4, high-frequency normal mode noise is detected by the normal mode noise detector 8a, and the first and second transistors Tr1 and Tr1 are thereby detected.
Drive r2. When the first transistor Tr1 is on, this supplies a compensating current for canceling the noise component.
【００２０】[0020]
【変形例】本発明は上述の実施例に限定されるものでな
く、例えば次の変形が可能なものである。 （１） 図２の回路を変形して図５に示すようにライン
フィルタ２を洩れ電流検出器８と整流回路３との間に接
続することができる。 （２） 図２の電源１を三相交流電源とし、整流回路３
を三相ブリッジ整流回路とし、洩れ電流検出器８を三相
の零相電流検出器とすることができる。 （３） スイッチング素子Ｑ1 〜Ｑ6 をバイポ−ラトラ
ンジスタとすること、トランジスタＴr1、Ｔr2をＦＥＴ
等の別の電流制御素子にすることができる。 （４） インバ−タ回路５を単相インバ−タ回路にする
ことができる。 （５） １つの方向のノイズ成分のみを抑制する場合に
は第１及び第２のトランジスタＴr1、Ｔr2の内の一方を
省くことができる。 （６） 誘導電動機６の３つの巻線の中点即ち三相負荷
の中点をグランドに接続する回路に対しても本発明を適
用することができる。[Modifications] The present invention is not limited to the above-described embodiment, and for example, the following modifications are possible. (1) By modifying the circuit of FIG. 2, the line filter 2 can be connected between the leakage current detector 8 and the rectifier circuit 3 as shown in FIG. (2) The power supply 1 of FIG.
Can be a three-phase bridge rectifier circuit, and the leakage current detector 8 can be a three-phase zero-phase current detector. (3) The switching elements Q1 to Q6 are bipolar transistors, and the transistors Tr1 and Tr2 are FETs.
Can be another current control element such as. (4) The inverter circuit 5 can be a single-phase inverter circuit. (5) When suppressing only the noise component in one direction, one of the first and second transistors Tr1 and Tr2 can be omitted. (6) The present invention can be applied to a circuit in which the midpoint of the three windings of the induction motor 6, that is, the midpoint of the three-phase load is connected to the ground.
【図１】従来のインバ−タ装置を示すブロック図であ
る。FIG. 1 is a block diagram showing a conventional inverter device.
【図２】本発明の第１の実施例のインバ−タ装置を示す
回路図である。FIG. 2 is a circuit diagram showing an inverter device according to a first embodiment of the present invention.
【図３】図２の各部の電流を示す波形図である。FIG. 3 is a waveform diagram showing currents in respective parts of FIG.
【図４】第２の実施例のインバ−タ装置を示す回路図で
ある。FIG. 4 is a circuit diagram showing an inverter device according to a second embodiment.
【図５】変形例のインバ−タ装置を示す回路図である。FIG. 5 is a circuit diagram showing an inverter device of a modified example.
５ インバ−タ回路 ６ 誘導電動機 ８ 洩れ電流検出器 Ｔr1、Ｔr2 補償電流供給用トランジスタ 5 Inverter circuit 6 Induction motor 8 Leakage current detector Tr1 and Tr2 Compensation current supply transistor
Claims (3)
て電力を変換する電力変換装置におけるノイズ低減装置
であって、 電力ラインのノイズ電流を検出するノイズ検出手段と、 前記ノイズ検出手段で検出されたノイズ電流に応答して
前記ノイズ電流と逆向きのノイズ補償電流を形成し、こ
のノイズ補償電流を前記電力変換装置のノイズ電流の流
れているラインに供給するノイズ補償電流供給回路とを
備えていることを特徴とするノイズ低減装置。1. A noise reduction device in a power conversion device for converting electric power based on ON / OFF of a switching element, the noise detection device detecting noise current in a power line, and the noise detection device detected by the noise detection device. A noise compensation current supply circuit that forms a noise compensation current in the opposite direction to the noise current in response to the noise current and supplies the noise compensation current to a line in which the noise current flows in the power conversion device. A noise reduction device characterized by the above.
用コンデンサと、 前記平滑用コンデンサに接続されたインバ−タ回路とか
らなり、 前記ノイズ検出手段は、前記インバ−タ回路の負荷から
グランドに流れる洩れ電流を検出するために前記交流電
源と前記整流回路との間に接続された洩れ電流検出手段
であり、 前記ノイズ補償電流供給回路は、前記平滑用コンデンサ
の一端とグランドとの間に接続された第１の電流制御素
子と前記平滑用コンデンサの他端とクランドとの間に接
続された第２の電流制御素子との内の少なくとも一方を
有し、前記第１及び第２の電流制御素子は前記洩れ電流
検出手段で検出された電流に応答してノイズ補償電流を
供給するものであることを特徴とする請求項１記載のノ
イズ低減装置。2. The power converter comprises: a rectifier circuit connected to an AC power source; a smoothing capacitor connected between a pair of DC output terminals of the rectifier circuit; and an inverter connected to the smoothing capacitor. The noise detection means is a leakage current detection means connected between the AC power supply and the rectifier circuit to detect a leakage current flowing from the load of the inverter circuit to the ground. The noise compensation current supply circuit includes a first current control element connected between one end of the smoothing capacitor and the ground and a second current control element connected between the other end of the smoothing capacitor and the ground. At least one of the current control elements is provided, and the first and second current control elements supply a noise compensation current in response to the current detected by the leakage current detection means. Noise reduction apparatus according to claim 1, wherein a.
用コンデンサと、 前記平滑用コンデンサに接続されたインバ−タ回路と、 前記交流電源と前記整流回路との間の電力ライン間に接
続された第１及び第２のラインフィルタ用コンデンサの
直列回路を含むラインフィルタと、から成り、 前記ノイズ検出手段は、前記交流電源と前記第１及び第
２のラインフィルタ用コンデンサの直列回路との間に接
続されたノ−マルモ−ドノイズ検出手段であり、 前記ノイズ補償電流供給回路は、前記平滑用コンデンサ
の一端と前記第１及び第２のラインフィルタ用コンデン
サの相互接続点との間に接続された第１の電流制御素子
と、前記相互接続点と前記平滑用コンデンサの他端との
間に接続された第２の電流制御素子との内の少なくとも
一方を有し、前記第１及び第２の電流制御素子は前記ノ
−マルモ−ドノイズ検出手段で検出されたノ−マルモ−
ドノイズに応答してノイズ補償電流を供給するものであ
ることを特徴とする請求項１記載のノイズ低減装置。3. The power converter comprises a rectifier circuit connected to an AC power source, a smoothing capacitor connected between a pair of DC output terminals of the rectifier circuit, and an inverter connected to the smoothing capacitor. And a line filter including a series circuit of first and second line filter capacitors connected between power lines between the AC power supply and the rectifier circuit, wherein the noise detection means comprises: It is a normal mode noise detection means connected between the AC power supply and the series circuit of the first and second line filter capacitors, wherein the noise compensation current supply circuit is connected to one end of the smoothing capacitor. A first current control element connected between the interconnection point of the first and second line filter capacitors, and the interconnection point and the other end of the smoothing capacitor And a second current control element connected between the first current control element and the second current control element, wherein the first and second current control elements are the normal-mode noise detected by the normal-mode noise detection means.
The noise reduction device according to claim 1, wherein a noise compensation current is supplied in response to the noise.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8099254A JP3044650B2 (en) | 1996-03-27 | 1996-03-27 | Power converter noise reduction device |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| JP8099254A JP3044650B2 (en) | 1996-03-27 | 1996-03-27 | Power converter noise reduction device |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| JPH09266677A true JPH09266677A (en) | 1997-10-07 |
| JP3044650B2 JP3044650B2 (en) | 2000-05-22 |
Family
ID=14242585
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| JP8099254A Expired - Fee Related JP3044650B2 (en) | 1996-03-27 | 1996-03-27 | Power converter noise reduction device |
Country Status (1)
| Country | Link |
|---|---|
| JP (1) | JP3044650B2 (en) |
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