CN109149939A - For low-floor tramcar AuCT light-weight design method - Google Patents

For low-floor tramcar AuCT light-weight design method Download PDF

Info

Publication number
CN109149939A
CN109149939A CN201811108360.8A CN201811108360A CN109149939A CN 109149939 A CN109149939 A CN 109149939A CN 201811108360 A CN201811108360 A CN 201811108360A CN 109149939 A CN109149939 A CN 109149939A
Authority
CN
China
Prior art keywords
resonant
inductance
capacitance
converter
llc
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Granted
Application number
CN201811108360.8A
Other languages
Chinese (zh)
Other versions
CN109149939B (en
Inventor
李骄松
夏猛
马法运
毕京斌
田以涛
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
CRRC Qingdao Sifang Rolling Stock Research Institute Co Ltd
Original Assignee
CRRC Qingdao Sifang Rolling Stock Research Institute Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by CRRC Qingdao Sifang Rolling Stock Research Institute Co Ltd filed Critical CRRC Qingdao Sifang Rolling Stock Research Institute Co Ltd
Priority to CN201811108360.8A priority Critical patent/CN109149939B/en
Publication of CN109149939A publication Critical patent/CN109149939A/en
Application granted granted Critical
Publication of CN109149939B publication Critical patent/CN109149939B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
    • H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M7/23—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only arranged for operation in parallel
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0048—Circuits or arrangements for reducing losses
    • H02M1/0054—Transistor switching losses
    • H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The present invention relates to one kind to be used for low-floor tramcar AuCT light-weight design method, it the steps include: that the minimum voltage stress Buck converter, the LLC that are equipped with minimum voltage stress resonant element are determined to frequency controlled resonant converter and split capacitor three-phase inverter to be sequentially connected in series as subordinate inverter, charger is equipped with DC/DC times to be connected with the output end of minimum voltage stress Buck converter and flows rectifier converter；Determine the resonant inductance L of minimum voltage stress Buck converter2, resonant capacitance Cr, resonant capacitance CsWith minimum output current Io,min；The restrictive condition that LLC determines the design of frequency controlled resonant converter is specified, magnetizing inductance L is selectedmValue, calculate capacitance Cb, transformer primary side leakage inductance Lk, resonant frequency fr, verify LLC and determine whether frequency controlled resonant converter meets verification condition；Middle line inductance L is introduced in split capacitor three-phase invertern, when threephase load imbalance, pass through and introduce center inductance LnEliminate neutral point potential uNSinusoidal perturbation.The AuCT that the present invention designs, power density is high, and volume and weight is small.

Description

For low-floor tramcar AuCT light-weight design method
Technical field
The invention belongs to rail vehicle converter topology fields, are related to tramcar current transformer, specifically, being related to one kind For low-floor tramcar AuCT light-weight design method and based on the AuCT of this method.
Background technique
With the continuous development of urban track traffic, operation cost is low together for low-floor tramcar, energy conservation and environmental protection, route It is laid with the advantages that simple, was widelyd popularize and was developed in recent years.Important set of the AuCT as low-floor tramcar At part, direct current side high-voltage power supply can be converted to AC output and DC output is supplied respectively to automobile-used AC and DC and loads, had with guarantee Rail electric car safe and stable operation.
Low-floor tramcar AuCT is typically located at roof, compared to railcar AuCT, low land Component devices are more compact inside plate tramcar AuCT and require power density bigger；Low-floor tramcar simultaneously AuCT load is complicated, and the load of guest room heat tracing, the drivers' cab single-phase load property responded output voltage quality cause output voltage Distortion.
Referring to Fig. 1, traditional subordinate inverter is isolated using Industrial Frequency Transformer (power: 50Hz), Industrial Frequency Transformer tool Have the advantages that stable, and provides circuit under unbalanced load for zero-sequence current, it is inhibited to unbalance voltage. But using Industrial Frequency Transformer there are volumes it is big, weight is heavy, at high cost and low efficiency the disadvantages of, advocated with tramcar " green Color trip " concept is runed counter to.
Summary of the invention
The present invention in view of the above-mentioned problems existing in the prior art, provides a kind of for low-floor tramcar auxiliary converter Device light-weight design method and AuCT based on this method, can reduce the volume and weight of AuCT, reduce Output voltage degree of unbalancedness.
In order to achieve the above object, the present invention provides one kind sets for the AuCT lightweight of low-floor tramcar Meter method, contains following steps:
The minimum voltage stress Buck converter, the LLC that are equipped with minimum voltage stress resonant element are determined into frequency controlled resonant converter It is sequentially connected in series with split capacitor three-phase inverter as subordinate inverter, charger is equipped with DC/DC times and flows rectifier converter, described DC/DC times is flowed rectifier converter and is connected with the output end of the minimum voltage stress Buck converter；
Determine the resonant inductance L of minimum voltage stress Buck converter2, resonant capacitance Cr, resonant capacitance CsIt is exported with minimum Electric current Io,min；
The restrictive condition that LLC determines the design of frequency controlled resonant converter is specified, magnetizing inductance L is selectedmValue, it is fixed to calculate LLC Capacitance C in frequency controlled resonant converterb, transformer primary side leakage inductance LkAnd resonant frequency fr, and verify the fixed frequency of LLC Whether controlled resonant converter meets following verification conditions: (1) item is realized in the no-voltage conducting for whether meeting transformer primary side switching tube PartIn formula, ZinFor input impedance, CresFor IGBT parallel parasitic capacitance, TrFor resonant Period, i.e.,Uin_minFor input voltage minimum value, Pin_maxFor input power maximum value；(2) the fixed frequency of LLC is humorous Whether the quality factor q of vibration converter meets conditionIn formula, LrsFor magnetizing inductance LmWith original Side leakage inductance LkRatio, i.e.,frsFor resonant frequency frWith switching frequency fsRatio；(3) become in dead time Whether depressor primary current is reversed；(4) whether input impedance is in perception, and there are angle allowances；If aforementioned four verification condition It cannot meet simultaneously, then need to select magnetizing inductance value L againmCalculate until while meeting aforementioned four verification condition；
Middle line inductance L is introduced in split capacitor three-phase invertern, middle line inductance LnCathode and three-phase export filtered electrical The common end of appearance is connected, middle line inductance LnAnode with two input split capacitors between intermediate point be connected, threephase load is not When balance, by introducing center inductance LnEliminate neutral point potential uNSinusoidal perturbation.
Preferably, the resonant inductance L of minimum voltage stress Buck converter is determined2, resonant capacitance Cr, resonant capacitance CsWith Minimum output current Io,minSpecific steps are as follows:
Resonant inductance L2Inductance value selection should meet following conditions:
In formula, trFor switching tube S1Current rise time, trrFor sustained diode4Reverse recovery time, io,peakFor Export current peak, UiFor input voltage；
Resonant capacitance CrWith resonant capacitance CsSelection the following steps are included:
(a) appoint and takeIt brings into formula (2), the minimum output current I under the conditions of acquiringo,min, formula (2) table It is shown as:
In formula, tr-off,maxFor the maximum resonance turn-off time in the case where meeting soft copped wave service condition, provided by designer；
(b) by step (a) value and required minimum output current Io,minIt brings formula (3) into and acquires resonant capacitance Cr, Formula (3) indicates are as follows:
In formula, ω is
(c) with the resonant capacitance C acquired in formula (4) verification step (b)r, formula (4) expression are as follows:
In formula, tfFor switching tube S1Downslope time；
If (d) condition in step (c) is unsatisfactory for, repeatedly step (a)-(c), until meet the condition in step (c), If the condition in step (c) meets, resonant capacitance C is selectedrCapacitance, select when, should be greater than theoretical value, resonant capacitance Cs Capacitance sought with formula (5), formula (5) indicate are as follows:
Preferably, LLC determines the design limitation condition of frequency controlled resonant converter are as follows:
Perception, i.e. Angle (Z must be presented in the input impedance of LLC resonant cavityin)>0；
LLC determines the quality factor q of frequency controlled resonant converter less than 0.005, works in sense to guarantee that LLC determines frequency controlled resonant converter The property area II；
The dead time that LLC determines frequency controlled resonant converter is greater than junction capacity discharge time, while being less than junction capacity discharge time The sum of zero-time is arrived with exciting current resonance.
Preferably, magnetizing inductance L is selectedmValue, calculate LLC and determine capacitance C in frequency controlled resonant converterb, transformation Device primary side leakage inductance LkAnd resonant frequency frSpecific steps are as follows:
Define magnetizing inductance LmValue range be 0.7mH≤Lm≤ 2mH, tentatively selected magnetizing inductance LmValue；
Junction capacity discharge time T is calculated separately by following formula (6), (7)1With exciting current resonance to zero-time Tm:
Tm=tan-1(n2×R/2πfrfrsLm)/π×Tr/2 (7)
In formula, n is transformer turns ratio, and R is transformer primary side equivalent impedance；
Dead time tdead≥T1, (8) calculating current angle according to the following equation
In formula, UoFrequency controlled resonant converter output voltage, I are determined for LLCoFrequency controlled resonant converter, which is determined, for LLC exports electric current；
Guarantee that LLC determines the work of frequency controlled resonant converter in the perceptual area II, following limitation should be met:
It calculates LLC and determines capacitance C in frequency controlled resonant converterb, transformer primary side leakage inductance LkAnd resonant frequency Rate fr。
Preferably, when threephase load balances, neutral point potential uNAre as follows:
In formula, udcThe output voltage of frequency controlled resonant converter is determined for LLC；
When accessing unbalanced load, neutral point potential uNIt shifts, i.e.,Middle line inductance L when introducingn, Neutral point potential expression formula is as follows:
In formula, umFor three-phase output voltage maximum value, Z is load impedance, CinFor three-phase output filter capacitor, θ is offset Angle；
When threephase load imbalance, neutral point potential has sinusoidal perturbation, by introducing center inductanceIt eliminates The disturbance, is restored to neutral point potential
In order to achieve the above object, the present invention also provides a kind of low-floor tramcar subordinate inverters, based on above-mentioned Design method, including subordinate inverter and charger, the subordinate inverter include minimum voltage stress Buck converter, LLC Determine frequency controlled resonant converter and split capacitor three-phase inverter, minimum voltage stress Buck converter, LLC determine frequency controlled resonant converter and Split capacitor three-phase inverter is sequentially connected in series, and the minimum voltage stress Buck converter is equipped with minimum voltage stress resonance list Member, the minimum voltage stress resonant element is by resonant inductance L2, resonant capacitance CrWith resonant capacitance CsComposition；The charger Rectifier converter is flowed equipped with DC/DC times, described DC/DC times is flowed rectifier converter and the minimum voltage stress Buck converter Output end is connected.
Preferably, the minimum voltage stress Buck converter further includes input filter inductance L1, switching tube S1, input filter Wave capacitor C1, four freewheeling diodes, afterflow inductance L3, two output filter capacitors being connected in series and two series connections Equalizing resistance；Input filter capacitor C1Anode respectively with input filter inductance L1Cathode, switching tube S1The pole C, resonant capacitance CrAnode be connected, switching tube S1The pole M and resonant inductance L2Anode be connected, switching tube S1The pole E respectively with resonant capacitance Cr Cathode, sustained diode1Anode, sustained diode3Cathode be connected；Sustained diode2Anode respectively with resonance Inductance L2Cathode, afterflow inductance L3Anode, resonant capacitance CsCathode, sustained diode4Anode be connected；Two pole of afterflow Pipe D1Cathode respectively with sustained diode2Anode, resonant capacitance anode be connected；Sustained diode2Cathode respectively with Sustained diode4Cathode, output filter capacitor C3Cathode be connected；Afterflow inductance L3With output filter capacitor C2Positive phase Even, equalizing resistance RC1It is connected in parallel on output filter capacitor C2Both ends, equalizing resistance RC2It is connected in parallel on output filter capacitor C3Both ends.
Preferably, it includes switching tube S that described DC/DC times, which is flowed rectifier converter,2, capacitance Cc, transformer T2, afterflow electricity Feel La, afterflow inductance Lb, output filter capacitor C6, counnter attack diode D9With two diodes；Switching tube S2The pole M and capacitance CcAnode be connected, capacitance CcCathode and transformer T2The v of primary sideaEnd is connected；Transformer T2The v of primary sidebEnd and output Filter capacitor C2With output filter capacitor C3Midpoint be connected；Transformer T2The v on secondary sidecEnd respectively with afterflow inductance LaCathode, Diode D8Anode be connected；Transformer T2The v on secondary sidedEnd respectively with afterflow inductance LbCathode, diode D7Anode be connected, Diode D7With diode D8Cathode with output filter capacitor C6Cathode be connected；Afterflow inductance LaWith afterflow inductance LbJust Pole respectively with output filter capacitor C6Anode, counnter attack diode D9Anode be connected.
Preferably, it includes two switching tubes being connected in parallel, capacitance C that the LLC, which determines frequency controlled resonant converter,b, transformation Device T1With two secondary side rectifier diodes, transformer T1With capacitance CbForm LLC resonant cavity；Switching tube S3With switching tube S4Across It connects between the positive negative output bus of minimum voltage stress Buck converter；Switching tube S3The pole M and capacitance CbPositive phase Even, switching tube S4The pole M and transformer T1The v of primary sidebEnd is connected, capacitance CbCathode and transformer T1The v of primary sideaHold phase Even；Transformer T1The v on secondary sidecEnd and pair side rectifier diode D5Intermediate point connection, transformer T1The v on secondary sidedEnd and secondary side are whole Flow diode D6Intermediate point connection.
Preferably, the split capacitor three-phase inverter includes the input split capacitor of two series connections, three parallel connections The switching tube of connection, three output inductors, three star-like connections output filter capacitor, middle inductor LnWith middle line capacitance Cn；Input split capacitor C4Anode with pair side rectifier diode D6Anode connection, input split capacitor C5Cathode and secondary side Rectifier diode D6Cathode connection；Switching tube S5, switching tube S6With switching tube S7Respectively with input split capacitor C4With input point Split capacitor C5The series circuit of composition is connected in parallel, switching tube S5The pole M and output inductor LuAnode be connected, switching tube S6The pole M and output inductor LvAnode be connected, switching tube S7The pole M and output inductor LwAnode be connected, output Filter capacitor Cu, output filter capacitor CvWith output filter capacitor CwCommon end and middle line capacitance CnAnode be connected, middle line electricity Hold CnCathode and middle line inductance LnCathode be connected, middle line inductance LnAnode with input split capacitor C4With input division electricity Hold C5Between intermediate point be connected.
Compared with prior art, the advantages and positive effects of the present invention are:
(1) design method of the present invention carries out light-weight design, light-weight design to low-floor tramcar AuCT For low-floor tramcar AuCT afterwards compared with existing traditional power frequency AuCT, power density is high, volume and Weight is small.
(2) present invention is designed prime Buck converter, and prime Buck converter is humorous equipped with minimum voltage stress The minimum voltage stress Buck converter of vibration unit utilizes passive flexible switch to realize that switch tube zero voltage turn-on and no-voltage close It is disconnected, and additional voltage stress is not introduced during realizing Sofe Switch, slow down the voltage at switching tube shutdown moment Stress.
(3) present invention needs the defect of frequency conversion for LLC converter, introduces Buck pressure regulation link in prime and realizes that LLC becomes Parallel operation determines frequency modulation system, and magnetic element is facilitated to design, when encountering input voltage or load variation, by adjusting prime Buck The output voltage of converter adapts to the variation；LLC converter design of the present invention is that LLC determines frequency controlled resonant converter, can be realized original The no-voltage conducting (i.e. ZVS) of side power device and low current shutdown, realize secondary side rectifier diode zero voltage turn-off (i.e. ZCS), the power density of subordinate inverter is greatly improved, interference (i.e. EMI) is reduced.
(4) split capacitor three-phase inverter of the present invention introduces middle line inductance in three phase inverter bridge, inhibits zero-sequence current, reduces Output voltage degree of unbalancedness improves system to the adaptability of unbalanced load, enhances the robustness of system.
(5) subordinate inverter of low-floor tramcar AuCT of the present invention uses Buck+LLC+INV thtee-stage shiplock Structure, charger are connected to Buck converter outlet side, when rear class inverter breaks down (or charger breaks down), fill Motor (or inverter) can work normally, and not influenced by non-faulty inverter (or charger).
Detailed description of the invention
Fig. 1 is the circuit diagram that AuCT is isolated in the existing low-floor tramcar power frequency of the present invention.
Fig. 2 is the circuit diagram of low-floor tramcar AuCT of the present invention.
Fig. 3 is the state diagram of minimum voltage stress Buck converter main element of the present invention.
Fig. 4 is the working principle waveform diagram that LLC of the present invention determines frequency controlled resonant converter.
In figure, 1, minimum voltage stress Buck converter, 2, LLC determine frequency controlled resonant converter, 3, split capacitor three-phase inversion Device, 4, DC/DC times flow rectifier converter.
Specific embodiment
In the following, the present invention is specifically described by illustrative embodiment.It should be appreciated, however, that not into one In the case where step narration, element, structure and features in an embodiment can also be advantageously incorporated into other embodiments In.
Present invention discloses one kind to be used for low-floor tramcar AuCT light-weight design method, contains following step It is rapid:
S1, the minimum voltage stress Buck converter, the LLC that are equipped with minimum voltage stress resonant element are determined into frequency resonant transformation Device and split capacitor three-phase inverter are sequentially connected in series as subordinate inverter, and charger is equipped with DC/DC times and flows rectifier converter, institute It states DC/DC times and flows rectifier converter and be connected with the output end of the minimum voltage stress Buck converter.
S2, the resonant inductance L for determining minimum voltage stress Buck converter2, resonant capacitance Cr, resonant capacitance CsAnd minimum Export electric current Io,min；The specific steps are that:
(1) resonant inductance L2Inductance value selection should meet following conditions:
In formula, trFor switching tube S1Current rise time, trrFor sustained diode4Reverse recovery time, io,peakFor Export current peak, UiFor input voltage；
(2) resonant capacitance CrWith resonant capacitance CsSelection the following steps are included:
(a) appoint and takeIt brings into formula (2), the minimum output current I under the conditions of acquiringo,min, formula (2) table It is shown as:
In formula, tr-off,maxFor the maximum resonance turn-off time in the case where meeting soft copped wave service condition, provided by designer；
(b) by step (a) value and required minimum output current Io,minIt brings formula (3) into and acquires resonant capacitance Cr, Formula (3) indicates are as follows:
In formula, ω is
(c) with the resonant capacitance C acquired in formula (4) verification step (b)r, formula (4) expression are as follows:
In formula, tfFor switching tube S1Downslope time；
If (d) condition in step (c) is unsatisfactory for, repeatedly step (a)-(c), until meet the condition in step (c), If the condition in step (c) meets, resonant capacitance C is selectedrCapacitance, select when, should be greater than theoretical value, resonant capacitance Cs Capacitance sought with formula (5), formula (5) indicate are as follows:
The working state figure of minimum voltage stress Buck converter said elements is referring to Fig. 3.
S3, clear LLC determine the restrictive condition of frequency controlled resonant converter design, select magnetizing inductance LmValue, calculate LLC Determine the capacitance C in frequency controlled resonant converterb, transformer primary side leakage inductance LkAnd resonant frequency fr, and it is fixed to verify LLC Whether frequency controlled resonant converter meets following verification conditions: (1) the no-voltage conducting for whether meeting transformer primary side switching tube is realized ConditionIn formula, ZinFor input impedance, CresFor IGBT parallel parasitic capacitance, TrIt is humorous for resonant cavity It shakes the period, i.e.,Uin_minFor input voltage minimum value, Pin_maxFor input power maximum value；(2) the fixed frequency of LLC Whether the quality factor q of controlled resonant converter meets conditionIn formula, LrsFor magnetizing inductance LmWith Primary side leakage inductance LkRatio, i.e.,frsFor resonant frequency frWith switching frequency fsRatio；(3) in dead time Whether primary side current of transformer is reversed；(4) whether input impedance is in perception, and there are angle allowances；If aforementioned four verifying item Part cannot meet simultaneously, then need to select magnetizing inductance value L againmCalculate until while meeting aforementioned four verifying item Part；
S4, middle line inductance L is introduced in split capacitor three-phase invertern, middle line inductance LnCathode and three-phase output filter The common end of capacitor is connected, middle line inductance LnAnode with two input split capacitors between intermediate point be connected, threephase load When uneven, by introducing center inductance LnEliminate neutral point potential uNSinusoidal perturbation.
In above-mentioned steps S3, LLC determines the design limitation condition of frequency controlled resonant converter are as follows:
Perception, i.e. Angle (Z must be presented in the input impedance of LLC resonant cavityin)>0；
LLC determines the quality factor q of frequency controlled resonant converter less than 0.005, works in sense to guarantee that LLC determines frequency controlled resonant converter The property area II；Static exciter inductance numeric area is 1mH effect in practical application, and primary side leakage inductance is several μ H, the two ratio Lrs About several hundred, this results in Mgain=f (frs) curve (wherein, Mgain indicate resonant cavity gain) is in equal gain transformation range Under, frequency changes greatly, and perception, capacitive reactances line of demarcation move to left, therefore sets the necessary very little of clocking requirement quality factor q, to protect Demonstrate,prove work and the perception area II.
The dead time that LLC determines frequency controlled resonant converter is greater than junction capacity discharge time, while being less than junction capacity discharge time The sum of zero-time is arrived with exciting current resonance, to guarantee that LLC determines the no-voltage of transformer primary side switching tube in frequency controlled resonant converter (i.e. ZVS) is connected and realizes condition.
In above-mentioned steps S3, magnetizing inductance L is selectedmValue, calculate LLC and determine capacitance in frequency controlled resonant converter Cb, transformer primary side leakage inductance LkAnd resonant frequency frSpecific steps are as follows:
(1) magnetizing inductance L is definedmValue range be 0.7mH≤Lm≤ 2mH, tentatively selected magnetizing inductance LmValue；
(2) junction capacity discharge time T is calculated separately by following formula (6), (7)1With exciting current resonance to zero-time Tm:
Tm=tan-1(n2×R/2πfrfrsLm)/π×Tr/2 (7)
In formula, n is transformer turns ratio, and R is transformer primary side equivalent impedance；
(3) dead time tdead≥T1, (8) calculating current angle according to the following equation
In formula, UoFrequency controlled resonant converter output voltage, I are determined for LLCoFrequency controlled resonant converter, which is determined, for LLC exports electric current；
(4) guarantee that LLC determines the work of frequency controlled resonant converter in the perceptual area II, following limitation should be met:
(5) it calculates LLC and determines capacitance C in frequency controlled resonant converterb, transformer primary side leakage inductance LkAnd resonant cavity is humorous Vibration frequency fr。
In above-mentioned steps S4, when threephase load balances, neutral point potential uNAre as follows:
In formula, udcThe output voltage of frequency controlled resonant converter is determined for LLC；
When accessing unbalanced load, neutral point potential uN shifts, i.e.,Middle line inductance L when introducingn, Neutral point potential uNExpression formula is as follows:
In formula, umFor three-phase output voltage maximum value, Z is load impedance, CinFor three-phase output filter capacitor, θ is offset Angle；
When threephase load imbalance, neutral point potential uNThere is sinusoidal perturbation, by introducing center inductanceDisappear Except the disturbance, make neutral point potential uNIt is restored toTo reduce non-equilibrium among three phase voltages.
When Buck converter, LLC determine frequency controlled resonant converter and the design of split capacitor three-phase inverter, no sequencing.Cause This, the sequence of above-mentioned steps S2, S3, S4 can be interchanged.
Referring to fig. 2, the present invention also provides a kind of low-floor tramcar subordinate inverters, are based on above-mentioned design method, Including subordinate inverter and charger, the subordinate inverter includes that minimum voltage stress Buck converter 1, LLC determine frequency resonance Converter 2 and split capacitor three-phase inverter 3, minimum voltage stress Buck converter 1, LLC determine frequency controlled resonant converter 2 and division Capacitor three-phase inverter 3 is sequentially connected in series, and the minimum voltage stress Buck converter 1 is equipped with minimum voltage stress resonant element, The minimum voltage stress resonant element is by resonant inductance L2, resonant capacitance CrWith resonant capacitance CsComposition；The charger is equipped with DC/DC times is flowed rectifier converter 4, and described DC/DC times is flowed rectifier converter 4 and the minimum voltage stress Buck converter 1 Output end is connected.
With continued reference to Fig. 2, the minimum voltage stress Buck converter further includes input filter inductance L1, switching tube S1, it is defeated Enter filter capacitor C1, four freewheeling diodes, afterflow inductance L3, two output filter capacitors being connected in series and two series connection companies The equalizing resistance connect；Input filter capacitor C1Anode respectively with input filter inductance L1Cathode, switching tube S1The pole C, resonance Capacitor CrAnode be connected, switching tube S1The pole M and resonant inductance L2Anode be connected, switching tube S1The pole E respectively with resonance electricity Hold CrCathode, sustained diode1Anode, sustained diode3Cathode be connected；Sustained diode2Anode respectively with Resonant inductance L2Cathode, afterflow inductance L3Anode, resonant capacitance CsCathode, sustained diode4Anode be connected；Afterflow Diode D1Cathode respectively with sustained diode2Anode, resonant capacitance anode be connected；Sustained diode2Cathode point Not and sustained diode4Cathode, output filter capacitor C3Cathode be connected；Afterflow inductance L3With output filter capacitor C2Just Extremely it is connected, equalizing resistance RC1It is connected in parallel on output filter capacitor C2Both ends, equalizing resistance RC2It is connected in parallel on output filter capacitor C3's Both ends.Utilize resonant inductance L2, resonant capacitance CrWith resonant capacitance CsSwitch tube S1Voltage, current waveform carry out shaping and Softening, to achieve the purpose that Sofe Switch.Equalizing resistance RC1It is connected in parallel on output filter capacitor C2Both ends, equalizing resistance RC2It is in parallel In output filter capacitor C3Both ends, play the role of pressure.
With continued reference to Fig. 2, it includes switching tube S that described DC/DC times, which is flowed rectifier converter,2, capacitance Cc, transformer T2, it is continuous Galvanic electricity sense La, afterflow inductance Lb, output filter capacitor C6, counnter attack diode D9With two diodes；Switching tube S2The pole M and blocking Capacitor CcAnode be connected, capacitance CcCathode and transformer T2The v of primary sideaEnd is connected；Transformer T2The v of primary sidebEnd with Output filter capacitor C2With output filter capacitor C3Midpoint be connected；Transformer T2The v on secondary sidecEnd respectively with afterflow inductance LaIt is negative Pole, diode D8Anode be connected；Transformer T2The v on secondary sidedEnd respectively with afterflow inductance LbCathode, diode D7Anode phase Even, diode D7With diode D8Cathode with output filter capacitor C6Cathode be connected；Afterflow inductance LaWith afterflow inductance Lb Anode respectively with output filter capacitor C6Anode, counnter attack diode D9Anode be connected.
With continued reference to Fig. 2, it includes two switching tubes being connected in parallel, capacitance C that the LLC, which determines frequency controlled resonant converter,b、 Transformer T1With two secondary side rectifier diodes, transformer T1With capacitance CbForm LLC resonant cavity, G1、G2、G3、G4To open Close the driving signal of pipe；Switching tube S3With switching tube S4It is connected across between the positive negative output bus of minimum voltage stress Buck converter； Switching tube S3The pole M and capacitance CbAnode be connected, switching tube S4The pole M and transformer T1The v of primary sidebEnd is connected, blocking Capacitor CbCathode and transformer T1The v of primary sideaEnd is connected, and transformer integrates leakage inductance LkBelong to transformer T1Ontology；Transformer T1 The v on secondary sidecEnd and pair side rectifier diode D5Intermediate point connection, transformer T1The v on secondary sidedEnd and pair side rectifier diode D6's Intermediate point connection.Referring to fig. 4, driving signal G1With driving signal G4It is identical, driving signal G2With driving signal G3It is identical, resonance Chamber switching frequency is higher than LLC and determines the switching frequency of frequency controlled resonant converter, to guarantee that harmonic period is less than switch periods, for secondary side Diode zero-current switching creates conditions；By output voltage UoConvert transformer T1Primary side, and using the voltage to transformer T1 Excitation, demagnetizing effect, realize primary side switch pipe no-voltage conducting and low current shutdown.
With continued reference to Fig. 2, the split capacitor three-phase inverter includes the input split capacitor of two series connections, three The switching tube that is connected in parallel, three output inductors, three star-like connections output filter capacitor, middle inductor LnAnd middle line Capacitor Cn；Input split capacitor C4Anode with pair side rectifier diode D6Anode connection, input split capacitor C5Cathode with Secondary side rectifier diode D6Cathode connection；Switching tube S5, switching tube S6With switching tube S7Respectively with input split capacitor C4With it is defeated Enter split capacitor C5The series circuit of composition is connected in parallel, switching tube S5The pole M and output inductor LuAnode be connected, open Close pipe S6The pole M and output inductor LvAnode be connected, switching tube S7The pole M and output inductor LwAnode be connected, Output filter capacitor Cu, output filter capacitor CvWith output filter capacitor CwCommon end and middle line capacitance CnAnode be connected, in Line capacitance CnCathode and middle line inductance LnCathode be connected, middle line inductance LnAnode with input split capacitor C4With input point Split capacitor C5Between intermediate point be connected.
Above-described embodiment is used to explain the present invention, rather than limits the invention, in spirit and right of the invention It is required that protection scope in, to any modifications and changes for making of the present invention, both fall within protection scope of the present invention.

Claims (10)

1. one kind is used for low-floor tramcar AuCT light-weight design method, which is characterized in that contain following steps:
The minimum voltage stress Buck converter, the LLC that are equipped with minimum voltage stress resonant element are determined into frequency controlled resonant converter and divided It splits capacitor three-phase inverter to be sequentially connected in series as subordinate inverter, charger is equipped with DC/DC times and flows rectifier converter, the DC/ DC times is flowed rectifier converter and is connected with the output end of the minimum voltage stress Buck converter；
Determine the resonant inductance L of minimum voltage stress Buck converter2, resonant capacitance Cr, resonant capacitance CsAnd minimum output current Io,min；
The restrictive condition that LLC determines the design of frequency controlled resonant converter is specified, magnetizing inductance L is selectedmValue, calculate LLC and determine frequency resonance Capacitance C in converterb, transformer primary side leakage inductance LkAnd resonant frequency fr, and verify LLC and determine the change of frequency resonance Whether parallel operation meets following verification conditions: (1) whether meeting the no-voltage conducting realization condition of transformer primary side switching tubeIn formula, ZinFor input impedance, CresFor IGBT parallel parasitic capacitance, TrFor resonant week Phase, i.e.,Uin_minFor input voltage minimum value, Pin_maxFor input power maximum value；(2) LLC determines frequency resonance Whether the quality factor q of converter meets conditionIn formula, LrsFor magnetizing inductance LmWith primary side Leakage inductance LkRatio, i.e.,frsFor resonant frequency frWith switching frequency fsRatio；(3) transformation in dead time Whether device primary current is reversed；(4) whether input impedance is in perception, and there are angle allowances；If aforementioned four verification condition is not It can meet simultaneously, then need to select magnetizing inductance value L againmCalculate until while meeting aforementioned four verification condition；
Middle line inductance L is introduced in split capacitor three-phase invertern, middle line inductance LnCathode and three-phase output filter capacitor Common end is connected, middle line inductance LnAnode with two input split capacitors between intermediate point be connected, threephase load imbalance When, by introducing center inductance LnEliminate neutral point potential uNSinusoidal perturbation.
2. being used for low-floor tramcar AuCT light-weight design method as described in claim 1, which is characterized in that Determine the resonant inductance L of minimum voltage stress Buck converter2, resonant capacitance Cr, resonant capacitance CsWith minimum output current Io,min Specific steps are as follows:
Resonant inductance L2Inductance value selection should meet following conditions:
In formula, trFor switching tube S1Current rise time, trrFor sustained diode4Reverse recovery time, io,peakFor output Current peak, UiFor input voltage；
Resonant capacitance CrWith resonant capacitance CsSelection the following steps are included:
(a) appoint and takeIt brings into formula (2), the minimum output current I under the conditions of acquiringo,min, formula (2) expression are as follows:
In formula, tr-off,maxFor the maximum resonance turn-off time in the case where meeting soft copped wave service condition, provided by designer；
(b) by step (a) value and required minimum output current Io,minIt brings formula (3) into and acquires resonant capacitance Cr, formula (3) it indicates are as follows:
In formula, ω is
(c) with the resonant capacitance C acquired in formula (4) verification step (b)r, formula (4) expression are as follows:
In formula, tfFor switching tube S1Downslope time；
If (d) condition in step (c) is unsatisfactory for, repeatedly step (a)-(c), until meeting the condition in step (c), if step Suddenly the condition in (c) meets, then selectes resonant capacitance CrCapacitance, select when, should be greater than theoretical value, resonant capacitance CsElectricity Capacitance is sought with formula (5), and formula (5) indicates are as follows:
3. being used for low-floor tramcar AuCT light-weight design method as claimed in claim 2, which is characterized in that LLC determines the design limitation condition of frequency controlled resonant converter are as follows:
Perception, i.e. Angle (Z must be presented in the input impedance of LLC resonant cavityin)>0；
LLC determines the quality factor q of frequency controlled resonant converter less than 0.005, works in perceptual II to guarantee that LLC determines frequency controlled resonant converter Area；
The dead time that LLC determines frequency controlled resonant converter is greater than junction capacity discharge time, while being less than junction capacity discharge time and encouraging Magnetic current resonance arrives the sum of zero-time.
4. being used for low-floor tramcar AuCT light-weight design method as claimed in claim 3, which is characterized in that Selected magnetizing inductance LmValue, calculate LLC and determine capacitance C in frequency controlled resonant converterb, transformer primary side leakage inductance LkWith And resonant frequency frSpecific steps are as follows:
Define magnetizing inductance LmValue range be 0.7mH≤Lm≤ 2mH, tentatively selected magnetizing inductance LmValue；
Junction capacity discharge time T is calculated separately by following formula (6), (7)1With exciting current resonance to zero-time Tm:
Tm=tan-1(n2×R/2πfrfrsLm)/π×Tr/2 (7)
In formula, n is transformer turns ratio, and R is transformer primary side equivalent impedance；
Dead time tdead≥T1, (8) calculating current angle according to the following equation
In formula, UoFrequency controlled resonant converter output voltage, I are determined for LLCoFrequency controlled resonant converter, which is determined, for LLC exports electric current；
Guarantee that LLC determines the work of frequency controlled resonant converter in the perceptual area II, following limitation should be met:
It calculates LLC and determines capacitance C in frequency controlled resonant converterb, transformer primary side leakage inductance LkAnd resonant frequency fr。
5. being used for low-floor tramcar AuCT light-weight design method as claimed in claim 4, which is characterized in that When threephase load balances, neutral point potential uNAre as follows:
In formula, udcThe output voltage of frequency controlled resonant converter is determined for LLC；
When accessing unbalanced load, neutral point potential uN shifts, i.e.,Middle line inductance L when introducingn, neutral Point current potential expression formula is as follows:
In formula, umFor three-phase output voltage maximum value, Z is load impedance, CinFor three-phase output filter capacitor, θ is deviation angle；
When threephase load imbalance, neutral point potential has sinusoidal perturbation, by introducing center inductanceThis is eliminated to disturb It is dynamic, it is restored to neutral point potential
6. a kind of low-floor tramcar AuCT, based on auxiliary for low-floor tramcar as described in claim 1 Help current transformer light-weight design method, including subordinate inverter and charger, which is characterized in that the subordinate inverter includes most Small voltage stress Buck converter, LLC determine frequency controlled resonant converter and split capacitor three-phase inverter, and minimum voltage stress Buck becomes Parallel operation, LLC determine frequency controlled resonant converter and split capacitor three-phase inverter is sequentially connected in series, the minimum voltage stress Buck converter Equipped with minimum voltage stress resonant element, the minimum voltage stress resonant element is by resonant inductance L2, resonant capacitance CrAnd resonance Capacitor CsComposition；The charger is equipped with DC/DC times and flows rectifier converter, described DC/DC times flow rectifier converter and it is described most The output end of small voltage stress Buck converter is connected.
7. low-floor tramcar AuCT as claimed in claim 6, which is characterized in that the minimum voltage stress Buck converter further includes input filter inductance L1, switching tube S1, input filter capacitor C1, four freewheeling diodes, afterflow inductance L3, two output filter capacitors being connected in series and two series connections equalizing resistances；Input filter capacitor C1Anode respectively With input filter inductance L1Cathode, switching tube S1The pole C, resonant capacitance CrAnode be connected, switching tube S1The pole M and resonance Inductance L2Anode be connected, switching tube S1The pole E respectively with resonant capacitance CrCathode, sustained diode1Anode, afterflow two Pole pipe D3Cathode be connected；Sustained diode2Anode respectively with resonant inductance L2Cathode, afterflow inductance L3It is positive, humorous Shake capacitor CsCathode, sustained diode4Anode be connected；Sustained diode1Cathode respectively with sustained diode2Sun Pole, the anode of resonant capacitance are connected；Sustained diode2Cathode respectively with sustained diode4Cathode, output filter capacitor C3Cathode be connected；Afterflow inductance L3With output filter capacitor C2Anode be connected, equalizing resistance RC1It is connected in parallel on output filter capacitor C2Both ends, equalizing resistance RC2It is connected in parallel on output filter capacitor C3Both ends.
8. low-floor tramcar AuCT as claimed in claim 7, which is characterized in that described DC/DC times is flowed rectification Converter includes switching tube S2, capacitance Cc, transformer T2, afterflow inductance La, afterflow inductance Lb, output filter capacitor C6, it is anti- Anti- diode D9With two diodes；Switching tube S2The pole M and capacitance CcAnode be connected, capacitance CcCathode with Transformer T2The v of primary sideaEnd is connected；Transformer T2The v of primary sidebEnd and output filter capacitor C2With output filter capacitor C3Midpoint It is connected；Transformer T2The v on secondary sidecEnd respectively with afterflow inductance LaCathode, diode D8Anode be connected；Transformer T2Secondary side vdEnd respectively with afterflow inductance LbCathode, diode D7Anode be connected, diode D7With diode D8Cathode with output Filter capacitor C6Cathode be connected；Afterflow inductance LaWith afterflow inductance LbAnode respectively with output filter capacitor C6It is positive, anti- Anti- diode D9Anode be connected.
9. low-floor tramcar AuCT as claimed in claim 6, which is characterized in that the LLC determines the change of frequency resonance Parallel operation includes two switching tubes being connected in parallel, capacitance Cb, transformer T1With two secondary side rectifier diodes, transformer T1 With capacitance CbForm LLC resonant cavity；Switching tube S3With switching tube S4It is positive and negative defeated to be connected across minimum voltage stress Buck converter Out between bus；Switching tube S3The pole M and capacitance CbAnode be connected, switching tube S4The pole M and transformer T1The v of primary sideb End is connected, capacitance CbCathode and transformer T1The v of primary sideaEnd is connected；Transformer T1The v on secondary sidecEnd and secondary side rectification two Pole pipe D5Intermediate point connection, transformer T1The v on secondary sidedEnd and pair side rectifier diode D6Intermediate point connection.
10. low-floor tramcar AuCT as claimed in claim 9, which is characterized in that the split capacitor three-phase Inverter includes the input split capacitor of two series connections, three switching tubes being connected in parallel, three output inductors, three Output filter capacitor, the middle inductor L of a star-like connectionnWith middle line capacitance Cn；Input split capacitor C4Anode rectified with secondary side Diode D6Anode connection, input split capacitor C5Cathode and pair side rectifier diode D6Cathode connection；Switching tube S5、 Switching tube S6With switching tube S7Respectively with input split capacitor C4With input split capacitor C5The series circuit of composition is connected in parallel, Switching tube S5The pole M and output inductor LuAnode be connected, switching tube S6The pole M and output inductor LvPositive phase Even, switching tube S7The pole M and output inductor LwAnode be connected, output filter capacitor Cu, output filter capacitor CvAnd output Filter capacitor CwCommon end and middle line capacitance CnAnode be connected, middle line capacitance CnCathode and middle line inductance LnCathode phase Even, middle line inductance LnAnode with input split capacitor C4With input split capacitor C5Between intermediate point be connected.
CN201811108360.8A 2018-09-21 2018-09-21 Lightweight design method for auxiliary converter of low-floor tramcar Active CN109149939B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201811108360.8A CN109149939B (en) 2018-09-21 2018-09-21 Lightweight design method for auxiliary converter of low-floor tramcar

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201811108360.8A CN109149939B (en) 2018-09-21 2018-09-21 Lightweight design method for auxiliary converter of low-floor tramcar

Publications (2)

Publication Number Publication Date
CN109149939A true CN109149939A (en) 2019-01-04
CN109149939B CN109149939B (en) 2020-06-05

Family

ID=64823340

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201811108360.8A Active CN109149939B (en) 2018-09-21 2018-09-21 Lightweight design method for auxiliary converter of low-floor tramcar

Country Status (1)

Country Link
CN (1) CN109149939B (en)

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110932533A (en) * 2019-12-06 2020-03-27 合肥工业大学 Topological high-frequency common-mode voltage suppression method for common-neutral open-winding motor control converter
CN113258780A (en) * 2021-05-11 2021-08-13 中车青岛四方车辆研究所有限公司 Parameter selection method and control method for tramcar auxiliary power supply DC/DC circuit

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101249801A (en) * 2008-03-31 2008-08-27 北京交通大学 Automobile auxiliary current transformer
US20110090717A1 (en) * 2009-10-21 2011-04-21 Myongji University Industry And Academia Cooperation Foundation Two-stage insulated bidirectional DC/DC power converter using a constant duty ratio LLC resonant converter
CN206575329U (en) * 2017-03-02 2017-10-20 深圳市斯泰迪新能源科技有限公司 A kind of BUCK converter circuits
CN206650590U (en) * 2017-04-24 2017-11-17 株洲中车时代电气股份有限公司 Low floor vehicle AuCT

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101249801A (en) * 2008-03-31 2008-08-27 北京交通大学 Automobile auxiliary current transformer
US20110090717A1 (en) * 2009-10-21 2011-04-21 Myongji University Industry And Academia Cooperation Foundation Two-stage insulated bidirectional DC/DC power converter using a constant duty ratio LLC resonant converter
CN206575329U (en) * 2017-03-02 2017-10-20 深圳市斯泰迪新能源科技有限公司 A kind of BUCK converter circuits
CN206650590U (en) * 2017-04-24 2017-11-17 株洲中车时代电气股份有限公司 Low floor vehicle AuCT

Non-Patent Citations (1)

* Cited by examiner, † Cited by third party
Title
饶沛南等: "一种新型低地板车用轻量化高频辅助变流器的研制", 《机车电传动》 *

Cited By (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN110932533A (en) * 2019-12-06 2020-03-27 合肥工业大学 Topological high-frequency common-mode voltage suppression method for common-neutral open-winding motor control converter
CN110932533B (en) * 2019-12-06 2021-08-10 合肥工业大学 Topological high-frequency common-mode voltage suppression method for common-neutral open-winding motor control converter
CN113258780A (en) * 2021-05-11 2021-08-13 中车青岛四方车辆研究所有限公司 Parameter selection method and control method for tramcar auxiliary power supply DC/DC circuit

Also Published As

Publication number Publication date
CN109149939B (en) 2020-06-05

Similar Documents

Publication Publication Date Title
CN105610336B (en) MMC type multiport electric power electric transformer based on double capacitance modules
CN104967300B (en) A kind of pre-charge circuit and photovoltaic DC-to-AC converter
CN106059306B (en) A kind of multiple-unit diode capacitance network high-gain full-bridge isolated DC converter
CN102301577A (en) Converter for single-phase and three-phase operation, d.c. voltage supply and battery charger
CN103227575A (en) Three-phase soft-switched PCF rectifiers
CN102891611A (en) Five-level power converter, and control method and control device for five-level power converter
CN204334330U (en) A kind of modularization high-voltage power supply circuit
CN101902129A (en) Current-type multi-resonance direct current (DC) converter
CN107800312B (en) A kind of output ripple and low pfc converter
Na et al. Active power filter for single-phase Quasi-Z-source integrated on-board charger
CN102361408A (en) Non-isolated photovoltaic grid-connected inverter and switching control time sequence thereof
CN109039038A (en) Capacitor energy storage type single-phase rectifier secondary ripple wave suppressing method based on virtual impedance
CN108847775A (en) Novel electric power electric transformer topological structure
CN106887957A (en) A kind of hybrid distribution transformer of Multiple coil magnetic integrated-type
Indalkar et al. Comparison of AC-DC Converter Topologies Used for Battery Charging in Electric Vehicle
Sen et al. Three-phase medium voltage DC fast charger based on single-stage soft-switching topology
CN109149939A (en) For low-floor tramcar AuCT light-weight design method
CN108023411A (en) A kind of single-phase contactless power supply system with power factor emendation function
CN205847124U (en) A kind of switched inductors type mixes quasi-Z-source inverter
CN102832828A (en) Magnetic combined three-phase input AC (Alternating Current)/DC (Direct Current) full-bridge high frequency converter
CN110445227A (en) High and low frequency ripple current suppressing method in the vehicle-mounted single-phase charging system of electric car
CN109327147A (en) A kind of power regulation device of High Frequency Solid State induction heating power
Strothmann et al. Common-mode-free bidirectional three-phase PFC-rectifier for non-isolated EV charger
CN101234449A (en) Inversion submerged arc welding electric power main circuit topological structure
CN104541443B (en) Rectification circuit and method for nonequilibrium two-phase DC power networks

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant