CN106560991A - Pulse width modulation method for H-bridge cascading-type inverter - Google Patents
Pulse width modulation method for H-bridge cascading-type inverter Download PDFInfo
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- CN106560991A CN106560991A CN201610664729.8A CN201610664729A CN106560991A CN 106560991 A CN106560991 A CN 106560991A CN 201610664729 A CN201610664729 A CN 201610664729A CN 106560991 A CN106560991 A CN 106560991A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/483—Converters with outputs that each can have more than two voltages levels
- H02M7/49—Combination of the output voltage waveforms of a plurality of converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses a pulse width modulation method for an H-bridge cascading-type inverter, and the method comprises the following steps: setting a specific function optimization target with the minimum harmonic current, and a nonlinear constraint with the H-bridge power balance; solving an initial switching angle value of a corresponding modulation degree through employing a genetic algorithm; solving an optimal switching angle value through employing a nonlinear programming function Fmincon; carrying out the planning of switching angle values in a whole modulation ratio range, and carrying out the serialization of the switching angle values in an allowed specific function index. The method employs a multilevel synchronization optimization pulse width modulation method to effectively solve problems of energy quality at low switching frequency and the instantaneous power balance of an H-bridge module, and is successfully used in the field of AC transmission.
Description
Technical field
The present invention relates to a kind of modulator approach of multi-electrical level inverter, more particularly to a kind of H bridges cascaded inverter is same
Step optimization pulse duration modulation method.
Background technology
Traditional Multilevel modulation technology includes phase-shifting carrier wave PWM (Carrier phase-shifted pulse-width
Modulation, CPS-PWM), stacking PWM (Phase disposition pulse-width modulation, PD-PWM),
Multilevel space vector PWM (Space vector pulse-width modulation, SVPWM) and many level SHEPWM
(Selective harmonic elimination pulse-width modulation, SHEPWM) etc..
CPS-PWM can be automatically obtained the power equalization of H-bridge unit, but voltage utilization is relatively low.PD-PWM cannot be naturally real
Existing power equalization, needs the pulse train in each power model of half period interior circulation.It is inverse that many level SVPWMs are applied to many level
When becoming device, when output-voltage levels number is more than 5, voltage vector is selected and action time calculates all extremely complex.
Many level SHEPWM when each power model switch angle is calculated, simply with fundamental modulation ratio and specified Harmonics elimination
For constraints, do not consider that modular power is balanced.Staircase wave method as many level SHEPWM a kind of special circumstances,
Can be using active power equalization and cycle pulse power equalization method come balanced each module voltage stress and current stress.Wattful power
Rate equalization needs the phase relation for considering fundamental voltage and electric current, increases power equalization constraint equation to readjust switching angle
Degree.Cycle pulse power equalization method includes pulse interlacing method and pulse offsets method again, and pulse interlacing method is causing output voltage just
Half cycle and negative half period lose zero point symmetry, and the even-order harmonic of individual module output voltage is significantly increased;Pulse offsets Fa Keping
The voltage stress of weighing apparatus modules and devices switch loss, but the active power and reactive power of modules but phase not to the utmost
Together.
Synchronous fluorimetry pulsewidth modulation (Synchronous optimal pulse-width modulation, SOPWM) is needed
Specific function optimization aim is set, such as harmonic current virtual value minimum, efficiency optimization and torque pulsation is minimum, not exclusively
Inverter itself, but inverter and load are considered as a whole mathematical model, solved most by function minimization
Excellent switch angle.
SOPWM can efficiently solve the problems such as quality of power supply of low switching frequency, equilibrium of H-bridge unit instantaneous power;Due to
SOPWM existing correlative studys in two level, three-level inverter, and being applied to many level H-bridge cascade connection type inverters can increase
Switching angle computation complexity, therefore the achievement in research based on many level H-bridge cascade connection type inverters of SOPWM is actually rare.
The content of the invention
In order to overcome the shortcoming and defect of prior art, the purpose of the present invention is to meet the same of total harmonic current minimum
When, propose a kind of Synchronous fluorimetry pulse duration modulation method of the H bridge cascaded inverters of energy efficient balance unit instantaneous power.
The technical solution adopted for the present invention to solve the technical problems is:A kind of pulsewidth modulation of H bridges cascaded inverter
Method, comprises the following steps:
Step S10:According to control system performance requirement determine single H bridge inverters within 1/4 cycle switching angle number and
Modulation ratio m is interval;
Step S20:Set up Harmonic Current Distortion rate target extremal function and H bridge power equalizations fundamental voltage it is non-linear
Constraints;
Step S30:Asked by genetic algorithm in modulation ratio m interval according to the Nonlinear Constraints that step S20 is obtained
Solve the initial switch angle value of corresponding modulation degree;
Step S40:Initial switch angle value is obtained according to step S30, using the Non-Linear Programming function of Matlab
Fmincon solves optimized switching angle value;
Step S50:When reaching the setting cycle calculations number of times of step S30, step S40, all of harmonic current of comparison is abnormal
Variability, stores the optimized switching angle value of corresponding modulation ratio m;
Step S60:Switch angle value in Integrated comparative modulation ratio m interval, all discontinuous switch angle that will be solved
Value carries out continuous treatment;
Step S70:The switch angle value of serialization is stored in memory, is produced according to H bridge inverters control law
Pwm signal.
Further, described step S30 is comprised the following steps:
Step S301:Nonlinear Constraints are obtained according to step S20 and sets up initial optimization object function, determine switching angle
The border of angle value and linear inequality constraint condition;
Step S302:Setting initial population parameter, calculates single individual fitness value in population, is selected according to fitness
Parent individuality, gene information from parent population produces new son individual, by small probability disturbance to change population in individuality
Gene information and create the offspring of variation;
Step S303:When meeting optimization end condition, choice of modulation obtains corresponding initial switch angle value than m.
A kind of pulse duration modulation method of described H bridges cascaded inverter, its initial optimization object function is
Wherein N be H bridges cascade number, k be H bridges switching angle number within 1/4 cycle, specific gravity factor λ1、λ2More than 0, and N λ1+
λ2=1.
Further, described step S40 is comprised the following steps:
Step S401:Final optimization pass object function and nonlinear restriction equation are obtained according to step S20, it is determined that switch angle
The border of value and linear inequality constraint condition;
Step S402:Switch angle value is solved using the Non-Linear Programming function Fmincon in constrained optimization;
Step S403:When meeting optimization end condition, choice of modulation obtains corresponding optimized switching angle value than m.
A kind of pulse duration modulation method of described H bridges cascaded inverter, final optimization pass object function is
The nonlinear restriction equation is
The present invention compared with prior art, has the advantages that:
(1) modulator approach of the invention minimizes total harmonic current of H bridge cascaded inverters balanced with modular power
Combine, while total harmonic current is minimized, energy efficient balance modules power effectively improves output current ripple
Shape, reduces total Harmonic Current Distortion rate.
(2) SOPWM that uses of the present invention is for CPS-PWM, PD-PWM and SVPWM, when total Harmonic Current Distortion
When rate is identical, with lower switching frequency, can significantly reduce the switching loss of power device.
Description of the drawings
Fig. 1 is 2 H bridge cascaded inverter main circuit topological structures;
Fig. 2 is the calculation flow chart of the present invention;
Fig. 3 is the relation between inverter switching frequency and motor in synchrony frequency;
Fig. 4 is the relation of the switch angle that optimization is calculated when k is equal to 5 and modulation ratio;
Fig. 5 is the relation of switch angle when k is equal to 5 after continuity optimization and modulation ratio;
Fig. 6 is the relation of Harmonic Current Distortion rate and modulation ratio before and after serialization;
Fig. 7 is the relation that angle and modulation ratio are switched when k is equal to 4;
Fig. 8 is the relation that angle and modulation ratio are switched when k is equal to 3;
Fig. 9 is the relation of Harmonic Current Distortion rate and gamut internal modulation ratio;
Figure 10 is when devices switch frequency is that 300Hz, synchronous angular frequency are equal to 75Hz, using the electricity of SPWM modulator approaches
Pressure, electric current and torque profile figure;
Figure 11 is when devices switch frequency is that 300Hz, synchronous angular frequency are equal to 75Hz, using SOPWM modulator approaches
Voltage, electric current and torque profile figure.
Specific embodiment
The present invention is described in further detail with reference to the accompanying drawings and examples.
As shown in figure 1, considering from circuit topological structure and modulator approach complexity, five level are using more one kind
Many level topological structures, the present invention just by five-electrical level inverter driving asynchronous machine as a example by, other multi-electrical level inverter analysis classes
Seemingly.
The switch angle optimization computation flow process of H bridge cascaded inverter SOPWM methods is as shown in Fig. 2 including following step
Suddenly:
Step S10
Single H bridge inverters switching angle number and modulation ratio m area within 1/4 cycle are determined according to control system performance requirement
Between.If the maximum allowable operating frequency of switching device is fsmax, fundamental voltage frequency is f1, for single H bridge inverters were at 1/4 week
Switching angle number is in phase
Modulation ratio m meets with switching angle number k
If H bridge cascaded inverters IGBT allows peak frequency fsmaxFor 300Hz, rated output frequency fNFor 100Hz, then
Inverter switching frequency fsWith motor in synchrony frequency f1Design curve it is as shown in Figure 3:Can Setting pattern switch stagnant ring, to avoid
Modulating mode in frequency error factor point sweeping action, as shown by the dotted line in fig. 3.When synchronizing frequency f1During less than 50Hz, many level
Inverter can also obtain less Harmonic Current Distortion rate using asynchronous SPWM;When synchronizing frequency f1During more than 50Hz, adopt
Frequency-division section SOPWM.
Step S20
Set up the target extremal function of Harmonic Current Distortion rate and the fundamental voltage nonlinear restriction bar of H bridge power equalizations
Part.If UnFor the nth harmonic voltage magnitude of inverter output voltage, f1For fundamental frequency, LσFor asynchronous machine rotor leakage reactance it
With, the impact of negligible 3 multiple subharmonic voltage when loading with three phase electric machine, then a certain mutually total harmonic current of motor is effective
Value is represented by
When the H bridges of N levels cascade adopt 180 ° of square-wave frequency modulations, if DC bus-bar voltage is Udc, total harmonic current has
Valid value is represented by
IhWith Ih_sqEnter rower for base value to change, and be defined as Harmonic Current Distortion rate d.In order that total harmonic wave electricity
Stream is minimized, then had
Index d is related to the THD of electric machine phase current, can weigh the size of phase current THD, directly affects motor control
Energy.
In 1/4 periodic regime, switching the selection of angle value has the k free degree, and H bridge cascaded inverter output voltages are
Bring formula (6) into formula (5) Harmonic Current Distortion rate d can be obtained and be
By fundamental voltage U1To export fundamental voltage 4U during 180 ° of square-wave frequency modulationsdc/ π enters rower and changes for base value, and defines
For modulation ratio m.For balanced single H bridge inverters instantaneous output voltage, need to increase Nonlinear Constraints is
Step S30
Accordingly adjusted by genetic algorithm for solving in modulation ratio m interval according to the Nonlinear Constraints that step S20 is obtained
The initial switch angle value of system.Real work step using the switch angle optimizing of genetic algorithm is as follows.
Step S301:The target function type (7) for solving as needed and formula (8), setting up initial optimization object function is
Determine border and the linear inequality constraint condition of variable.If minimum pulse width is 50 μ s, according to the most scun for allowing
Wide degree switchs angle interval to determine
Then linear inequality constraints condition
Variable boundary condition
[LB UB]=[0.5 Δ α 0.5 (π-Δ α)] (12)
Step S302:Setting initial population parameter, calculates single individual fitness value in population, is selected according to fitness
Parent individuality, gene information from parent population produces new son individual, by small probability disturbance to change population in individuality
Gene information and create the offspring of variation;
Step S303:When meeting optimization end condition, choice of modulation obtains corresponding initial switch angle value than m;Initially
Optimization object function is
Wherein N be H bridges cascade number, k be H bridges switching angle number within 1/4 cycle, specific gravity factor λ1、λ2More than 0, and N λ1+
λ2=1.
Step S40
Initial switch angle value is obtained according to step S30, is solved most using the Non-Linear Programming function Fmincon of Matlab
Excellent switch angle value, comprises the following steps.
Step S401:Final optimization pass object function and nonlinear restriction equation are obtained according to step S20, it is determined that switch angle
The border of value and linear inequality constraint condition.Optimization object function is set to formula (7);The switch that initial point is obtained for genetic algorithm
Angle;Linear inequality constraint condition is set to formula (11);Variable boundary condition is set to formula (12);Nonlinear restriction equation is set to formula
(8)。
Step S402:Switch angle value is solved using the Non-Linear Programming function Fmincon in constrained optimization;
Step S403:When meeting optimization end condition, choice of modulation obtains corresponding optimized switching angle value than m;Finally
Optimization object function is
The nonlinear restriction equation is
Step S50
When reaching the setting cycle calculations number of times of step S30, step S40, all of Harmonic Current Distortion rate of comparison, storage
The optimized switching angle value of corresponding modulation ratio m, optimization is calculated when k is equal to 5 switch angle and relation such as Fig. 4 institutes of modulation ratio
Show.
Step S60
Switch angle value in Integrated comparative modulation ratio m interval, all discontinuous switch angle value for solving is connected
Continuousization process;When modulation ratio m occurs minor variations, switch angle changing value is less than as far as possible π/18, can reduce motor output
Electromagnetic torque pulsation size.The step of all discontinuous switch angle value for solving is carried out into continuous treatment is as follows:
Step S601:Again planning switch angle curve, angle value is switched as the initial of discontinuity point using continuity point
Value, in the case where allowing Harmonic Current Distortion rate d, plans as a whole the solution of all modulation ratios m.
Step S602:Solved using genetic algorithm optimizing, Fmincon function optimizations are calculated, re-optimization is all discontinuous
Point.The switch angle that continuity optimization is calculated when k is equal to 5 is as shown in Figure 5 with the relation of modulation ratio.
The serialization of switch angle sacrifices fractional harmonic current distortion rate index, Harmonic Current Distortion rate before and after serialization
With the relation of modulation ratio as shown in fig. 6, Harmonic Current Distortion rate d of the partial modulation than m even increased 100%.
Respectively as shown in Figure 7 and Figure 8, switch angle is substantially continuous for the relation of switch angle and modulation ratio when k is equal to 4 and 3,
Calculation procedure and k are equal to identical when 5.
The relation of Harmonic Current Distortion rate and gamut internal modulation ratio is humorous as shown in figure 9, when modulation ratio m is less than 0.93
Ripple current distortion rate d is less than 0.2, and the inhibition of harmonic current is preferable;When modulation ratio m is more than 0.93, Harmonic Current Distortion
Rate d moves closer to 180 ° of square-wave frequency modulations.
Step S70
The switch angle value of serialization is stored in memory, pwm signal is produced according to H bridge inverters control law.
When devices switch frequency is that 300Hz, synchronous angular frequency are equal to 75Hz, using the voltage of SPWM modulator approaches, electricity
Stream and torque profile figure are as shown in Figure 10;When devices switch frequency is that 300Hz, synchronous angular frequency are equal to 75Hz, using SOPWM
The voltage of modulator approach, electric current and torque profile figure are as shown in figure 11;Figure 10 and Figure 11 compare CPS-PWM and segmentation SOPWM
Voltage, electric current and torque profile.During low switching frequency, using Stator Current Harmonic aberration rate, the torque pulsation of segmentation SOPWM
Much smaller than CPS-PWM.Different from CPS-PWM, the integral multiple of IGBT switching frequencies always fundamental voltage frequency is segmented SOPWM
Part sideband harmonic wave is eliminated, while low-order harmonic can be suppressed, low-order harmonic electric current, electricity when can efficiently solve low switching frequency
The excessive problem of machine output torque pulsation.
Finally it should be noted that:Above example is most only to illustrate technical scheme rather than a limitation
Pipe has been described in detail with reference to above-described embodiment to the present invention, it will be understood by those skilled in the art that:Still can be with
The specific implementation method of the present invention is modified or equivalent, and without departing from any modification of spirit and scope of the invention
Or equivalent, it all should cover in the middle of scope of the presently claimed invention.
Claims (6)
1. a kind of pulse duration modulation method of H bridges cascaded inverter, it is characterised in that comprise the following steps:
Step S10:Single H bridge inverters switching angle number and modulation within 1/4 cycle are determined according to control system performance requirement
It is more interval than m;
Step S20:Set up the target extremal function of Harmonic Current Distortion rate and the fundamental voltage nonlinear restriction of H bridge power equalizations
Condition;
Step S30:Pass through genetic algorithm for solving phase in modulation ratio m interval according to the Nonlinear Constraints that step S20 is obtained
Answer the initial switch angle value of modulation degree;
Step S40:Initial switch angle value is obtained according to step S30, is asked using the Non-Linear Programming function Fmincon of Matlab
Solution optimized switching angle value;
Step S50:When reaching the setting cycle calculations number of times of step S30, step S40, all of Harmonic Current Distortion rate of comparison,
Store the optimized switching angle value of corresponding modulation ratio m;
Step S60:Switch angle value in Integrated comparative modulation ratio m interval, all discontinuous switch angle value for solving is entered
Row continuous treatment;
Step S70:The switch angle value of serialization is stored in memory, PWM letters are produced according to H bridge inverters control law
Number.
2. the pulse duration modulation method of a kind of H bridges cascaded inverter according to claim 1, it is characterised in that described
Step S30 is comprised the following steps:
Step S301:Nonlinear Constraints are obtained according to step S20 and sets up initial optimization object function, it is determined that switch angle value
Border and linear inequality constraint condition;
Step S302:Setting initial population parameter, calculates single individual fitness value in population, and according to fitness parent is selected
Individuality, gene information from parent population produces new son individual, by small probability disturbance to change population in genes of individuals
Information and create the offspring of variation;
Step S303:When meeting optimization end condition, choice of modulation obtains corresponding initial switch angle value than m.
3. the pulse duration modulation method of a kind of H bridges cascaded inverter according to claim 1, it is characterised in that described
Step S40 is comprised the following steps:
Step S401:Final optimization pass object function and nonlinear restriction equation are obtained according to step S20, it is determined that switch angle value
Border and linear inequality constraint condition;
Step S402:Switch angle value is solved using the Non-Linear Programming function Fmincon in constrained optimization;
Step S403:When meeting optimization end condition, choice of modulation obtains corresponding optimized switching angle value than m.
4. the pulse duration modulation method of a kind of H bridges cascaded inverter according to claim 1, it is characterised in that described
Step S60 is comprised the following steps:
Step S601:Again planning switch angle curve, angle value is switched as the initial value of discontinuity point using continuity point;
Step S602:Solved using genetic algorithm optimizing, Fmincon function optimizations are calculated, all discontinuity poinies of re-optimization.
5. the pulse duration modulation method of a kind of H bridges cascaded inverter according to claim 2, it is characterised in that it is described just
Beginning optimization object function is
Wherein N is that H bridges cascade number, and k is H bridges switching angle number, specific gravity factor within 1/4 cycleλ 1、λ 2More than 0, and Nλ 1+λ 2=1。
6. the pulse duration modulation method of a kind of H bridges cascaded inverter according to claim 3, it is characterised in that it is described most
Whole optimization object function is
The nonlinear restriction equation is
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CN109104112A (en) * | 2018-08-13 | 2018-12-28 | 武汉船用电力推进装置研究所(中国船舶重工集团公司第七二研究所) | A kind of pulse duration modulation method of three-phase NPC-H bridge five-electrical level inverter |
CN111464064A (en) * | 2020-05-09 | 2020-07-28 | 湖南人文科技学院 | Multilevel DC link inverter and harmonic suppression method thereof |
CN114389515A (en) * | 2022-03-24 | 2022-04-22 | 佛山仙湖实验室 | Method, system, equipment and medium for suppressing harmonic current of permanent magnet synchronous motor |
CN114996841A (en) * | 2022-05-26 | 2022-09-02 | 哈尔滨工业大学 | Optimal coplanarity transfer search method based on tangent initial value |
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Cited By (7)
Publication number | Priority date | Publication date | Assignee | Title |
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CN109104112A (en) * | 2018-08-13 | 2018-12-28 | 武汉船用电力推进装置研究所(中国船舶重工集团公司第七二研究所) | A kind of pulse duration modulation method of three-phase NPC-H bridge five-electrical level inverter |
CN111464064A (en) * | 2020-05-09 | 2020-07-28 | 湖南人文科技学院 | Multilevel DC link inverter and harmonic suppression method thereof |
CN111464064B (en) * | 2020-05-09 | 2021-06-04 | 湖南人文科技学院 | Harmonic suppression method of multilevel DC link inverter |
CN114389515A (en) * | 2022-03-24 | 2022-04-22 | 佛山仙湖实验室 | Method, system, equipment and medium for suppressing harmonic current of permanent magnet synchronous motor |
CN114389515B (en) * | 2022-03-24 | 2022-07-05 | 佛山仙湖实验室 | Method, system, equipment and medium for suppressing harmonic current of permanent magnet synchronous motor |
CN114996841A (en) * | 2022-05-26 | 2022-09-02 | 哈尔滨工业大学 | Optimal coplanarity transfer search method based on tangent initial value |
CN114996841B (en) * | 2022-05-26 | 2023-04-07 | 哈尔滨工业大学 | Optimal coplanarity transfer search method based on tangent initial value |
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