CN103684024B - The inverter of a kind of times of streaming difference output - Google Patents

The inverter of a kind of times of streaming difference output Download PDF

Info

Publication number
CN103684024B
CN103684024B CN201310590548.1A CN201310590548A CN103684024B CN 103684024 B CN103684024 B CN 103684024B CN 201310590548 A CN201310590548 A CN 201310590548A CN 103684024 B CN103684024 B CN 103684024B
Authority
CN
China
Prior art keywords
switching tube
inverter
former limit
filter inductance
output
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN201310590548.1A
Other languages
Chinese (zh)
Other versions
CN103684024A (en
Inventor
邓焰
吕自波
彭浩
李楚杉
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Zhejiang University ZJU
Original Assignee
Zhejiang University ZJU
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Zhejiang University ZJU filed Critical Zhejiang University ZJU
Priority to CN201310590548.1A priority Critical patent/CN103684024B/en
Publication of CN103684024A publication Critical patent/CN103684024A/en
Application granted granted Critical
Publication of CN103684024B publication Critical patent/CN103684024B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Abstract

The invention discloses the inverter of a kind of times of streaming difference output, comprise two isolated form DC-DC conversion circuit; The former limit of DC-DC conversion circuit is full-bridge circuit structure, and secondary is current-doubling rectifier structure; The output of two DC-DC conversion circuit secondary is connected to load two ends respectively to form differential configuration.Duty-cycle loss phenomenon is not had during inverter of the present invention work, thus the voltage waveform distortion fundamentally eliminating dead band and bring; Inverter adopts the structure of difference output, eliminates the wave distortion that the non-ideal characteristic due to side circuit brings further, also has very high common mode disturbances rejection ability simultaneously, thus obtain the extremely low output voltage of irregularity of wave form.In addition, inverter of the present invention exports between input mutually isolated with high frequency transformer, reduces the electromagnetic interference of input to load.

Description

The inverter of a kind of times of streaming difference output
Technical field
The invention belongs to electric and electronic technical field, be specifically related to the inverter of a kind of times of streaming difference output.
Background technology
Along with the progress of modern science and technology, there is increasing precision instrument and equipment in all trades and professions, mechanical arm system (being commonly called as Leonardo da Vinci's operating robot) as other in bed used on clinical medicine, wafer fab chip production line equipment, and various precision processing machine.Precision instrument and equipment proposes very high requirement to power supply, not only requires that supply power voltage is stable, frequency departure is little, irregularity of wave form is low, also requires that the electromagnetic interference of power supply unit to instrument is little simultaneously.Therefore, the power supply of precision instrument and equipment directly can not adopt civil power, and needs custom-designed reliable and stable and irregularity of wave form meets the requirements of inverter.
On the other hand, along with growth in the living standard, high-quality stereo set is more and more common in the life of people.In stereo set, audio power amplifying circuit is crucial part.High quality audio power amplifier not only wants the distortion factor little, and audio-frequency noise is low, and requires that frequency response bandwidth scope is large, proposes demand to bandwidth, circuit that output waveform aberration rate is low.The sonar set similarly detecting under water and be widely used in military field.Active sonar sends the underwater sound signal of certain frequency by underwater acoustic transducer and detects echo and carry out detecting underwater object, and underwater acoustic transducer requires that the irregularity of wave form of power supply is extremely low, proposes severe challenge to traditional variable frequency power supply.
Traditional bridge-type inverter structure is simple, technology maturation, is widely used in conventional ac power supply apparatus.But in the above-mentioned application scenario needing high accuracy inverter, bridge-type inverter encounters the difficulty being difficult to overcome.Bridge inverter main circuit leading directly to operationally in order to avoid brachium pontis, must add Dead Time between the switching signal of upper and lower switching tube.The introducing of Dead Time can cause exporting fundamental voltage and reduce, and low-order harmonic voltage increases, and wave distortion is serious.In order to solve the wave distortion problem brought in dead band, Seon-Hwan.HandK.Jang-Mok is DeadTimeCompensationMethodforVoltage-FedPWMInverter.Ener gyConversion(IEEETransactionson at title, 2010.25 (1): propose in document p.1-10.) and add dead area compensation mechanism in the controlling, but this way needs to detect output current, by judging that the polarity of electric current decides the increase and decrease of duty ratio.And be difficult to accomplish accurately to the detection of current polarity near current zero-crossing point in reality.
Lihua.CandZ.P.Fang is Dead-TimeEliminationforVoltageSourceInverters.PowerElect ronics(IEEETransactionson at title, 2008.23 (2): in document p.574-580), propose the control strategy adopted without Dead Time, leading directly in order to avoid brachium pontis in this control strategy, need the on off state judging switching tube accurately, in practical application, generally judged the on off state of switching tube by detection filter inductive current or the anti-and conducting state of diode of switching tube; But because inductive current exists ripple, add the impact of various disturbing factor, make the validity of method have a greatly reduced quality, the reliability of device also reduces greatly.In a word, existing various scheme, owing to needing to detect accurately some variable in circuit, is thus difficult to apply in actual device.
In addition, traditional bridge-type inverter is a kind of structure of non-isolation type, and during work, output is easy to the impact of the electromagnetic interference be subject to from input; And switching tube is difficult to realize Sofe Switch, which has limited circuit realiration high frequency.
Summary of the invention
For the above-mentioned technical problem existing for prior art, the present invention proposes the inverter of a kind of times of streaming difference output, this inverter at work Dead Time can not cause duty-cycle loss, thus fundamentally solves the difficulty that conventional inverter runs into; Simultaneously because it adopts the structure of difference output, therefore, it is possible to eliminate the wave distortion that the non-ideal characteristic due to side circuit brings further, also there is very high common mode disturbances rejection ability simultaneously, thus obtain the extremely low output voltage of irregularity of wave form.
An inverter for times streaming difference output, be made up of two electronic circuits, described electronic circuit is isolated form DC-DC conversion circuit; The former limit of described DC-DC conversion circuit is full-bridge circuit structure, and secondary is current-doubling rectifier structure;
The output of two electronic circuit secondary is connected to inverter load two ends respectively to form difference output structure;
Described electronic circuit is used for VD DC input voitage be transformed to alternating current component, and two groups of VD that two electronic circuits are corresponding are made difference and obtained ac output voltage at inverter load two ends.The initial phase of the alternating current component in two groups of VD independently controls respectively.
Preferably, the former limit of two electronic circuits shares a brachium pontis; This not only reduces two power switch pipes, former limit circuit is simplified, and be conducive to the Sofe Switch that inverter realizes all switching tubes of former limit circuit.
The former limit of described electronic circuit comprises a former limit winding and two brachium pontis in parallel, and each brachium pontis is the anti-and switching tube S of diodes by two bands 1~ S 2be composed in series; The Same Name of Ends of former limit winding is connected with the intermediate node of a wherein brachium pontis, and different name end is connected with the intermediate node of another brachium pontis.
Preferably, the either end of described former limit winding is connected with the intermediate node of corresponding brachium pontis by capacitance; The magnetic biasing problem of high frequency transformer can be improved, the decrease speed of isolating transformer leakage inductance electric current in circuit commutation course greatly can be accelerated under the prerequisite not changing circuit operating pattern, reduce the requirement to isolating transformer leakage inductance, thus reduce the technological requirement of isolating transformer.
Save the capacitance on the former limit of described electronic circuit, the occasion that inverter can be made to be applicable to the very high and transformer magnetic biasing problem of transformer manufacture craft obtained solving very well; Save capacitance, better output waveform can be obtained.
Preferably, two switching tube S 1~ S 2source electrode be all parallel with buffer capacitor with drain electrode two ends, described buffer capacitor is the parasitic capacitance of switching tube inside or is an external electric capacity additional on the basis of parasitic capacitance; This buffer capacitor is conducive to switching tube and realizes Sofe Switch, avoids the various electromagnetic interference problems because switching tube hard switching brings.
Described electronic circuit secondary comprises the switching tube S of two anti-also diodes of band 3~ S 4, two filter inductance L 1~ L 2, a vice-side winding and a filter capacitor C o1; Wherein: filter inductance L 1one end and filter inductance L 2one end and filter capacitor C o1one end be connected in described output, filter inductance L 1the other end and the different name end of vice-side winding and switching tube S 3drain electrode be connected, filter inductance L 2the other end and the Same Name of Ends of vice-side winding and switching tube S 4drain electrode be connected, filter capacitor C o1the other end and switching tube S 3source electrode and switching tube S 4source electrode be connected and ground connection, two switching tube S 3~ S 4grid all receive the control signal that external control circuit provides.
According to actual conditions, described inverter load two ends are parallel with filter capacitor C o3; Filter capacitor C o3under being operated in exchange status, coordinate the filter capacitor C of two DC-DC conversion circuit secondary o1work can obtain better output waveform.
As another embodiment: described electronic circuit secondary comprises the switching tube S of two anti-also diodes of band 3~ S 4, two filter inductance L 1~ L 2with a vice-side winding; Wherein: filter inductance L 1one end and filter inductance L 2one end be connected in described output, filter inductance L 1the other end and the different name end of vice-side winding and switching tube S 3drain electrode be connected, filter inductance L 2the other end and the Same Name of Ends of vice-side winding and switching tube S 4drain electrode be connected, switching tube S 3source electrode and switching tube S 4source electrode be connected and ground connection, two switching tube S 3~ S 4grid all receive the control signal that external control circuit provides, described inverter load two ends are parallel with filter capacitor C o3.This secondary circuit topology is simplified, and decreases filter capacitor use amount, can improve the reliability of device.
Inverter hinge structure of the present invention has the following advantages:
(1) there is not duty-cycle loss in the course of the work in inverter of the present invention, do not need to take any dead area compensation strategy just can obtain the ultralow interchange output waveform of an aberration rate.
(2) power switch pipe in inverter of the present invention is easy to realize Sofe Switch, avoids the various electromagnetic interference problems because switching tube hard switching brings, is easy to the high frequency of realizing circuit, is conducive to the raising of circuit efficiency simultaneously.
(3) the former secondary circuit of inverter of the present invention is mutually isolated by high frequency transformer, inhibits input to the electromagnetic interference of output.
(4) inverter of the present invention is based upon on ripe technical foundation, and electronic circuit is traditional DC-DC circuit, and former limit is full bridge structure, and secondary is double current rectify structure; Circuit adopts traditional phase-shifting full-bridge PWM method, and the method principle is simple, technology maturation.
Inverter of the present invention can be used for powering to precision instrument, or is used as the power amplifier of high-quality sound equipment, can also be used to power to the underwater acoustic transducer of active sonar.
Accompanying drawing explanation
Fig. 1 is the structural representation of the first execution mode of inverter of the present invention.
Fig. 2 is the structural representation of inverter the second execution mode of the present invention.
Fig. 3 is the structural representation of the third execution mode of inverter of the present invention.
Fig. 4 is the structural representation of inverter of the present invention 4th kind of execution mode.
Fig. 5 is the structural representation of inverter of the present invention 5th kind of execution mode.
Fig. 6 is the structural representation of inverter of the present invention 6th kind of execution mode.
Fig. 7 is the waveform schematic diagram of inverter output voltage of the present invention.
Fig. 8 is that the THD of inverter output voltage waveform of the present invention analyzes schematic diagram.
Embodiment
In order to more specifically describe the present invention, below in conjunction with the drawings and the specific embodiments, technical scheme of the present invention and relative theory thereof are described in detail.
An inverter for times streaming difference output, comprises two isolated form DC-DC conversion circuit; The former limit of DC-DC conversion circuit is full-bridge circuit structure, and secondary is current-doubling rectifier structure; The former limit of two DC-DC conversion circuit shares a brachium pontis, and the output of two DC-DC conversion circuit secondary is connected to load two ends respectively to form differential configuration.
As shown in Figure 1, former limit circuit comprises:
1) the first former limit branch road in parallel with input power, by band anti-paralleled diode D s1the first power switch tube S 1, band anti-paralleled diode D s2the second power switch tube S 2, the first buffer capacitor C s1, the second buffer capacitor C s2composition; Wherein be with anti-paralleled diode D s1the first power switch tube S 1drain electrode be connected with the positive pole of power supply, band anti-paralleled diode D s1the first power switch tube S 1source electrode and band anti-paralleled diode D s2the second power switch tube S 2drain electrode be connected in A point, band anti-paralleled diode D s2the second power switch tube S 2source electrode be connected with the negative pole of power supply, the first buffer capacitor C s1two ends respectively with band anti-paralleled diode D s1the first power switch tube S 1drain electrode be connected with source electrode, the second buffer capacitor C s2two ends respectively with band anti-paralleled diode D s2the second power switch tube S 2drain electrode be connected with source electrode;
2) the second former limit branch road in parallel with input power, by band anti-paralleled diode D s3the 3rd power switch tube S 3, band anti-paralleled diode D s4the 4th power switch tube S 4, the 3rd buffer capacitor C s3, the 4th buffer capacitor C s4composition; Wherein be with anti-paralleled diode D s4the 4th power switch tube S 4drain electrode be connected with the positive pole of power supply, band anti-paralleled diode D s4the 4th power switch tube S 4source electrode and band anti-paralleled diode D s3the 3rd power switch tube S 3drain electrode be connected in B point, band anti-paralleled diode D s3the 3rd power switch tube S 3source electrode be connected with the negative pole of power supply, the 4th buffer capacitor C s4two ends respectively with band anti-paralleled diode D s4the 4th power switch tube S 4drain electrode be connected with source electrode, the 3rd buffer capacitor C s3two ends respectively with band anti-paralleled diode D s3the 3rd power switch tube S 3drain electrode be connected with source electrode;
3) the 3rd former limit branch road in parallel with input power, by band anti-paralleled diode D s5the 5th power switch tube S 5, band anti-paralleled diode D s6the 6th power switch tube S 6, the 5th buffer capacitor C s5, the 6th buffer capacitor C s6composition; Wherein be with anti-paralleled diode D s5the 5th power switch tube S 5drain electrode be connected with the positive pole of power supply, band anti-paralleled diode D s5the 5th power switch tube S 5source electrode and band anti-paralleled diode D s6the 6th power switch tube S 6drain electrode be connected in C point, band anti-paralleled diode D s6the 6th power switch tube S 6source electrode be connected with the negative pole of power supply, the 5th buffer capacitor C s5two ends respectively with band anti-paralleled diode D s5the 5th power switch tube S 5drain electrode be connected with source electrode, the 6th buffer capacitor C s6two ends respectively with band anti-paralleled diode D s6the 6th power switch tube S 6drain electrode be connected with source electrode;
4) the first isolating transformer T 1former limit winding N 11, the first capacitance C p1; Wherein the first isolating transformer T 1former limit winding N 11same Name of Ends and band anti-paralleled diode D s1the first power switch tube S 1source electrode and band anti-paralleled diode D s2the second power switch tube S 2drain electrode be connected to A point altogether, the first isolating transformer T 1former limit winding N 11the other end and the first capacitance C p1one end be connected, the first capacitance C p1the other end and band anti-paralleled diode D s4the 4th power switch tube S 4source electrode and band anti-paralleled diode D s3the 3rd power switch tube S 3drain electrode be connected to B point altogether;
5) the second isolating transformer T 2former limit winding N 21, the second capacitance C p2; Wherein the second isolating transformer T 2former limit winding N 21same Name of Ends and band anti-paralleled diode D s4the 4th power switch tube S 4source electrode and band anti-paralleled diode D s3the 3rd power switch tube S 3drain electrode be connected to B point altogether, the second isolating transformer T 2former limit winding N 21the other end and the second capacitance C p2one end be connected, the second capacitance C p2the other end and band anti-paralleled diode D s5the 5th power switch tube S 5source electrode and band anti-paralleled diode D s6the 6th power switch tube S 6drain electrode be connected to " C " point altogether;
Secondary circuit comprises:
1) the first secondary branch road between output port anode D and ground is connected across, by band anti-paralleled diode D s7the 7th power switch tube S 7, the second filter inductance L 2composition; Wherein the second filter inductance L 2one end be connected with output port anode D, the second filter inductance L 2the other end and band anti-paralleled diode D s7the 7th power switch tube S 7drain electrode be connected, band anti-paralleled diode D s7the 7th power switch tube S 7source electrode with ground connect;
2) the second secondary branch road between output port anode " D " and ground is connected across, by band anti-paralleled diode D s8the 8th power switch tube S 8, the first filter inductance L 1composition; Wherein the first filter inductance L 1one end be connected with output port anode D, the first filter inductance L 1the other end and band anti-paralleled diode D s8the 8th power switch tube S 8drain electrode be connected, band anti-paralleled diode D s8the 8th power switch tube S 8source electrode with ground connect;
3) the 3rd secondary branch road between output port negative terminal E and ground is connected across, by band anti-paralleled diode D s9the 9th power switch tube S 9, the 4th filter inductance L 4composition; Wherein the 4th filter inductance L 4one end be connected with output port negative terminal E, the 4th filter inductance L 4the other end and band anti-paralleled diode D s9the 9th power switch tube S 9drain electrode be connected, band anti-paralleled diode D s9the 9th power switch tube S 9source electrode with ground connect;
4) the 4th secondary branch road between output port negative terminal E and ground is connected across, by band anti-paralleled diode D s10the tenth power switch tube S 10, the 3rd filter inductance L 3composition; Wherein the 3rd filter inductance L 3one end be connected with output port negative terminal E, the 3rd filter inductance L 3the other end and band anti-paralleled diode D s10the tenth power switch tube S 10drain electrode be connected, band anti-paralleled diode D s10the tenth power switch tube S 10source electrode with ground connect;
5) the first isolating transformer T 1vice-side winding N 12, the second isolating transformer T 2vice-side winding N 22; Wherein the first isolating transformer T 1vice-side winding N 12different name end and band anti-paralleled diode D s7the 7th power switch tube S 7drain electrode be connected, the first isolating transformer T 1vice-side winding N 12same Name of Ends and band anti-paralleled diode D s8the 8th power switch tube S 8drain electrode be connected; Second isolating transformer T 2vice-side winding N 22same Name of Ends and band anti-paralleled diode D s9the 9th power switch tube S 9drain electrode be connected, the second isolating transformer T 2vice-side winding N 22different name end and band anti-paralleled diode D s10the tenth power switch tube S 10drain electrode be connected;
6) the first filter capacitor C o1, the second filter capacitor C o2; Wherein the first filter capacitor C o1be connected across between output port anode " D " and ground, the second filter capacitor C o2be connected across between the negative terminal " E " of output port and ground.
First buffer capacitor C in Fig. 1 s1, the second buffer capacitor C s2, the 3rd buffer capacitor C s3, the 4th buffer capacitor C s4, the 5th buffer capacitor C s5, the 6th buffer capacitor C s6be made up of independent electric capacity, or by the anti-also diode D of band s1the first power switch tube S 1parasitic capacitance between drain electrode and source electrode, be with instead also diode D s2the second power switch tube S 2parasitic capacitance between drain electrode and source electrode, be with instead also diode D s3the 3rd power switch tube S 3parasitic capacitance between drain electrode and source electrode, be with instead also diode D s4the 4th power switch tube S 4parasitic capacitance between drain electrode and source electrode, be with instead also diode D s5the 5th power switch tube S 5parasitic capacitance between drain electrode and source electrode, be with instead also diode D s6the 6th power switch tube S 6parasitic capacitance between drain electrode and source electrode is formed.
As another kind of execution mode, as shown in Figure 2, the former limit circuit of inverter can simplify.The first capacitance C in Fig. 1 p1with the second capacitance C p2can be removed.The secondary circuit of inverter remains unchanged simultaneously.
As another kind of execution mode, as shown in Figure 3, the secondary circuit of inverter is compared with the first execution mode shown in Fig. 1, has met the 3rd filter capacitor C at D, E two ends of output port o3, former limit circuit is identical with the former limit circuit shown in Fig. 1.
As another kind of execution mode, as shown in Figure 4, the secondary circuit of inverter is compared with the second execution mode shown in Fig. 2, has met the 3rd filter capacitor C at D, E two ends of output port o3, former limit circuit is identical with the former limit circuit shown in Fig. 2.
As another kind of execution mode, as shown in Figure 5, the secondary circuit of inverter is compared with the first execution mode shown in Fig. 1, eliminates the first filter capacitor C o1, the second filter capacitor C o2, meanwhile met the 3rd filter capacitor C at D, E two ends of output port o3, former limit circuit is identical with the former limit circuit shown in Fig. 1.
As another kind of execution mode, as shown in Figure 6, the secondary circuit of inverter is compared with the second execution mode shown in Fig. 2, eliminates the first filter capacitor C o1, the second filter capacitor C o2, meanwhile met the 3rd filter capacitor C at D, E two ends of output port o3, former limit circuit is identical with the former limit circuit shown in Fig. 2.
In figure, band anti-paralleled diode D s1the first power switch tube S 1, band anti-paralleled diode D s2the second power switch tube S 2, band anti-paralleled diode D s3the 3rd power switch tube S 3, band anti-paralleled diode D s4the 4th power switch tube S 4, band anti-paralleled diode D s5the 5th power switch tube S 5, band anti-paralleled diode D s6the 6th power switch tube S 6, band anti-paralleled diode D s7the 7th power switch tube S 7, band anti-paralleled diode D s8the 8th power switch tube S 8, band anti-paralleled diode D s9the 9th power switch tube S 9, band anti-paralleled diode D s10the tenth power switch tube S 10common MOSFET all can be adopted to realize.
Inverter of the present invention adopts traditional phase-shifting full-bridge PWM method, and secondary circuit adopts the structure of difference output, and former secondary circuit is mutually isolated by high-frequency isolation transformer.For the first embodiment shown in Fig. 1, output voltage is made to be V in, the duty ratio of two phase-shifting full-bridge DC-DC circuit is respectively d 1, d 2, transformer turns ratio is N.Then according to the feature of times streaming DC-DC circuit, the voltage expression can releasing D, E 2 is respectively v D = d 1 V in 2 N , v E = d 2 V in 2 N , So output voltage v o = v D - v E = ( d 1 - d 2 ) V in 2 N . Work as d 1, d 2by a DC quantity (D), (amplitude is A, and angular frequency is ω, and initial phase angle is respectively with of ac , ) superimposed formation and direct current biasing equal time, namely then can obtain this output is an amplitude frequency is initial phase angle is alternating voltage.Because circuit working process does not produce duty-cycle loss, therefore this ac output voltage has high waveform quality.
Fig. 7 is the simulation waveform of the first embodiment of inverter shown in Fig. 1, ordinate v in figure orepresent output voltage, unit volt (V), abscissa representing time, unit microsecond (ms), output voltage frequency is 1000 hertz (Hz).The analysis result of the total harmonic distortion factor (THD) that Fig. 8 is the output voltage waveforms shown in Fig. 7.Wherein ordinate represents voltage magnitude, unit volt (V), and abscissa is harmonic number.F 1represent frequency, v 1mtable is fundamental voltage amplitude.This inverter output waveforms aberration rate extremely low (THD=0.09) can be found out from the analysis result of Fig. 7 and Fig. 8, demonstrate feasibility and the advantage of technical solution of the present invention.

Claims (1)

1. an inverter for times streaming difference output, is characterized in that: be made up of two electronic circuits, and described electronic circuit is isolated form DC-DC conversion circuit; The former limit of described DC-DC conversion circuit is full-bridge circuit structure, and secondary is current-doubling rectifier structure;
The output of two electronic circuit secondary is connected to inverter load two ends respectively to form difference output structure;
Described electronic circuit is used for VD DC input voitage be transformed to alternating current component, and two groups of VD that two electronic circuits are corresponding are made difference and obtained ac output voltage at inverter load two ends;
One of them electronic circuit secondary comprises the switching tube S of two anti-also diodes of band 7~ S 8, two filter inductance L 1~ L 2, a vice-side winding N 12with a filter capacitor C o1; Wherein: filter inductance L 1one end and filter inductance L 2one end and filter capacitor C o1one end be connected in the output of this electronic circuit secondary, filter inductance L 1the other end and vice-side winding N 12same Name of Ends and switching tube S 8drain electrode be connected, filter inductance L 2the other end and vice-side winding N 12different name end and switching tube S 7drain electrode be connected, filter capacitor C o1the other end and switching tube S 7source electrode and switching tube S 8source electrode be connected and ground connection, two switching tube S 7~ S 8grid all receive the control signal that external control circuit provides;
Another electronic circuit secondary comprises the switching tube S of two anti-also diodes of band 9~ S 10, two filter inductance L 3~ L 4, a vice-side winding N 22with a filter capacitor C o2; Wherein: filter inductance L 3one end and filter inductance L 4one end and filter capacitor C o2one end be connected in the output of this electronic circuit secondary, filter inductance L 3the other end and vice-side winding N 22different name end and switching tube S 10drain electrode be connected, filter inductance L 4the other end and vice-side winding N 22same Name of Ends and switching tube S 9drain electrode be connected, filter capacitor C o2the other end and switching tube S 9source electrode and switching tube S 10source electrode be connected and ground connection, two switching tube S 9~ S 10grid all receive the control signal that external control circuit provides;
The former limit of two electronic circuits shares a brachium pontis; Described inverter load two ends are parallel with filter capacitor C o3;
The former limit of described electronic circuit comprises a former limit winding and two brachium pontis in parallel, and by two bands, the anti-and switching tube of diodes is composed in series each brachium pontis; The Same Name of Ends of former limit winding is connected with the intermediate node of a wherein brachium pontis, and different name end is connected with the intermediate node of another brachium pontis; The either end of described former limit winding is connected with the intermediate node of corresponding brachium pontis by capacitance; Switching tube source electrode in brachium pontis is parallel with buffer capacitor with drain electrode two ends, and described buffer capacitor is the parasitic capacitance of switching tube inside or is an external electric capacity additional on the basis of parasitic capacitance.
CN201310590548.1A 2013-11-21 2013-11-21 The inverter of a kind of times of streaming difference output Active CN103684024B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN201310590548.1A CN103684024B (en) 2013-11-21 2013-11-21 The inverter of a kind of times of streaming difference output

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN201310590548.1A CN103684024B (en) 2013-11-21 2013-11-21 The inverter of a kind of times of streaming difference output

Publications (2)

Publication Number Publication Date
CN103684024A CN103684024A (en) 2014-03-26
CN103684024B true CN103684024B (en) 2016-04-27

Family

ID=50320580

Family Applications (1)

Application Number Title Priority Date Filing Date
CN201310590548.1A Active CN103684024B (en) 2013-11-21 2013-11-21 The inverter of a kind of times of streaming difference output

Country Status (1)

Country Link
CN (1) CN103684024B (en)

Families Citing this family (3)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US9577852B2 (en) * 2014-11-03 2017-02-21 Infineon Technologies Ag Common-mode suppressor based on differential transmission line
CN108429466B (en) * 2018-04-12 2019-10-18 浙江大学 A kind of three road output DC-DC converter of isolation hybrid modulation based on three-phase LLC resonance circuit and phase whole-bridging circuit
CN110572039A (en) * 2019-09-17 2019-12-13 汕头大学 Novel full-bridge direct-current converter based on current-doubling rectifier

Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101414791A (en) * 2008-12-02 2009-04-22 福州大学 Differential decompression DC chopper type high-frequency chain inverter

Family Cites Families (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN2385469Y (en) * 1999-08-04 2000-06-28 深圳永达辉科技有限公司 Power supply device for phase-shift resonance switch
US9379640B2 (en) * 2011-06-23 2016-06-28 The Board Of Trustees Of The University Of Illinois Scalable single-stage differential power converter

Patent Citations (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101414791A (en) * 2008-12-02 2009-04-22 福州大学 Differential decompression DC chopper type high-frequency chain inverter

Also Published As

Publication number Publication date
CN103684024A (en) 2014-03-26

Similar Documents

Publication Publication Date Title
CN109742968B (en) Diode clamping hybrid three-level double-active full-bridge converter and control method thereof
CN108258909A (en) Resonant transform circuit and its control method
CN103684024B (en) The inverter of a kind of times of streaming difference output
CN102624246B (en) Single-ended forward parallel push-pull type high-power converter
CN102231600A (en) Novel full-bridge soft switch circuit applied to arc welding inverter power supply
CN112202322B (en) Method for inhibiting secondary ripple current based on equivalent zero impedance of active negative capacitor
CN112731829A (en) Dynamic matching network of medical ultrasonic power supply and matching method thereof
CN102136804A (en) Novel Z source welding power source system
CN104638970A (en) Single-phase high-frequency inverter based on SCC-LCL-T resonant network
CN103683951B (en) A kind of inverter of full wave type difference output
CN103825477A (en) Three-phase single tube DCM Boost PFC converter
CN103280955B (en) The DC side harmonics of double reverse-stars type thyristor rectifier system suppresses System and method for
CN205490225U (en) Two -way ACDC circuit of high -frequency chopper isolated form
CN103916036A (en) Buck high-frequency isolation type five-level inverter
CN203761292U (en) High-frequency isolation type five-level inverter
CN104796027B (en) Voltage balance circuit and three-phase inverter
CN105006980B (en) The three level NPC current transformer PWM control strategies overlapped based on carrier wave
CN103856089A (en) High-frequency isolation-type five-level inverter
CN104539177B (en) Synchronous rectification drive circuit and synchronous rectification method of switching power supply
CN106026673A (en) Wide-scope input LLC resonance converter with high-voltage gain
CN104092396B (en) A kind of double Boost inverter of single inductance and control method thereof
CN102497104B (en) Resonant transformation circuit applied to medical equipment and provided with synchronous rectification control
CN104037769A (en) Parameter design method for single-phase PAPF and output LCL filter
CN107124105A (en) Improve isolated form three-level PFC converter PF control system and method
CN104184323A (en) Bidirectional DC/DC converter circuit

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
C10 Entry into substantive examination
SE01 Entry into force of request for substantive examination
C14 Grant of patent or utility model
GR01 Patent grant