CN102969885B - Without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector and modulator approach - Google Patents

Without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector and modulator approach Download PDF

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CN102969885B
CN102969885B CN201210429575.6A CN201210429575A CN102969885B CN 102969885 B CN102969885 B CN 102969885B CN 201210429575 A CN201210429575 A CN 201210429575A CN 102969885 B CN102969885 B CN 102969885B
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main switch
switch
voltage
diode
shunt capacitance
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CN102969885A (en
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李睿
王艺翰
梁星
蔡旭
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Shanghai Zhonglv New Energy Technology Co.,Ltd.
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Shanghai Jiaotong University
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    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02P—CLIMATE CHANGE MITIGATION TECHNOLOGIES IN THE PRODUCTION OR PROCESSING OF GOODS
    • Y02P80/00—Climate change mitigation technologies for sector-wide applications
    • Y02P80/10—Efficient use of energy, e.g. using compressed air or pressurized fluid as energy carrier

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Abstract

The invention provides a kind of without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector and modulator approach, comprise the load of power factor corrector DC side, DC bus capacitor, ac filter inductance, the brachium pontis having the full control main switch of anti-paralleled diode to form by two, with another brachium pontis be made up of two Diode series, the auxiliary switch of anti-paralleled diode is had access between DC bus capacitor and the brachium pontis side DC bus of Diode series, main switch and auxiliary switch two ends shunt capacitance, diode two ends shunt capacitance on brachium pontis, the resonant branch that the cross-over connection of auxiliary switch two ends is connected with clamping capacitance by resonant inductance.Main switch of the present invention adopts sine wave pulse width modulation method, and auxiliary switch modulation signal is synchronous with main switch.Structure of the present invention is simple, and DC side exports and can use as DC power supply.Switching loss is little, and circuit efficiency is high, is conducive to improving operating frequency, and then improves power density.

Description

Without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector and modulator approach
Technical field
The present invention relates to Bridgeless Power Factor Corrector, particularly, relate to a kind of without auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector circuit topology and modulator approach.
Background technology
Single-phase power factor correcting device general at present, as shown in Figure 1, it comprises by four diode D its circuit 1~ D 4the single-phase full bridge brachium pontis formed, is connected on the input filter inductance L between brachium pontis mid point and AC network.This single-phase power factor correcting device can realize being used as the functions such as communication power supply, but in the loop passage of this circuit, diode is more, and conduction loss is larger.In order to reduce diode current flow loss, Bridgeless Power Factor Corrector is suggested, and as shown in Figure 2, it comprises the full control main switch S having anti-paralleled diode by two to its circuit 1~ S 2the brachium pontis formed, by two diode D 3~ D 4form another brachium pontis, be connected on the input filter inductance L between brachium pontis mid point and AC network, it is characterized in that two main switch S 1~ S 2shunt capacitance C respectively 1~ C 2, two diode D 3~ D 4shunt capacitance C respectively 3~ C 4, adopt this structure, eliminate the pressure drop of a diode in line current passage, improve efficiency.But circuit working is in hard switching state, there is the reverse-recovery problems of diode, devices switch loss is large, limits the raising of operating frequency, reduces circuit efficiency and there is larger electromagnetic interference.
Through retrieval, publication number is the Chinese patent of 101599695A, this invention " provides a kind of Bridgeless power factor circuit correcting circuit and control method thereof, circuit comprises: the first inductor, second inductor, first diode, second diode, the parallel branch of load and electric capacity, , first gate-controlled switch device, second gate-controlled switch device, 3rd gate-controlled switch device, 4th gate-controlled switch device and control unit, described control unit controls shutoff and the conducting of described 3rd gate-controlled switch device and described 4th gate-controlled switch device, synchronous with the switching of civil power power frequency positive-negative half-cycle to realize it.Technical scheme provided by the invention can further improve Bridgeless power factor circuit correcting circuit efficiency, improve electromagnetic interference common-mode noise without bridge Bridgeless power factor circuit correcting circuit.”
Compared with the Chinese patent application being 101599695A with publication number, first: the topological structure that the present invention proposes and corresponding control strategy are more simple, the switching device of use is less, and filter inductance volume and weight is less, secondly, the topological structure proposed in 101599695A and control strategy main purpose are by increasing a parallel power current branch, the resistance value of parallel power current branch is reduced, thus the conduction loss reduced on this branch road, but all switching tubes of this circuit are all hard switchings, under high-frequency work condition, the switching loss of power factor corrector circuit is even more serious, therefore the topological structure that proposes of 101599695A and control strategy actual raising efficiency not obvious when high-frequency work, and the present invention is by increasing an auxiliary branch, the no-voltage realizing all switches is open-minded, effective twin zener dioder Reverse recovery, thus reduction switching loss, power factor corrector efficiency can be effectively improve when high-frequency work, effectively can also reduce EMI simultaneously.
Summary of the invention
For defect of the prior art, the object of this invention is to provide a kind of can the reverse recovery current of twin zener dioder, reduce switching loss, improve circuit efficiency, reduce electromagnetic interference and realize that switch tube zero voltage opens without auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector and modulator approach.
According to an aspect of the present invention, provide a kind of without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector, comprise DC side load R, the DC bus capacitor C in parallel with load R, have the full control main switch S of anti-paralleled diode by two 1, S 2the brachium pontis formed, by two diode D 3, D 4form another brachium pontis, be connected on the input filter inductance L between brachium pontis mid point and AC network, wherein: two main switch S 1, S 2an electric capacity in parallel i.e. the first electric capacity C respectively 1, the second electric capacity C 2, two diode D 3, D 4an electric capacity in parallel i.e. the 3rd electric capacity C respectively 3, the 4th electric capacity C 4, between DC bus capacitor C and the brachium pontis side DC bus of Diode series, have access to the auxiliary switch S of anti-paralleled diode 5, auxiliary switch S 5two ends shunt capacitance C 5, and at auxiliary switch S 5two ends cross-over connection is by resonant inductance L rwith clamping capacitance C cthe resonant branch be in series.
According to another aspect of the present invention, provide a kind of modulator approach without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector, wherein: main switch adopts sine wave pulse width modulation method, and auxiliary switch modulation signal is synchronous with main switch modulation signal.Auxiliary switch turned off from the diode change of current at main switch before full control switch, creates no-voltage open condition for main switch.Within the blink that auxiliary switch turns off, upper and lower two Switch Cut-through of main switch brachium pontis provide freewheeling path to resonant inductance, make resonant inductance stored energy be enough to realize power factor corrector zero voltage switch.
Compared with prior art, the present invention has following beneficial effect:
Of the present invention simple without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector structure, in power factor corrector, the Reverse recovery of the anti-paralleled diode of full control switch is inhibited, and decreases electromagnetic interference.In circuit, to realize no-voltage open-minded for all device for power switching, thus reduce switching loss, improves circuit efficiency, is conducive to improving operating frequency, and then improves power density.The circuit of power factor corrector of the present invention can realize, to the control of output dc voltage power and stable, can be used as communication DC power supply.
Accompanying drawing explanation
By reading the detailed description done non-limiting example with reference to the following drawings, other features, objects and advantages of the present invention will become more obvious:
Fig. 1 is hard switching single-phase power factor correcting device;
Fig. 2 is that hard switching is without bridge single-phase power factor correcting device;
Fig. 3 is the first physical circuit figure of the present invention;
Fig. 4 is the second physical circuit figure of the present invention;
Fig. 5 is the third physical circuit figure of the present invention;
Fig. 6 is the 4th kind of physical circuit figure of the present invention;
Fig. 7 is the Pulse Width Control sequential chart of the present invention under positive half cycle operating mode;
Fig. 8 ~ Figure 16 is the work equivalent electric circuit of the present invention in the next switch periods of positive half cycle operating mode;
Figure 17 is the present invention at the mains voltage of the next switch periods of positive half cycle operating mode and current waveform;
Figure 18 is the Pulse Width Control sequential chart of the present invention under negative half period operating mode;
Figure 19 ~ Figure 27 is the work equivalent electric circuit of the present invention in the next switch periods of negative half period operating mode;
Figure 28 is the present invention at the mains voltage of the next switch periods of negative half period operating mode and current waveform.
Embodiment
Below in conjunction with specific embodiment, the present invention is described in detail.Following examples will contribute to those skilled in the art and understand the present invention further, but not limit the present invention in any form.It should be pointed out that to those skilled in the art, without departing from the inventive concept of the premise, some distortion and improvement can also be made.These all belong to protection scope of the present invention.
With reference to Fig. 3, of the present invention without auxiliary voltage zero voltage switch Bridgeless Power Factor Corrector, comprise DC side load R, DC bus capacitor C, have anti-paralleled diode D by two 1~ D 2full control main switch S 1~ S 2the brachium pontis formed, by two diode D 3~ D 4form another brachium pontis, be connected on the input filter inductance L between brachium pontis mid point and AC network, wherein: two main switch S 1~ S 2shunt capacitance C respectively 1~ C 2, two diode D 3~ D 4shunt capacitance C respectively 3~ C 4, between DC bus capacitor C and the brachium pontis side DC bus of Diode series, have access to the auxiliary switch S of anti-paralleled diode 5, auxiliary switch S 5two ends shunt capacitance C 5, and at auxiliary switch S 5two ends cross-over connection is by resonant inductance L rwith clamping capacitance C cthe resonant branch be in series.
In specific embodiment shown in Fig. 3, auxiliary switch S 5emitter and power factor corrector DC bus capacitor C anode are connected, and collector electrode and diode brachium pontis positive bus-bar are connected, clamping capacitance C cbe connected with diode brachium pontis positive bus-bar, resonant inductance L rbe connected with power factor corrector DC bus capacitor C anode.
In another embodiment shown in Fig. 4, auxiliary switch S 5emitter and power factor corrector DC bus capacitor C anode are connected, and collector electrode and diode brachium pontis positive bus-bar are connected, resonant inductance L rbe connected with diode brachium pontis positive bus-bar, clamping capacitance C cbe connected with power factor corrector DC bus capacitor C anode.
In another embodiment shown in Fig. 5, auxiliary switch S 5collector electrode and power factor corrector DC bus capacitor C negative terminal are connected, and emitter and diode brachium pontis negative busbar are connected, clamping capacitance C cbe connected with diode brachium pontis negative busbar, resonant inductance L rbe connected with power factor corrector DC bus capacitor C negative terminal.
In another embodiment shown in Fig. 6, auxiliary switch S 5collector electrode and power factor corrector DC bus capacitor C negative terminal are connected, and emitter and diode brachium pontis negative busbar are connected, resonant inductance L rbe connected with diode brachium pontis negative busbar, clamping capacitance C cbe connected with power factor corrector DC bus capacitor C negative terminal.
Sine Wave Pulse Width Modulation (SPWM) is adopted without auxiliary voltage zero voltage switch power factor corrector.Within the whole modulating wave cycle, the complementary conducting of S1 and S2.
If Sine Modulated voltage is u ref=msin (ω t), when adopting bipolar modulation, switch S 1 duty ratio D=msin (ω t), switch S 2 duty ratio D=1-msin (ω t).
Positive and negative two half periods are divided into without auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector operating state.Here first for analyzing without the switch periods of auxiliary voltage zero voltage switch power factor corrector at positive half cycle shown in Fig. 3, the switching pulse Control timing sequence of power factor corrector as shown in Figure 7.In a switch duty cycle, power factor corrector has 9 operating states.Fig. 8 ~ Figure 16 is the work equivalent electric circuit in the next switch periods of positive half cycle operating mode.Mains voltage during work and current waveform are as shown in figure 17.
The concrete phase analysis of positive half cycle is as follows:
Stage 1 (t 0-t 1):
As shown in Figure 8, main switch S 1with auxiliary switch S 5be in conducting state.By main switch S 1anti-paralleled diode D 1, and by auxiliary switch S 5with the auxiliary clamp branch road that resonance inductance L r and clamping capacitance Cc forms, diode D 4composition loop, the electric current of resonant inductance Lr increases gradually.
Stage 2 (t 1-t 2):
As shown in Figure 9, t 1moment, auxiliary switch S 5turn off, resonant inductance L rto main switch S 2shunt capacitance C 2with diode D 3shunt capacitance C 3electric discharge, to auxiliary switch S 5shunt capacitance C 5charging, S 5zero voltage turn-off.To t 2moment, main switch S 2shunt capacitance C 2with diode D 3shunt capacitance C 3both end voltage resonance to zero, main switch S 2anti-paralleled diode D 2start conducting, resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc.To t 2moment, resonant inductance L rwith main switch S 2shunt capacitance C 2, diode D 3shunt capacitance C 3, auxiliary switch S5 shunt capacitance C 5resonance completes, main switch S 2no-voltage can be realized open-minded.
Stage 3 (t 2-t 3):
As shown in Figure 10, t 2moment, main switch S 1drive singal turns off, S 1anti-paralleled diode D 1still conducting state is in.Resonant inductance L rterminal voltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces.
Stage 4 (t 3-t 4):
As shown in figure 11, t 3in the moment, drive main switch S 2realize no-voltage open-minded.Main switch S 2with main switch S 1anti-paralleled diode D 1the change of current, main switch S 1anti-and diode D 1experience reversely restoring process, due to resonant inductance L rexistence, main switch S 1anti-and diode D 1reverse recovery current is suppressed.Resonant inductance L rterminal voltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces.
Stage 5 (t 4-t 5):
As shown in figure 12, at t 4in the moment, again drive main switch S 1open-minded, thus force main switch S 1, S 2whole bridge arm direct pass, to resonant inductance L rfreewheeling path is provided, makes resonant inductance electric current continue to reduce, namely oppositely increase, make resonant inductance store more energy, be enough to realize power factor corrector zero voltage switch.
Stage 6(t 5-t 6)
As shown in figure 13, to t 5moment, main switch S 1again turn off.From t 5moment, resonant inductance L rstart and main switch S 1shunt capacitance C 1, diode D 3shunt capacitance C 3, auxiliary switch S 5shunt capacitance C 5resonance, main switch S 1two ends electric capacity C 1with diode D 3shunt capacitance C 3voltage starts to increase, auxiliary switch S 5two ends shunt capacitance C 5voltage reduces, to t 6moment, auxiliary switch S 5two ends shunt capacitance C 5voltage is reduced to zero, auxiliary switch S 5anti-also diode D 5conducting, auxiliary switch S 5no-voltage can be realized open-minded.
Stage 7 (t 6-t 7):
As shown in figure 14, to t 6moment, resonant inductance L rwith main switch S 1shunt capacitance C 1, diode D 3shunt capacitance C 3, auxiliary switch S 5shunt capacitance C 5resonance stops, and main switch side DC bus-bar voltage is V dc.AC network and main switch S 2, diode D 4form current loop.
Stage 8 (t 7-t 8):
As shown in figure 15, to t 7moment, main switch S 2turn off, the electric current in filter inductance L is to main switch S 2shunt capacitance C 2charging, to main switch S 1shunt capacitance C 1electric discharge, due to S 2the existence of shunt capacitance, S 2realize zero voltage turn-off.To t 8moment, main switch S 1anti-paralleled diode D 1clamp, main switch S 1can be open-minded under zero voltage condition.
Stage 9 (t 8-t 9):
As shown in figure 16, to t 8moment, main switch S 1drive singal is open-minded, main switch S 1body in diode D 1conducting, t 9moment and t 0moment circuit state is identical, repeats next cycle.
When shown in Fig. 3 without auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector at negative half period time be that auxiliary switch is at switching tube S 2anti-paralleled diode D 2to main switch S 1turn off before the change of current, its concrete circuit diagram is as shown in Figure 18 ~ 28.Like this, the operating mode without the whole power frequency period of auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector shown in Fig. 3 is all analyzed.
The concrete phase analysis of negative half period is as follows:
Stage 1 (t 0-t 1):
As shown in figure 19, main switch S 2with auxiliary switch S 5be in conducting state.By main switch S 2anti-paralleled diode D 2, and by auxiliary switch S 5with the auxiliary clamp branch road that resonance inductance L r and clamping capacitance Cc forms, diode D 3composition loop, the electric current of resonant inductance Lr increases gradually.
Stage 2 (t 1-t 2):
As shown in figure 20, t 1moment, auxiliary switch S 5turn off, resonant inductance L rto main switch S 1shunt capacitance C 1with diode D 4shunt capacitance C 4electric discharge, to auxiliary switch S 5shunt capacitance C 5charging, S 5zero voltage turn-off.To t 2moment, main switch S 1shunt capacitance C 1with diode D 4shunt capacitance C 4both end voltage resonance to zero, main switch S 1anti-paralleled diode D 1start conducting, resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc.To t 2moment, resonant inductance L rwith main switch S 1shunt capacitance C 1, diode D 4shunt capacitance C 4, auxiliary switch S5 shunt capacitance C 5resonance completes, main switch S 1no-voltage can be realized open-minded.
Stage 3 (t 2-t 3):
As shown in figure 21, t 2moment, main switch S 2drive singal turns off, S 2anti-paralleled diode D 2still conducting state is in.Resonant inductance L rterminal voltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces.
Stage 4 (t 3-t 4):
As shown in figure 22, t 3in the moment, drive main switch S 1realize no-voltage open-minded.Main switch S 1with main switch S 2anti-paralleled diode D 2the change of current, main switch S 2anti-and diode D 2experience reversely restoring process, due to resonant inductance L rexistence, main switch S 2anti-and diode D 2reverse recovery current is suppressed.Resonant inductance L rterminal voltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces.
Stage 5 (t 4-t 5):
As shown in figure 23, at t 4in the moment, again drive main switch S 2open-minded, thus force main switch S 1, S 2whole bridge arm direct pass, to resonant inductance L rfreewheeling path is provided, makes resonant inductance electric current continue to reduce, namely oppositely increase, make resonant inductance store more energy, be enough to realize power factor corrector zero voltage switch.
Stage 6(t 5-t 6)
As shown in figure 24, to t 5moment, main switch S 2again turn off.From t 5moment, resonant inductance L rstart and main switch S 2shunt capacitance C 2, diode D 4shunt capacitance C 4, auxiliary switch S 5shunt capacitance C 5resonance, main switch S 1two ends electric capacity C 1with diode D 3shunt capacitance C 3voltage starts to increase, auxiliary switch S 5two ends shunt capacitance C 5voltage reduces, to t 6moment, auxiliary switch S 5two ends shunt capacitance C 5voltage is reduced to zero, auxiliary switch S 5anti-also diode D 5conducting, auxiliary switch S 5no-voltage can be realized open-minded.
Stage 7 (t 6-t 7):
As shown in figure 25, to t 6moment, resonant inductance L rwith main switch S 2shunt capacitance C 2, diode D 4shunt capacitance C 4, auxiliary switch S 5shunt capacitance C 5resonance stops, and main switch side DC bus-bar voltage is V dc.AC network and main switch S 1, diode D 3form current loop.
Stage 8 (t 7-t 8):
As shown in figure 26, to t 7moment, main switch S 1turn off, the electric current in filter inductance L is to main switch S 1shunt capacitance C 1charging, to main switch S 2shunt capacitance C 2electric discharge, due to S 1the existence of shunt capacitance, S 1realize zero voltage turn-off.To t 8moment, main switch S 2anti-paralleled diode D 2clamp, main switch S 2can be open-minded under zero voltage condition.
Stage 9 (t 8-t 9):
As shown in figure 27, to t 8moment, main switch S 2drive singal is open-minded, main switch S 2body in diode D 2conducting, t 9moment and t 0moment circuit state is identical, repeats next cycle.
Structure of the present invention is simple, and DC side exports and can use as DC power supply.Switching loss is little, and circuit efficiency is high, is conducive to improving operating frequency, and then improves power density.
Above specific embodiments of the invention are described.It is to be appreciated that the present invention is not limited to above-mentioned particular implementation, those skilled in the art can make various distortion or amendment within the scope of the claims, and this does not affect flesh and blood of the present invention.

Claims (1)

1., without a modulator approach for auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector circuit, it is characterized in that:
Describedly comprise power factor corrector DC side load R, DC bus capacitor C, by two main switch S without auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector circuit 1, S 2the brachium pontis formed, by two diode D 3, D 4form another brachium pontis, be connected on the input filter inductance L between brachium pontis mid point and AC network, wherein: two main switch S 1, S 2there is anti-paralleled diode D respectively 1, D 2, two main switch S 1, S 2first electric capacity C in parallel respectively 1, the second electric capacity C 2, two diode D 3, D 43rd electric capacity C in parallel respectively 3, the 4th electric capacity C 4, at DC bus capacitor C and diode D 3, D 4anti-paralleled diode D is had access between the brachium pontis side DC bus be in series 5auxiliary switch S 5, auxiliary switch S 5two ends shunt capacitance C 5, and at auxiliary switch S 5two ends cross-over connection is by resonant inductance L rwith clamping capacitance C cthe resonant branch be in series; Described auxiliary switch S 5collector electrode and DC bus capacitor C anode be connected, emitter and brachium pontis side DC bus anode are connected, clamping capacitance C cbe connected with brachium pontis side DC bus anode, resonant inductance L rbe connected with power factor corrector DC bus capacitor C anode;
Described main switch S 1, S 2adopt sine wave pulse width modulation method, auxiliary switch S 5modulation signal is synchronous with main switch modulation signal; Auxiliary switch S 5at main switch S 1, S 2from diode D 1, D 2the change of current is to main switch S 1, S 2turn off, be main switch S before 1, S 2create no-voltage and open condition; At auxiliary switch S 5in the blink turned off, main switch S 1, S 2lead directly to resonant inductance L rfreewheeling path is provided, makes resonant inductance L rstored energy is enough to realize power factor corrector zero voltage switch;
Describedly be divided into positive and negative two half periods without auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector operating state, in a switch duty cycle, power factor corrector has 9 operating states;
The positive half cycle concrete stage is as follows:
Stage 1 (t 0-t 1):
T 0moment, main switch S 1with auxiliary switch S 5be in conducting state; By main switch S 1anti-paralleled diode D 1, by auxiliary switch S 5with the auxiliary clamp branch road that resonance inductance L r and clamping capacitance Cc forms, diode D 4composition loop, the electric current of resonant inductance Lr increases gradually;
Stage 2 (t 1-t 2):
T 1moment, auxiliary switch S 5turn off, resonant inductance L rto main switch S 2shunt capacitance C 2with diode D 3shunt capacitance C 3electric discharge, to auxiliary switch S 5shunt capacitance C 5charging, auxiliary switch S 5zero voltage turn-off; To t 2moment, main switch S 2shunt capacitance C 2with diode D 3shunt capacitance C 3both end voltage resonance to zero, main switch S 2anti-paralleled diode D 2start conducting, resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc; To t 2moment, resonant inductance L rwith main switch S 2shunt capacitance C 2, diode D 3shunt capacitance C 3, auxiliary switch S 5shunt capacitance C 5resonance completes, main switch S 2no-voltage can be realized open-minded;
Stage 3 (t 2-t 3):
T 2moment, main switch S 1drive singal turns off, main switch S 1anti-paralleled diode D 1still conducting state is in; Resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces;
Stage 4 (t 3-t 4):
T 3in the moment, drive main switch S 2realize no-voltage open-minded; Main switch S 2with main switch S 1anti-paralleled diode D 1the change of current, main switch S 1anti-paralleled diode D 1experience reversely restoring process, due to resonant inductance L rexistence, main switch S 1anti-paralleled diode D 1reverse recovery current is suppressed; Resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces;
Stage 5 (t 4-t 5):
At t 4in the moment, again drive main switch S 1open-minded, thus force main switch S 1, S 2whole bridge arm direct pass, to resonant inductance L rfreewheeling path is provided, makes resonant inductance L relectric current continues to reduce, and namely oppositely increases, makes resonant inductance L rstore more energy, be enough to realize power factor corrector zero voltage switch;
Stage 6 (t 5-t 6)
To t 5moment, main switch S 1again turn off; From t 5moment, resonant inductance L rstart and main switch S 1shunt capacitance C 1, diode D 3shunt capacitance C 3, auxiliary switch S 5shunt capacitance C 5resonance, main switch S 1two ends electric capacity C 1with diode D 3shunt capacitance C 3voltage starts to increase, auxiliary switch S 5two ends shunt capacitance C 5voltage reduces, to t 6moment, auxiliary switch S 5two ends shunt capacitance C 5voltage is reduced to zero, auxiliary switch S 5anti-paralleled diode D 5conducting, auxiliary switch S 5no-voltage can be realized open-minded;
Stage 7 (t 6-t 7):
To t 6moment, resonant inductance L rwith main switch S 1shunt capacitance C 1, diode D 3shunt capacitance C 3, auxiliary switch S 5shunt capacitance C 5resonance stops, and brachium pontis side DC bus-bar voltage is V dc; AC network and main switch S 2, diode D 4form current loop;
Stage 8 (t 7-t 8):
To t 7moment, main switch S 2turn off, the electric current in input filter inductance L is to main switch S 2shunt capacitance C 2charging, to main switch S 1shunt capacitance C 1electric discharge, due to main switch S 2shunt capacitance C 2existence, main switch S 2realize zero voltage turn-off; To t 8moment, main switch S 1anti-paralleled diode D 1clamp, main switch S 1can be open-minded under zero voltage condition;
Stage 9 (t 8-t 9):
To t 8moment, main switch S 1drive singal is open-minded, main switch S 1anti-paralleled diode D 1conducting, t 9moment and t 0moment circuit state is identical, repeats next cycle;
The negative half period concrete stage is as follows:
Stage 1 (t 0-t 1):
T 0moment, main switch S 2with auxiliary switch S 5be in conducting state; By main switch S 2anti-paralleled diode D 2, by auxiliary switch S 5with the auxiliary clamp branch road that resonance inductance L r and clamping capacitance Cc forms, diode D 3composition loop, resonant inductance L relectric current increase gradually;
Stage 2 (t 1-t 2):
T 1moment, auxiliary switch S 5turn off, resonant inductance L rto main switch S 1shunt capacitance C 1with diode D 4shunt capacitance C 4electric discharge, to auxiliary switch S 5shunt capacitance C 5charging, auxiliary switch S 5zero voltage turn-off; To t 2moment, main switch S 1shunt capacitance C 1with diode D 4shunt capacitance C 4both end voltage resonance to zero, main switch S 1anti-paralleled diode D 1start conducting, resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc; To t 2moment, resonant inductance L rwith main switch S 1shunt capacitance C 1, diode D 4shunt capacitance C 4, auxiliary switch S 5shunt capacitance C 5resonance completes, main switch S 1no-voltage can be realized open-minded;
Stage 3 (t 2-t 3):
T 2moment, main switch S 2drive singal turns off, main switch S 2anti-paralleled diode D 2still conducting state is in; Resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces;
Stage 4 (t 3-t 4):
T 3in the moment, drive main switch S 1realize no-voltage open-minded; Main switch S 1with main switch S 2anti-paralleled diode D 2the change of current, main switch S 2anti-paralleled diode D 2experience reversely restoring process, due to resonant inductance L rexistence, main switch S 2anti-paralleled diode D 2reverse recovery current is suppressed; Resonant inductance L rvoltage is power factor corrector DC voltage V by clamp dc, resonant inductance L relectric current linearly reduces;
Stage 5 (t 4-t 5):
At t 4in the moment, again drive main switch S 2open-minded, thus force main switch S 1, S 2whole bridge arm direct pass, to resonant inductance L rfreewheeling path is provided, makes resonant inductance L relectric current continues to reduce, and namely oppositely increases, makes resonant inductance L rstore more energy, be enough to realize power factor corrector zero voltage switch;
Stage 6 (t 5-t 6)
To t 5moment, main switch S 2again turn off; From t 5moment, resonant inductance L rstart and main switch S 2shunt capacitance C 2, diode D 4shunt capacitance C 4, auxiliary switch S 5shunt capacitance C 5resonance, main switch S 1two ends electric capacity C 1with diode D 3shunt capacitance C 3voltage starts to increase, auxiliary switch S 5two ends shunt capacitance C 5voltage reduces, to t 6moment, auxiliary switch S 5two ends shunt capacitance C 5voltage is reduced to zero, auxiliary switch S 5anti-paralleled diode D 5conducting, auxiliary switch S 5no-voltage can be realized open-minded;
Stage 7 (t 6-t 7):
To t 6moment, resonant inductance L rwith main switch S 2shunt capacitance C 2, diode D 4shunt capacitance C 4, auxiliary switch S 5shunt capacitance C 5resonance stops, and brachium pontis side DC bus-bar voltage is V dc; AC network and main switch S 1, diode D 3form current loop;
Stage 8 (t 7-t 8):
To t 7moment, main switch S 1turn off, the electric current in input filter inductance L is to main switch S 1shunt capacitance C 1charging, to main switch S 2shunt capacitance C 2electric discharge, due to main switch S 1shunt capacitance C 1existence, main switch S 1realize zero voltage turn-off; To t 8moment, main switch S 2anti-paralleled diode D 2clamp, main switch S 2can be open-minded under zero voltage condition;
Stage 9 (t 8-t 9):
To t 8moment, main switch S 2drive singal is open-minded, main switch S 2anti-paralleled diode D 2conducting, t 9moment and t 0moment circuit state is identical, repeats next cycle;
When without auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector at negative half period time be auxiliary switch S 5at main switch S 2anti-paralleled diode D 2to main switch S 1turn off before the change of current, like this, the operating mode without the whole power frequency period of auxiliary voltage stress zero voltage switch Bridgeless Power Factor Corrector is all analyzed.
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CN104852567A (en) * 2015-05-20 2015-08-19 常州信息职业技术学院 Totem-pole bridgeless power factor correction circuit of soft switch
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