TWI488415B - Three - phase feedforward inductor current control device and its control method - Google Patents
Three - phase feedforward inductor current control device and its control method Download PDFInfo
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Description
本發明係有關一種三相電流控制裝置及其控制法，特別是有關一種三相前饋式電感電流控制裝置及其控制法。The invention relates to a three-phase current control device and a control method thereof, in particular to a three-phase feedforward inductor current control device and a control method thereof.
工業負載幾乎都是非線性或不平衡負載，造成電壓飄動、諧波電流及電壓源不平衡。此外，自從愈來愈多單位功率因數的再生能源注入到交流電網，例如太陽能發電裝置取得太陽能而轉變成電能後，此電能可直接併入市內配電網或以電池儲存能量，但此類再生能源也會導致市電電壓和頻率的飄動和三相不平衡，而造成必須與電網解聯。Industrial loads are almost always non-linear or unbalanced loads, causing voltage fluctuations, harmonic currents, and voltage source imbalances. In addition, since more and more unit power factor renewable energy is injected into the AC grid, for example, the solar power generation device converts electricity into solar energy, the electric energy can be directly incorporated into the local distribution network or stored energy by the battery, but such renewable energy It will also cause the fluctuation of the mains voltage and frequency and the three-phase unbalance, which will result in the need to be disconnected from the grid.
因此，在國際最新標準，如VDE-AR-N4105，根據電力公司的要求，市電併聯型換流器需要操作在功率因數領先或落後0.9，使它可以維持交流電網電壓在正常的工作範圍。隨著再生能源市電併聯系統的需求增加，虛功率注入變成愈來愈重要，且功因領先或落後的範圍將會擴大。對市電併聯型換流器來說，有一些應用，如一般的市電併聯型換流器(意即賣電力給市電)、整流(意即從市電購買電力)、虛功率補償器(static synchronous compensator，STATCOM)及主動式電力濾波器(active power filter，APF)。Therefore, in the latest international standards, such as VDE-AR-N4105, according to the requirements of the power company, the mains parallel converter needs to operate at a power factor lead or 0.9 behind, so that it can maintain the AC grid voltage within the normal working range. As the demand for renewable energy mains parallel systems increases, virtual power injection becomes more and more important, and the scope of lead or backwardness will expand. For the mains parallel converter, there are some applications, such as the general commercial parallel converter (meaning to sell electricity to the mains), rectification (meaning to buy electricity from the mains), virtual synchronous compensator , STATCOM) and active power filter (APF).
依據目前現有的控制方式，基本上都是基於空間向量脈波寬度調變(Space Vector PWM，SVPWM)，可以使用d-q轉換來得到責任比的控制法則，空間向量脈寬調變是建立在三相電壓平衡的情況下，利用電流誤差補償來克服市電諧波造成的失真以及取樣延遲的控制問題等。惟三相之電感值並不是固定不變，在功率越大的系統中，電流越大會使得感值變得越小。由於空間向量脈寬調變本身是以三相電感相等的條件來推導控制法則，當電感隨著電流變化而改變時，以空間向量脈寬調變推導之控制法則就不成立。According to the current control methods, basically based on space vector pulse width modulation (Space Vector PWM, SVPWM), you can use dq conversion to get the control law of the ratio of responsibility, space vector pulse width modulation is based on three-phase In the case of voltage balance, current error compensation is used to overcome the distortion caused by the harmonics of the mains and the control problem of the sampling delay. However, the inductance value of the three phases is not fixed. In systems with higher power, the larger the current, the smaller the sense value becomes. Since the space vector pulse width modulation itself derives the control law based on the condition that the three-phase inductance is equal, when the inductance changes with the current change, the control law derived from the space vector pulse width modulation is not established.
倘若控制器沒有將電感變化納入考量，勢必要用極大的補償 量來克服電感值的不足，這會將使得系統存在發散的風險。因此，將電感變化加入控制法則是不可或缺的。接著，在一般換流器的控制器中，往往因為開關切換的雜訊干擾到回授取樣，而造成控制器震盪或誤動作。雖然可以使用類比濾波器濾除高頻雜訊，卻會造成回授訊號延遲與系統響應變慢，而使得換流器的交流輸出失真。If the controller does not take into account the change in inductance, it is necessary to use great compensation. The amount to overcome the lack of inductance, which will make the system risk of divergence. Therefore, adding inductance changes to the control law is indispensable. Then, in the controller of the general inverter, the noise of the switch is often disturbed to the feedback sampling, which causes the controller to oscillate or malfunction. Although the analog filter can be used to filter out high-frequency noise, it will cause the feedback signal delay and system response to slow down, which will make the AC output of the inverter distorted.
再者，空間向量脈波寬度調變有兩個限制：一是d-q轉換是基於相量形式，假設換流器的電流和市電電壓是正弦波且三相平衡，如果存在電壓諧波或三相不平衡，d-q轉換將會產生錯誤的結果，且其電流諧波和控制延遲也將導致d-q轉換的值不正確；二是假設三相電感為固定值以求得d-q轉換值，然而在高功率的應用時，電感值將會隨著電流變化而變化，因而導致穩定性變差。縱使在現有的技術當中，有許多方法一直致力於使用市電電壓補償和電流預測來減少電流諧波；另外一種方法即一週期控制(One-Cycle Control，OCC)，使用雙降壓電路概念來推導出控制法則，而不使用傳統的SVPWM及d-q框轉換。但是以上的方法皆無考慮電感值隨著電流變化而變化。Furthermore, the space vector pulse width modulation has two limitations: First, the dq conversion is based on the phasor form, assuming that the current and the mains voltage of the converter are sinusoidal and the three phases are balanced, if there are voltage harmonics or three phases Unbalanced, dq conversion will produce erroneous results, and its current harmonics and control delay will also cause the dq conversion value to be incorrect; second, assume that the three-phase inductance is a fixed value to obtain the dq conversion value, but at high power In the application, the inductance value will change with the current, resulting in poor stability. Even though there are many methods in the existing technology, we have been working to reduce current harmonics using mains voltage compensation and current prediction. Another method is One-Cycle Control (OCC), which uses the concept of dual-buck circuit to derive Control rules are used instead of traditional SVPWM and dq box conversion. However, none of the above methods considers that the inductance value changes with current.
有鑑於此，本發明係針對上述之問題，本發明提出一種三相前饋式電感電流控制裝置及其控制法，以涵蓋電感值隨著電流的變化，且使功因範圍可以從0~1變化。從現有的太陽能併網換流器加入實虛功率之控制，也可以達到靜止同步補償器(STATCOM)之功能，可達到一機多功能的換流器，並可以因應電壓浮動及頻率飄移的程度，來注入功因為0~1的實虛功補償，藉此得以解決以上所述之缺失。In view of the above, the present invention is directed to the above problems, and the present invention provides a three-phase feedforward inductor current control device and a control method thereof to cover the variation of the inductance value with the current, and the power factor range can be from 0 to 1. Variety. From the existing solar grid-connected converter to the real virtual power control, it can also achieve the function of the static synchronous compensator (STATCOM), which can reach a multi-function inverter and can respond to voltage fluctuation and frequency drift. In order to solve the above-mentioned shortcomings, the injection of work is compensated by the real virtual work of 0~1.
本發明之主要目的，係在提供一種三相前饋式電感電流控制裝置及其控制法，其係為可允許電感電流變化之三相前饋式電流控制法於實功與虛功注入電網之應用。本發明藉由加入電感電流變化的考量，重新推導出不同於傳統SVPWM的控制法則，並且可使功率因素於0~1超前或落後，如此一來，不但是精簡了開關切換時序，可改善傳統SVPWM因三相不平衡、電流諧波與控制延遲而使得d-q轉換不成立的限制。The main object of the present invention is to provide a three-phase feedforward inductor current control device and a control method thereof, which are three-phase feedforward current control method capable of allowing a change in inductor current to be injected into a power grid in real power and virtual work. application. The invention re-introduces the control law different from the traditional SVPWM by adding the variation of the inductor current, and can make the power factor lead or lag behind 0~1, thus not only simplifying the switching timing, but also improving the tradition. SVPWM limits the dq conversion due to three-phase unbalance, current harmonics, and control delay.
為達上述之目的，本發明揭示一種三相前饋式電感電流控制裝置，包含有三相換流器具有可控式開關，且三相換流器並聯直流電壓源， 以輸出三相電流，濾波電路電性連接三相換流器，接收三相電流，以濾除三相電流之雜訊，藉以修正三相電壓之功率因素，並輸出電感電流至電網，微處理電路具有交流回授電路及直流回授電路，交流回授電路電性連接三相換流器、濾波電路及電網，藉以接收三相電流、電感電流及三相電壓，以輸出迴授電流及迴授電壓，直流回授電路電性連接直流電壓源，以接收直流電壓訊號，藉此微處理電路根據前饋式電感電流控制法以校正迴授電流、迴授電壓及直流電壓訊號，以得到電流預測變化量，再根據三相責任比控制演算法以計算電流預測變化量，以決定可控式開關之責任比，藉此以驅動三相換流器。In order to achieve the above purpose, the present invention discloses a three-phase feedforward inductor current control device, which comprises a three-phase inverter with a controllable switch, and a three-phase converter with a parallel DC voltage source, To output three-phase current, the filter circuit is electrically connected to the three-phase inverter, and receives three-phase current to filter out the noise of the three-phase current, thereby correcting the power factor of the three-phase voltage, and outputting the inductor current to the grid, and micro-processing The circuit has an AC feedback circuit and a DC feedback circuit, and the AC feedback circuit is electrically connected to the three-phase inverter, the filter circuit and the power grid to receive the three-phase current, the inductor current and the three-phase voltage to output the feedback current and return The voltage feedback and DC feedback circuit is electrically connected to the DC voltage source to receive the DC voltage signal, whereby the microprocessor circuit corrects the feedback current, the feedback voltage and the DC voltage signal according to the feedforward inductor current control method to obtain the current. The change amount is predicted, and then the current prediction change amount is calculated according to the three-phase duty ratio control algorithm to determine the duty ratio of the controllable switch, thereby driving the three-phase inverter.
一種三相前饋式電感電流控制法，包括下列步驟，接收直流電壓源，轉輸出成三相電流，接收三相電流轉輸出成迴授電流及電感電流，並濾除三相電流之雜訊，藉以修正三相電壓之功率因素，再輸出等電感電流至電網，且參考電感電流及三相電壓，藉此輸出迴授電壓，接收迴授電流、電感電流及三相電壓、迴授電壓及直流電壓訊號，根據前饋式電感電流控制法校正迴授電流、迴授電壓及直流電壓訊號，以得到電流預測變化量，再根據三相責任比控制演算法，計算電流預測變化量，以決定可控式開關之責任比。A three-phase feedforward inductor current control method includes the following steps: receiving a DC voltage source, converting the output into a three-phase current, receiving the three-phase current to output the feedback current and the inductor current, and filtering out the noise of the three-phase current By correcting the power factor of the three-phase voltage, and then outputting the same inductor current to the grid, and referring to the inductor current and the three-phase voltage, thereby outputting the feedback voltage, receiving the feedback current, the inductor current, the three-phase voltage, and the feedback voltage and The DC voltage signal corrects the feedback current, the feedback voltage and the DC voltage signal according to the feedforward inductor current control method to obtain the current prediction variation, and then calculates the current prediction variation according to the three-phase responsibility ratio control algorithm to determine The duty ratio of the controllable switch.
底下藉由具體實施例配合所附的圖式詳加說明，當更容易瞭解本發明之目的、技術內容、特點及其所達成之功效。The purpose, technical contents, features and effects achieved by the present invention will be more readily understood by the detailed description of the embodiments and the accompanying drawings.
10‧‧‧三相前饋式電感電流控制裝置10‧‧‧Three-phase feedforward inductor current control device
12‧‧‧直流電壓源12‧‧‧DC voltage source
14‧‧‧電網14‧‧‧ Grid
16‧‧‧三相換流器16‧‧‧Three-phase inverter
18‧‧‧可控式開關18‧‧‧Controllable switch
20‧‧‧濾波電路20‧‧‧Filter circuit
22‧‧‧微處理電路22‧‧‧Microprocessing circuits
24‧‧‧交流回授電路24‧‧‧AC feedback circuit
26‧‧‧直流回授電路26‧‧‧DC feedback circuit
28‧‧‧絕緣柵雙極電晶體28‧‧‧Insulated gate bipolar transistor
30‧‧‧二極體30‧‧‧ diode
32‧‧‧R相開關32‧‧‧R phase switch
34‧‧‧S相開關34‧‧‧S phase switch
36‧‧‧T相開關36‧‧‧T phase switch
38‧‧‧電感組38‧‧‧Inductance group
40‧‧‧電容組40‧‧‧Capacitor group
42‧‧‧電流選擇器42‧‧‧current selector
44‧‧‧電壓選擇器44‧‧‧Voltage selector
46‧‧‧單晶片46‧‧‧ single chip
48‧‧‧驅動電路48‧‧‧ drive circuit
i L ‧‧‧電感電流 i L ‧‧‧Inductor current
AC ‧‧‧交流端 AC ‧‧‧AC
V DC ‧‧‧直流電壓訊號 V DC ‧‧‧ DC voltage signal
v RS 、v TR 、v ST ‧‧‧三相電壓 v RS , v TR , v ST ‧‧‧ three-phase voltage
i R 、i S 、i T ‧‧‧三相電流 i R , i S , i T ‧‧‧ three-phase current
i fb,p( n ) 、i fb,n( n ) ‧‧‧迴授電流 i fb,p( n ) , i fb,n( n ) ‧‧‧recurrent current
v fb,p( n ) 、v fb,n( n ) ‧‧‧迴授電壓 v fb,p( n ) , v fb,n( n ) ‧‧‧reciprocal voltage
i ref ‧‧‧參考電流 i ref ‧‧‧reference current
n ‧‧‧週期次數 n ‧‧‧cycles
i e (.) 、i v (.) ‧‧‧三相電流預測變化量 i e (.) , i v (.) ‧‧‧Three-phase current prediction change
D p 、D n 、D F ‧‧‧責任比 D p , D n , D F ‧ ‧ liability ratio
△i L ‧‧‧三相電感電流變化量 △i L ‧‧‧Three-phase inductor current change
T s ‧‧‧切換週期 T s ‧‧‧ switching cycle
i e ‧‧‧誤差量 i e ‧‧‧error
L ‧‧‧電感量 L ‧‧‧Inductance
i v ‧‧‧電流預測變化量 i v ‧‧‧current prediction change
r ‧‧‧電感電流方向 r ‧‧‧Inductor current direction
v ‧‧‧電壓量值 v ‧‧‧Voltage
u R ‧‧‧R相控制訊號 u R ‧‧‧R phase control signal
u S ‧‧‧S相控制訊號 u S ‧‧‧S phase control signal
u T ‧‧‧T相控制訊號 u T ‧‧‧T phase control signal
i LR ‧‧‧R相電感電流 i LR ‧‧‧R phase inductor current
i LS ‧‧‧S相電感電流 i LS ‧‧‧S phase inductor current
i LT ‧‧‧T相電感電流phase of the inductor current i LT ‧‧‧T
L R ‧‧‧R相電感 L R ‧‧‧R phase inductance
L S ‧‧‧S相電感 L S ‧‧‧S phase inductor
L T ‧‧‧T相電感 L T ‧‧‧T phase inductor
S RH 、S RL 、S SH 、S SL 、S TH 、S TL ‧‧‧驅動訊號 S RH , S RL , S SH , S SL , S TH , S TL ‧‧‧ drive signals
G c,p ,、G c,n ,、G c,F ‧‧‧控制增益 G c,p ,, G c,n ,, G c,F ‧‧‧Control gain
L (‧) ‧‧‧三相電感 L (‧) ‧‧‧Three-phase inductor
K p ‧‧‧電流誤差補償量 K p ‧‧‧current error compensation
第1圖係為本發明之三相前饋式電感電流控制裝置方塊圖。Figure 1 is a block diagram of a three-phase feedforward inductor current control device of the present invention.
第2圖係為本發明之三相換流器驅動示意圖。Figure 2 is a schematic diagram of the driving of the three-phase inverter of the present invention.
第3圖係為本發明之前饋式電感電流控制法方塊圖。Figure 3 is a block diagram of the feed inductor current control method of the present invention.
第4圖係為本發明之三相前饋式電感電流控制方法流程圖。Figure 4 is a flow chart of the three-phase feedforward inductor current control method of the present invention.
第5圖係為本發明之三角波模式取樣示意圖。Figure 5 is a schematic diagram of the sampling of the triangular wave mode of the present invention.
本發明於此列舉一實施例，參閱第1圖、第2圖及第3圖，藉此說明本發明之三相前饋式電感電流控制裝置方塊圖、三相換流器驅動 示意圖及前饋式電感電流控制法方塊圖。如圖所示，本發明之三相前饋式電感電流控制裝置10，係用於並聯直流電壓源12，藉此轉換輸出複數電感電流i L ，以透過交流端AC 注入電網14中。其中，直流電壓源12具有直流電壓訊號V DC ，且電網具有三相電壓v RS 、v TR 、v ST 。The present invention will be described with reference to FIG. 1 , FIG. 2 and FIG. 3 , and the block diagram of the three-phase feedforward inductor current control device of the present invention, the three-phase converter driving schematic and the feedforward are described. Block diagram of the inductor current control method. As shown, the three-phase feedforward inductor current control device 10 of the present invention is used to connect a DC voltage source 12 in parallel, thereby converting and outputting a plurality of inductor currents i L for injection into the grid 14 through the AC terminal AC . The DC voltage source 12 has a DC voltage signal V DC , and the power grid has three-phase voltages v RS , v TR , v ST .
如前所述，本發明之三相前饋式電感電流控制裝置10係包含有三相換流器16，且其三相換流器16具有複數可控式開關18，三相換流器16並聯直流電壓源12，可輸出三相電流i R 、i S 、i T ，濾波電路20電性連接三相換流器16，接收三相電流i R 、i S 、i T ，以濾除三相電流i R 、i S 、i T 之雜訊，藉以修正三相電壓v RS 、v TR 、v ST 及三相電流i R 、i S 、i T 之功率因素，並以輸出複數電感電流i L 至電網14中。As described above, the three-phase feedforward inductor current control device 10 of the present invention includes a three-phase inverter 16 and the three-phase inverter 16 has a plurality of controllable switches 18, and the three-phase inverters 16 are connected in parallel. The DC voltage source 12 can output three-phase currents i R , i S , i T , and the filter circuit 20 is electrically connected to the three-phase inverter 16 to receive the three-phase currents i R , i S , i T to filter out the three phases. The noise of the currents i R , i S , i T , by which the power factors of the three-phase voltages v RS , v TR , v ST and the three-phase currents i R , i S , i T are corrected, and the complex inductor current i L is output To the grid 14.
此外，微處理電路22具有交流回授電路24及直流回授電路26，交流回授電路24電性連接三相換流器16、濾波電路20及電網14，藉以接收三相電流i R 、i S 、i T 及三相電壓v RS 、v TR 、v ST ，以輸出複數迴授電流i fb,p( n ) 、i fb,n( n ) 及複數迴授電壓v fb,p( n ) 、v fb,n( n ) ，直流回授電路26電性連接直流電壓源12，以接收直流電壓訊號V DC 。In addition, the microprocessor circuit 22 has an AC feedback circuit 24 and a DC feedback circuit 26. The AC feedback circuit 24 is electrically connected to the three-phase inverter 16, the filter circuit 20, and the power grid 14, thereby receiving three-phase currents i R , i . S , i T and three-phase voltages v RS , v TR , v ST for outputting complex feedback currents i fb,p( n ) , i fb,n( n ) and complex feedback voltages v fb,p( n ) And v fb,n( n ) , the DC feedback circuit 26 is electrically connected to the DC voltage source 12 to receive the DC voltage signal V DC .
微處理電路22根據前饋式電感電流控制法以校正迴授電流i fb,p( n ) 、i fb,n( n ) 、迴授電壓v fb,p( n ) 、v fb,n( n ) 及直流電壓訊號V DC ，以得到電流預測變化量i v (.) ，再根據三相責任比控制演算法以計算電流預測變化量i v (.) ，以決定複數可控式開關18之責任比，藉此以驅動三相換流器16。此外，如前述之前饋式電感電流控制法係將比較直流電壓訊號V DC 、迴授電流i fb,p( n ) 、i fb,n( n ) 及迴授電壓v fb,p( n ) 、v fb,n( n ) ，以取到電流預測變化量i v (.) ，電流預測變化量i v (.) 可表示為i ref (n+1)-i ref (n) ，且前述之i ref 為參考電流，n 為週期次數。The microprocessor circuit 22 corrects the feedback currents i fb,p( n ) , i fb,n( n ) , the feedback voltages v fb,p( n ) , v fb,n( n according to the feedforward inductor current control method. ) and the DC voltage signal V DC, to obtain the predicted amount of change in current i v (.), and then the responsibility of a three-phase current ratio control algorithm to calculate the predicted variation amount i v (.), to determine a plurality of controllable switches 18 The duty ratio is thereby used to drive the three-phase inverter 16. In addition, as described above, the feed-forward inductor current control method compares the DC voltage signal V DC , the feedback currents i fb, p( n ) , i fb, n( n ) and the feedback voltage v fb,p( n ) , v fb,n( n ) for taking the current predicted change amount i v (.) , and the current predicted change amount i v (.) can be expressed as i ref (n+1)-i ref (n) , and the foregoing i ref is the reference current and n is the number of cycles.
另外，本發明於前所述及之三相電流i R 、i S 、i T 係各別具有R相控制訊號u R 、S相控制訊號u S 及T相控制訊號u T ，且電感電流i L 係具有R相電感電流i LR 、S相電感電流i LS 及T相電感電流i LT 。In addition, the three-phase currents i R , i S , i T of the present invention have the R phase control signal u R , the S phase control signal u S and the T phase control signal u T , respectively, and the inductor current i The L system has an R-phase inductor current i LR , an S-phase inductor current i LS , and a T-phase inductor current i LT .
接續，參閱第2圖，本發明於前所述之三相前饋式電感電流控制裝置10，其中每一可控式開關18，各具有絕緣柵雙極電晶體28及二極體30，且絕緣柵雙極電晶體28並聯二極體30，且由每二可控式開關18分別各自組成R相開關32、S相開關34及T相開關36，且S相開關34並聯R相開關32，T相開關36並聯S相開關34，藉此R相開關32輸出R相控 制訊號u R ，S相開關34輸出S相控制訊號u S ，T相開關36輸出T相控制訊號u T 。Next, referring to FIG. 2, the three-phase feedforward inductor current control device 10 of the present invention, wherein each of the controllable switches 18 has an insulated gate bipolar transistor 28 and a diode 30, and The insulated gate bipolar transistor 28 is connected in parallel with the diode 30, and each of the two controllable switches 18 respectively constitutes an R phase switch 32, an S phase switch 34 and a T phase switch 36, and the S phase switch 34 is connected in parallel with the R phase switch 32. The T-phase switch 36 is connected in parallel with the S-phase switch 34, whereby the R-phase switch 32 outputs the R-phase control signal u R , the S-phase switch 34 outputs the S-phase control signal u S , and the T-phase switch 36 outputs the T-phase control signal u T .
復閱第1圖及第2圖，濾波電路20包含有電感組38，且其電感組38各具有R相電感L R 、S相電感L S 及T相電感L T 電性連接此複數可控式開關18，藉此分別對應接收三相電流i R 、i S 、i T ，再分別對應輸出R相電感電流i LR 、S相電感電流i LS 及T相電感電流i LT ，電容組40電性連接電感組38，藉以接收並濾除R相電感電流i LR 、S相電感電流i LS 及T相電感電流i LT ，以修正三相電壓v RS 、v TR 、v ST 之功率因素，再以輸出電感電流i L 至電網14中。Referring to FIG. 1 and FIG. 2, the filter circuit 20 includes an inductor group 38, and the inductor group 38 has an R-phase inductor L R , an S-phase inductor L S and a T-phase inductor L T electrically connected to the complex controllable The switch 18 is configured to respectively receive the three-phase currents i R , i S , i T , and then respectively output the R-phase inductor current i LR , the S-phase inductor current i LS and the T-phase inductor current i LT , and the capacitor group 40 is electrically The inductor group 38 is connected to receive and filter the R-phase inductor current i LR , the S-phase inductor current i LS , and the T-phase inductor current i LT to correct the power factors of the three-phase voltages v RS , v TR , and v ST , and then The inductor current i L is output to the grid 14.
復閱第1圖、第2圖及第3圖，交流回授電路24係包含有電流選擇器42電性連接三相換流器16，以接收三相電流i R 、i S 、i T ，以輸出迴授電流i fb,p( n ) 、i fb,n( n ) ，電壓選擇器44電性連接濾波電路20及電網14，以接收電感電流i L 及三相電壓v RS 、v TR 、v ST ，藉此輸出迴授電壓v fb,p( n ) 、v fb,n( n ) 。Referring to FIG. 1 , FIG. 2 and FIG. 3 , the AC feedback circuit 24 includes a current selector 42 electrically connected to the three-phase inverter 16 for receiving three-phase currents i R , i S , i T , To output the feedback currents i fb,p( n ) , i fb,n( n ) , the voltage selector 44 is electrically connected to the filter circuit 20 and the grid 14 to receive the inductor current i L and the three-phase voltages v RS , v TR And v ST , thereby outputting feedback voltages v fb,p( n ) , v fb,n( n ) .
此外，微處理電路22係包括有單晶片46電性連接交流回授電路24及直流回授電路26，並根據前饋式電感電流控制法校正迴授電流i fb,p( n ) 、i fb,n( n ) 、迴授電壓v fb,p( n ) 、v fb,n( n ) 及直流電壓訊號V DC ，以得到電流預測變化量，再根據三相責任比控制演算法進行計算該電流預測變化量，以決定複數可控式開關18之責任比，驅動電路48電性連接單晶片46及三相換流器16，藉此以適當之責任比輸出驅動訊號S RH 、S RL 、S SH 、S SL 、S TH 、S TL ，以驅動三相換流器16。另外，本發明之三相責任比控制演算法係以三角波以產生切換週期，並於三角波之峰值時取樣迴授電流i fb,p( n ) 、i fb,n( n ) ，且於前所述之迴授電流i fb,p( n ) 、i fb,n( n ) 代表切換週期內之電感電流i L 之平均值。In addition, the microprocessor circuit 22 includes a single chip 46 electrically connected to the AC feedback circuit 24 and the DC feedback circuit 26, and corrects the feedback currents i fb, p( n ) , i fb according to the feedforward inductor current control method. , n( n ) , feedback voltage v fb,p( n ) , v fb,n( n ) and DC voltage signal V DC to obtain the current predicted change amount, and then calculate according to the three-phase duty ratio control algorithm. The current predicts the amount of change to determine the duty ratio of the plurality of controllable switches 18. The driver circuit 48 is electrically coupled to the single chip 46 and the three-phase inverter 16, thereby outputting the drive signals S RH , S RL , with appropriate duty ratios. S SH , S SL , S TH , S TL to drive the three-phase inverter 16 . In addition, the three-phase duty ratio control algorithm of the present invention uses a triangular wave to generate a switching period, and samples the feedback currents i fb,p( n ) , i fb,n( n ) at the peak of the triangular wave, and The feedback currents i fb,p( n ) , i fb,n( n ) represent the average of the inductor currents i L during the switching period.
接續，本發明於此列舉一方法實施例，參閱第4圖，藉以說明本發明之三相前饋式電感電流控制方法流程圖，參閱同時輔以第1圖、第2圖及第3圖。如圖所示，本發明之一種三相前饋式電感電流控制法，係應用於三相前體式電感電流控制裝置10，且係並聯直流電壓源12，以輸出複數電感電流i L 注入電網14中，此外，直流電壓源12具有直流電壓訊號V DC ，電網14則具有三相電壓v RS 、v TR 、v ST 。Next, the present invention exemplifies a method embodiment. Referring to FIG. 4, a flow chart of the three-phase feedforward inductor current control method of the present invention will be described. Referring to FIG. 1 , FIG. 2 and FIG. 3 simultaneously. As shown in the figure, a three-phase feedforward inductor current control method of the present invention is applied to a three-phase precursor inductor current control device 10, and is a parallel DC voltage source 12, which is injected into the grid 14 by outputting a complex inductor current i L . In addition, the DC voltage source 12 has a DC voltage signal V DC , and the grid 14 has three-phase voltages v RS , v TR , v ST .
本發明之三相前饋式電感電流控制法係包含有：步驟S10接收直流電壓源12，轉以輸出成三相電流i R 、i S 、i T ，步驟S12，接收三相電 流i R 、i S 、i T 轉輸出成複數迴授電流i fb,p( n ) 、i fb,n( n ) 及複數電感電流i L ，步驟S14，濾除三相電流i R 、i S 、i T 之雜訊，藉以修正三相電壓v RS 、v TR 、v ST 之功率因素，以輸出電感電流i L 至電網14，步驟S16，參考電感電流i L 及三相電壓v RS 、v TR 、v ST ，藉此輸出複數迴授電壓v fb,p( n ) 、v fb,n( n ) 。The three-phase feedforward inductor current control method of the present invention comprises: receiving the DC voltage source 12 in step S10, converting the output into three-phase currents i R , i S , i T , step S12, receiving the three-phase current i R , i S , i T are outputted into complex feedback currents i fb,p( n ) , i fb,n( n ) and complex inductor current i L , step S14, filtering out three-phase currents i R , i S , i T The noise is used to correct the power factor of the three-phase voltages v RS , v TR , v ST to output the inductor current i L to the grid 14, step S16, reference inductor current i L and three-phase voltage v RS , v TR , v ST , thereby outputting a plurality of feedback voltages v fb,p( n ) , v fb,n( n ) .
接續，步驟S18，接收迴授電流i fb,p( n ) 、i fb,n( n ) 、電感電流i L 及三相電壓v RS 、v TR 、v ST 、迴授電壓v fb,p( n ) 、v fb,n( n ) 及直流電壓訊號V DC ，步驟S20，根據前饋式電感電流控制法校正迴授電流i fb,p( n ) 、i fb,n( n ) 、迴授電壓v fb,p( n ) 、v fb,n( n ) 及直流電壓訊號V DC ，以得到電流預測變化量，以及步驟S22，根據三相責任比控制演算法，計算電流預測變化量，以決定可控式開關18之責任比，並返回步驟S10。Next, in step S18, receiving feedback currents i fb, p( n ) , i fb, n( n ) , inductor current i L and three-phase voltages v RS , v TR , v ST , feedback voltage v fb, p ( n ) , v fb, n( n ) and the DC voltage signal V DC , step S20, correcting the feedback currents i fb, p( n ) , i fb, n( n ) , feedback according to the feedforward inductor current control method The voltages v fb,p( n ) , v fb,n( n ) and the DC voltage signal V DC are used to obtain a current predicted change amount, and in step S22, the current predicted change amount is calculated according to the three-phase duty ratio control algorithm to The duty ratio of the controllable switch 18 is determined and the process returns to step S10.
此外，如前所述之三相電流i R
、i S
、i T
各別具有R相控制訊號u R
、S相控制訊號u S
、T相控制訊號u T
，以追蹤每一週期的正弦參考電流i ref
。電感電流i L
各別為R相電感電流i LR
、S相電感電流i LS
及T相電感電流i LT
。此外，依據本發明之三相前饋式電感電流控制法，其三相電流i R
、i S
、i T
的零交越，可將0°~360°的相位分為六個相位區間，分別為有I區間0°~60°、II區間60°~120°、III區間120°~180°、IV區間180°~240°、V區間240°~300°以及VI區間300°~360°，因此，各區間所對應之三相電流i R
、i S
、i T
、三相電流預測變化量、三相電壓v RS
、v TR
、v ST
、R相電感L R
、S相電感L S
及T相電感L T
，以及可控式開關18所輸出之驅動訊號S RH
、S RL
、S SH
、S SL
、S TH
、S TL
狀態，則如表一及表二所示，其中表一係代表功因領先模式在公式中的參數，表二則係代表功因落後模式在公式中的參數，因此，其中下列表一及表二中的i e
(.)
係代表三相電流i R
、i S
、i T
，i v
(.)
則代表三相電流預測變化量：表一
本發明之前饋式電感電流控制法係將比較迴授電流i fb,p( n ) 、i fb,n( n ) 、迴授電壓v fb,p( n ) 、v fb,n( n ) 及直流電壓訊號V DC ，以取到電流預測變化量，電流預測變化量可表示為i ref (n+1)-i ref (n) ，其中i ref 為參考電流，n 為週期次數。The feed inductor current control method of the present invention compares the feedback currents i fb,p( n ) , i fb,n( n ) , the feedback voltages v fb,p( n ) , v fb,n( n ) and The DC voltage signal V DC is taken to obtain the current predicted change amount, and the current predicted change amount can be expressed as i ref (n+1)-i ref (n) , where i ref is the reference current and n is the number of cycles.
此外，三相責任比控制演算法係將電流預測變化量與延遲一切換週期之電流預測變化量相較之後，以取得三相電流預測變化量i v
(.)
、i e
(.)
，
切換週期之電流預測變化量相較之後，以取得三相電流預測變化量i v
(.)
、i e
(.)
，再依據三相電流預測變化量i v
(.)
、i e
(.)
、電感電流i L
，以決定複數可控式開關18之責任比，且三相責任比控制演算法之關係式為
其中，式1中△i L 為電感三相電流預測變化量，T s 為切換週期，i e 為誤差量，L 為電感量，V DC 為直流電壓，i v 為電流預測變化量，r 代表電感電流方向，D p 、D n 、D F 為各可控式開關18之責任比，v 為電壓量值。Where Δi L is the predicted change of the three-phase current of the inductor, T s is the switching period, i e is the error amount, L is the inductance, V DC is the DC voltage, i v is the current prediction variation, and r is the The direction of the inductor current, D p , D n , D F is the duty ratio of each controllable switch 18, and v is the magnitude of the voltage.
接續，參閱第5圖，藉此說明本發明之三角波模式取樣示意圖，參閱同時輔以第2圖及第3圖，如圖所示，本發明之三相前饋式電感電流控制法，其中三相責任比控制演算法係用三角波以產生切換週期，因此可控式開關18之責任比輸出就會以三角波的中心點(峰值)呈對稱分布，並在切換週期內的電感電流i L 平均值就會剛好等於參考電流i ref 準位。因此，只要在三角波的峰值處取樣迴授電流i fb,p( n ) 、i fb,n( n ) ，就可以讓迴授電流i fb,p( n ) 、i fb,n( n ) 準確地匹配參考電流i ref ，而且只需要一次取樣即可。且於三角波之峰值時取樣迴授電流i fb,p( n ) 、i fb,n( n ) ，迴授電流i fb,p( n ) 、i fb,n( n ) 代表切換週期內 之電感電流i L 之平均值。如第3圖所示，其中 、K p =1，控制增益G c,p ,、G c,n ,、G c,F 為三相電感L (‧) 的函式，且增 益將隨著電感電流而跟著改變，以達到動態及比例補償。對電流誤差補償量K p 來說，1是最佳選擇。當K p =1，可以真實反映下一週期回授電流及參考電流之間的變化，即i v (.) +i e (.) =i ref (n+1)-i ref (n)+i ref (n) -i fb (n) =i ref (n+1)-i fb (n) 。此外，第3圖中的電流選擇器42根據六個區間的i p 與i n ，決定適合的三相電流i R 、i S 、i T 帶入。同樣的，電壓選擇器44也是用來決定六區間所要帶入公式的三相電壓v RS 、v ST 、v TR 。最後，依據這個設計，我們提出的控制法可以精確的追蹤每一週期的正弦參考電流。Next, referring to FIG. 5, a schematic diagram of sampling of the triangular wave mode of the present invention will be described. Referring to FIG. 2 and FIG. 3 simultaneously, as shown in the figure, the three-phase feedforward inductor current control method of the present invention, three of which The phase-response ratio control algorithm uses a triangular wave to generate a switching period. Therefore, the duty-dependent switch 18 is more symmetrically distributed than the center point (peak) of the triangular wave, and the average value of the inductor current i L during the switching period. It will be exactly equal to the reference current i ref level. Therefore, as long as the sampling feedback current i fb at the peak of the triangular wave, p (n), i fb , n (n), you can let the feedback current i fb, p (n), i fb, n (n) accurately The ground matches the reference current i ref and only needs to be sampled once. And sampling the feedback currents i fb,p( n ) , i fb,n( n ) at the peak of the triangular wave, and the feedback currents i fb,p( n ) , i fb,n( n ) represent the inductances in the switching period. The average of the current i L . As shown in Figure 3, where , K p =1, the control gains G c,p , , G c,n , , G c,F are the functions of the three-phase inductor L (‧) , and the gain will change with the inductor current to achieve dynamic And proportional compensation. For the current error compensation amount K p , 1 is the best choice. When K p =1, it can truly reflect the change between the feedback current and the reference current in the next cycle, ie i v (.) + i e (.) = i ref (n+1) - i ref (n) + i ref (n) - i fb (n) = i ref (n+1)-i fb (n) . Further, the current selector 42 in Fig. 3 determines the appropriate three-phase currents i R , i S , i T to be carried in based on i p and i n of the six sections. Similarly, the voltage selector 44 is also used to determine the three-phase voltages v RS , v ST , v TR to be brought into the equation for the six intervals. Finally, based on this design, our proposed control method can accurately track the sinusoidal reference current of each cycle.
綜上所述，本發明於此揭示一種三相前饋式電感電流控制裝置10及其控制法，其係為可允許電感電流i L 變化之三相前饋式電流控制法於實功與虛功注入電網之應用。本發明加入電感電流i L 變化的考量，重新 推導出不同於傳統SVPWM的控制法則，並且可使功率因素於0~1超前或落後，如此一來，不但是精簡了開關切換時序，可改善傳統SVPWM因三相不平衡、電流諧波與控制延遲而使得d-q轉換不成立的限制。In summary, the present invention discloses a three-phase feedforward inductor current control device 10 and a control method thereof, which are three-phase feedforward current control methods that allow the change of the inductor current i L to be real and virtual. The application of power to the grid. The invention adds the consideration of the change of the inductor current i L , re-introduces the control rule different from the traditional SVPWM, and can make the power factor lead or lag behind 0~1, thus not only simplifying the switching timing, but also improving the tradition. SVPWM limits the dq conversion due to three-phase unbalance, current harmonics, and control delay.
雖然，本發明前述之實施例揭露如上，然其並非用以限訂本發明。在不脫離本發明之精神和範圍內所為之更動與潤飾，均屬於本發明專利範圍之主張。關於本發明所界定之專利範圍請參考所附之請求項。The foregoing embodiments of the present invention are disclosed above, but are not intended to limit the invention. Modifications and modifications made without departing from the spirit and scope of the invention are claimed in the scope of the invention. Please refer to the attached request for the scope of patents defined by the present invention.
10‧‧‧三相前饋式電感電流控制裝置10‧‧‧Three-phase feedforward inductor current control device
12‧‧‧直流電壓源12‧‧‧DC voltage source
14‧‧‧電網14‧‧‧ Grid
16‧‧‧三相換流器16‧‧‧Three-phase inverter
18‧‧‧可控式開關18‧‧‧Controllable switch
20‧‧‧濾波電路20‧‧‧Filter circuit
22‧‧‧微處理電路22‧‧‧Microprocessing circuits
24‧‧‧交流回授電路24‧‧‧AC feedback circuit
26‧‧‧直流回授電路26‧‧‧DC feedback circuit
28‧‧‧絕緣柵雙極電晶體28‧‧‧Insulated gate bipolar transistor
30‧‧‧二極體30‧‧‧ diode
32‧‧‧R相開關32‧‧‧R phase switch
34‧‧‧S相開關34‧‧‧S phase switch
36‧‧‧T相開關36‧‧‧T phase switch
38‧‧‧電感組38‧‧‧Inductance group
40‧‧‧電容組40‧‧‧Capacitor group
46‧‧‧單晶片46‧‧‧ single chip
48‧‧‧驅動電路48‧‧‧ drive circuit
i L ‧‧‧電感電流 i L ‧‧‧Inductor current
AC ‧‧‧交流端 AC ‧‧‧AC
V DC ‧‧‧直流電壓訊號 V DC ‧‧‧ DC voltage signal
v RS 、v TR 、v ST ‧‧‧三相電壓 v RS , v TR , v ST ‧‧‧ three-phase voltage
i R 、i S 、i T ‧‧‧三相電流 i R , i S , i T ‧‧‧ three-phase current
u R ‧‧‧R相控制訊號 u R ‧‧‧R phase control signal
u S ‧‧‧S相控制訊號 u S ‧‧‧S phase control signal
u T ‧‧‧T相控制訊號 u T ‧‧‧T phase control signal
i LR ‧‧‧R相電感電流 i LR ‧‧‧R phase inductor current
i LS ‧‧‧S相電感電流 i LS ‧‧‧S phase inductor current
i LT ‧‧‧T相電感電流phase of the inductor current i LT ‧‧‧T
L R ‧‧‧R相電感 L R ‧‧‧R phase inductance
L S ‧‧‧S相電感 L S ‧‧‧S phase inductor
L T ‧‧‧T相電感 L T ‧‧‧T phase inductor
S RH 、S RL 、S SH 、S SL 、S TH 、S TL ‧‧‧驅動訊號 S RH , S RL , S SH , S SL , S TH , S TL ‧‧‧ drive signals
Claims (11)
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