CN1937382A - Zero-voltage switch combined full-bridge three-level direct current converter - Google Patents
Zero-voltage switch combined full-bridge three-level direct current converter Download PDFInfo
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- CN1937382A CN1937382A CNA200610096759XA CN200610096759A CN1937382A CN 1937382 A CN1937382 A CN 1937382A CN A200610096759X A CNA200610096759X A CN A200610096759XA CN 200610096759 A CN200610096759 A CN 200610096759A CN 1937382 A CN1937382 A CN 1937382A
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Abstract
This DC converter is one kind of energy converter. It consists of the DC power supply (Vin), the bridge circuit, the isolation transformer IT, and the resonance inductance RI and the rectifier/filter circuit. The bridge consists of a 3-level inversion bridge arm and a 2-level inversion bridge arm. There adds an auxiliary winding (AW) on the primary side of IT. One end of the primary winding is connected to the output end of the 3-level inversion bridge arm while the other end to AW. Two clamp diodes (Dc1, Dc2) are respectively connected to the positive and the negative buses of the DC input of the inverter to form the clamping circuit. Another end of the AW is connected to RI. The other end of RI is connected to the output end of the 2-level inversion bridge arm. This converter is suitable to a wide input voltage range. It can decrease the currents through the clamping diodes rapidly, reduce loss and improves the work condition of clamping diodes during light load.
Description
One, technical field
Zero-voltage switch combined full-bridge three-level direct current converter of the present invention, the DC converter of genus transformation of electrical energy device.
Two, background technology
In recent years, three-level DC converter has been subjected to paying close attention to widely in the application of high pressure occasion, because its switch tube voltage stress only is input voltage half.In order to raise the efficiency and reduce the weight and the volume of converter, a lot of soft switch in three electrical levels DC converter circuit topologies have appearred in recent years.Leakage inductance and the junction capacitance of the switching tube soft switch of realizing switching tube of three-level DC converter of zero-voltage switch by transformer.Wherein two switching tubes of zero-voltage and zero-current switch three-level DC converter can be realized zero voltage switch, and other two switching tubes then can be realized Zero Current Switch.These converters have all only been realized the soft switch of switching tube, and still there is reverse-recovery problems in the output rectifying tube, oppositely recover to cause voltage oscillation, and the output rectifying tube will bear due to voltage spikes, are easy to damage.
Zero-voltage switch combined full-bridge three-level direct current converter, the voltage stress of its three level brachium pontis switching tube is half of input voltage, can in wide loading range, realize zero voltage switch, output rectified waveform medium-high frequency component is little, can reduce output inductor, input current is approximately a direct current electric current, can reduce advantages such as input filter.But the same output rectifying tube that exists oppositely recovers to cause the due to voltage spikes problem that produces on the rectifying tube.
The number of applying for a patent is that 200410064935.2 " combined full-bridge three-level direct current converter and full-bridge three-level DC converter " introduces two clamping diodes in combined full-bridge three-level direct current converter, the advantage that has not only kept primary circuit has been eliminated due to voltage spikes and voltage oscillation on the output rectifying tube simultaneously effectively.
Electric current is the poor of resonant inductance electric current and transformer primary current in the clamping diode.In order to reduce to flow through electric current in the clamping diode, reduce loss, just need reduce output inductor.And, then need increase output filter capacitor, and then the volume and the cost of converter have been increased in order to satisfy the output voltage ripple requirement.Simultaneously, when converter was operated in underloading even no-load condition, duty ratio was less relatively, and clamping diode is turn-offed firmly, causes the damage of clamping diode easily.
Three, summary of the invention
The objective of the invention is to defective at above-mentioned converter, develop a kind of Zero-voltage switch combined full-bridge three-level direct current converter with the auxiliary winding of transformer, not only can eliminate due to voltage spikes and voltage oscillation on the output rectifying tube, can also reduce to flow through electric current in the clamping diode effectively fast, improve conversion efficiency, improve the operational environment of clamping diode under the underloading situation simultaneously.
Zero-voltage switch combined full-bridge three-level direct current converter of the present invention, comprise that DC power supply forms bridge circuit, isolating transformer, resonant inductance, clamp circuit and current rectifying and wave filtering circuit by tri-level inversion brachium pontis and two-level inverter arm, wherein the tri-level inversion brachium pontis comprise be connected in parallel on the DC power supply positive-negative output end by input dividing potential drop electric capacity with import the input dividing potential drop condenser network that the dividing potential drop capacitances in series becomes; The inverter bridge leg that is connected into successively by first switching tube, second switch pipe, the 3rd switching tube, the 4th switching tube is connected in parallel on input dividing potential drop condenser network two outputs, above-mentioned four switching tubes individual diodes in parallel separately and a parasitic capacitance, a striding capacitance in parallel and a freewheeling circuit that is connected into by first fly-wheel diode and second fly-wheel diode between the series connection point of the series connection point of first switching tube and second switch pipe and the 3rd switching tube and the 4th switching tube, wherein the series connection point of two fly-wheel diodes is connected on the series connection point of two input dividing potential drop electric capacity; The inverter bridge leg that the two-level inverter arm is connected into by the 5th switching tube and the 6th switching tube is connected in parallel on input dividing potential drop condenser network two outputs equally; The clamp circuit that is connected into by two clamping diodes is connected in parallel on tri-level inversion brachium pontis two ends and two-level inverter arm two ends simultaneously; Two secondary winding non-same polarities with the number of turn of isolating transformer secondary are in series, the end of the same name of one of them secondary winding other end is connected in the current rectifying and wave filtering circuit anode, the series connection point of two secondary windings links to each other with the negative terminal of current rectifying and wave filtering circuit, it is characterized in that, the former limit winding of described isolating transformer links to each other with the auxiliary winding non-same polarity in former limit, the auxiliary winding other end in former limit is connected in resonant inductance one end, this resonant inductance other end is connected on the series connection point of two switching tubes of two-level inverter arm, and the former limit winding other end is connected on the series connection point of second switch Guan Yudi three switching tubes in the tri-level inversion brachium pontis; The series connection point of two clamping diodes of described clamp circuit is connected in the series connection point of the auxiliary winding of isolating transformer former limit winding and former limit.
The present invention's major technique characteristics compared with prior art are, owing to added the clamping diode circuit, the voltage oscillation and the due to voltage spikes that cause because of the reverse recovery of exporting rectifying tube have been eliminated, reduced the voltage stress of output rectifying tube, and eliminated of the loss of output rectifying tube, simultaneously, increased the auxiliary winding of transformer because of oppositely recovering to cause, can reduce to flow through electric current in the clamping diode effectively fast, improve the operational environment of clamping diode under the underloading situation.
Description of drawings
Accompanying drawing 1 is a Zero-voltage switch combined full-bridge three-level direct current converter electrical block diagram of the present invention.
Accompanying drawing 2 is the main waveform schematic diagrames of 3L mode of operation of the present invention.
Accompanying drawing 3 is the main waveform schematic diagrames of 2L mode of operation of the present invention.
Accompanying drawing 4-19 is the equivalent circuit structure schematic diagram of each switch mode.
Main designation in the above-mentioned accompanying drawing: V
In, supply voltage.C
D1, C
D2, input dividing potential drop electric capacity.Q
1～Q
6, switching tube.C
1～C
6, parasitic capacitance.D
1～D
6, body diode.D
F1, D
F2, fly-wheel diode.C
Ss1, striding capacitance.L
r, resonant inductance.T
r, isolating transformer.D
C1, D
C2, clamping diode.D
R1, D
R2, output rectifier diode.L
f, filter inductance.C
f, filter capacitor.R
Ld, load.V
o, output voltage.v
AB, A and B point-to-point transmission voltage.v
Rect, voltage after the rectification of transformer secondary.
Embodiment
Control method is as follows: switching tube Q
2And Q
3Be 180 ° of complementary conductings, switching tube Q
5And Q
6Be 180 ° of complementary conductings, and respectively with respect to switching tube Q
3And Q
2So the phase place that lags behind is definition switching tube Q
2And Q
3Be advance pipe, switching tube Q
5And Q
6Be the pipe that lags behind.Switching tube Q
1And Q
4Homophase is positioned at switching tube Q respectively
2And Q
3So PWM work is definition switching tube Q
1And Q
4Be the copped wave pipe.
When input voltage is low, switching tube Q
1And Q
4PWM work, switching tube Q
2, Q
3With switching tube Q
6, Q
5Between a less fixed skew is arranged, with switching tube Q
2, Q
3Realize ZVS and switching tube Q
5, Q
6Realize that ZVS separates.The voltage that export after the rectification this moment is three level waveforms, is referred to as three level modes (3L pattern).When input voltage is higher, switching tube Q
1And Q
4Pulsewidth will be reduced to zero, switching tube Q
2, Q
3With switching tube Q
6, Q
5Phase shift work, the voltage that export after the rectification this moment is two level waveforms, is referred to as two level modes (2L pattern).
Copped wave pipe Q
1, Q
4With advance pipe Q
2, Q
3Realize zero voltage switch by filter inductance and resonant inductance, pipe Q lags behind
5And Q
6Then realize zero voltage switch, thereby reduce the switching loss of switching tube, improve conversion efficiency by the energy of resonant inductance.In tri-level inversion brachium pontis circuit, also be added with continued flow tube D
F1, D
F2, and in sustained diode
F1Negative electrode and sustained diode
F2Anode between cross-over connection striding capacitance C
Ss1, its role is to the switching process of two pairs of switching tubes is coupled together.When the converter steady operation, striding capacitance C
Ss1On voltage constant be V
In/ 2.
Be main circuit structure with accompanying drawing 1 below, 4～18 narrate concrete operation principle of the present invention in conjunction with the accompanying drawings.By accompanying drawing 2 as can be known whole converter switch periods in the 3L pattern 20 kinds of switch mode are arranged, be respectively [t
0[t in the past],
0, t
1], [t
1, t
2], [t
2, t
3], [t
3, t
4], [t
4, t
5], [t
5, t
6], [t
6, t
7], [t
7, t
8], [t
8, t
9], [t
9, t
10], [t
10, t
11], [t
11, t
12], [t
12, t
13], [t
13, t
14], [t
14, t
15], [t
15, t
16], [t
16, t
17], [t
17, t
18], [t
18, t
19] (seeing accompanying drawing 2), wherein, [t
0In the past, t
9] be the preceding half period, [t
9, t
19] be the later half cycle.Below the working condition of each switch mode is made a concrete analysis of.
Before analyzing, make the following assumptions: 1. all switching tubes and diode are desirable device, rectifier diode D
R1And D
R2Except, its equivalence is an ideal diode and an electric capacity parallel connection, to be used for the simulated inverse recovery; 2. all inductance, electric capacity and transformer are ideal element; 3. striding capacitance C
Ss1Enough big, its voltage is constant substantially during stable state, is V
In/ 2.
1. switch mode 1[t
0[corresponding to accompanying drawing 4] in the past]
t
0Constantly, switching tube Q
1, Q
2And Q
6Conducting, AB point-to-point transmission voltage is v
AB=V
InSecondary rectifying tube D
R1Conducting, rectifying tube D
R2End.Energy is transmitted to secondary in former limit.
2. switch mode 2[t
0, t
1] [corresponding to accompanying drawing 5]
t
0Moment on-off switching tube Q
1, primary current i
pGive capacitor C
1Charging is simultaneously by striding capacitance C
Ss1Give capacitor C
4Discharge.Capacitor C
1And capacitor C
4Make switching tube Q
1Being approximately no-voltage turn-offs.Because voltage v
ABDescend diode D
C2Conducting immediately is with voltage v
CBPincers is zero, voltage v
ACDescend the corresponding decline of secondary voltage, rectifying tube D
R2Junction capacitance C
DR2Voltage also descend junction capacitance C
DR2Discharged.An output inductor electric current part is given junction capacitance C like this
DR2Discharge, remainder are converted former limit and are given capacitor C
1Charging and capacitor C
4Discharge.So primary current i
pAt t
0Step decline constantly because C point current potential is zero, is born the reverse voltage that is brought by auxiliary winding on the resonant inductance, promptly voltage is that the right side is just being born in a left side on the resonant inductance, so the resonant inductance current i
LrDescend to some extent, but because very short during this period of time, and voltage is less on the auxiliary winding, therefore can be similar to and think that its electric current is constant.It is higher than current i
pPart flow through diode D
C2To t
1Constantly, voltage v
C1Rise to V
In/ 2, diode D
F1The nature conducting, A point current potential is reduced to V
In/ 2, switch mode 2 finishes.
3. switch mode 3[t
1, t
2] [corresponding to accompanying drawing 6]
At t
1Constantly, diode D
F1Conducting, voltage v
ABBe clamped at V
In/ 2, junction capacitance C
DR2Discharge finishes, so current i
pAt t
1Step rises to I constantly
1, diode D
C2Turn-off.If this moment is voltage V
o＞V
InN
2/ 2 (n
1+ n
3), current i then
pAt voltage V
oEffect descend down; If this moment is voltage V
o＜V
InN
2/ 2 (n
1+ n
2), current i then
pAt voltage V
In/ 2 effect is risen down, the resonant inductance current i
LrWith current i
pKeep equating.Former limit continues to transmit energy to secondary.Accompanying drawing 6 has provided voltage V
o＞V
InN
2/ 2 (n
1+ n
3) situation.
4. switch mode 4[t
2, t
3] [corresponding to accompanying drawing 7]
t
2Moment on-off switching tube Q
2, current i
pGive capacitor C
2Charging is simultaneously by striding capacitance C
Ss1, give capacitor C
3Discharge.Capacitor C
2And capacitor C
3Make switching tube Q
2Being approximately no-voltage turn-offs.Voltage v
ABDescend, the same with the switch mode 1 of front, diode D
C2With conducting, with voltage v
CBPincers is zero, voltage v
ACDescend the corresponding decline of secondary voltage, rectifying tube D
R2Junction capacitance C
DR2Voltage also descend junction capacitance C
DR2Discharged.An output inductor electric current part is given junction capacitance C like this
DR2Discharge, remainder are converted former limit and are given capacitor C
2Charging and capacitor C
3Discharge.So current i
pAt t
2Step descends constantly, and because auxiliary winding voltage is less, so the resonant inductance current i
LrApproximate constant, it is higher than current i
pPart flow through diode D
C2To t
3Constantly, voltage v
C2=V
In/ 2, v
C3=0, v
AB=0.
5. switch mode 5[t
3, t
4] [corresponding to accompanying drawing 8]
Voltage v
AB=0, diode D
3And D
4Conducting, can no-voltage open switching tube Q this moment
3And Q
4Diode D
C2Still conducting, current i
pWith i
LrAll constant.Diode D
C2In electric current be current i
pWith i
LrDifference.At this moment, two rectifying tubes of secondary conducting simultaneously.
6. switch mode 6[t
4, t
5] [corresponding to accompanying drawing 9]
At t
4Constantly, no-voltage on-off switching tube Q
6, current i
LrGive capacitor C
6Capacitor C is given in charging simultaneously
5Discharge.Voltage v
ABBecome by zero negative, this moment voltage v
CB=-v
C6Resonant inductance L
rAnd capacitor C
5, C
6Resonance work.Current i
pContinue to remain unchanged current i
LrWith i
pDifference from diode D
C2In flow through.To t
5Constantly, voltage v
C5=0, voltage v
CB=V
In, diode D
5The nature conducting.
7. switch mode 7[t
5, t
6] [corresponding to accompanying drawing 10]
Diode D
5After the conducting, can no-voltage open switching tube Q
5Current i
pStill remain unchanged, two rectifying tubes of secondary are conducting simultaneously still, and the former limit of transformer winding, auxiliary winding and secondary winding voltage are zero, so voltage V
InAll be added in resonant inductance L
rTwo ends, the resonant inductance current i
LrLinear decline.At t
6Constantly, resonant inductance current i
LrDrop to and i
pEquate diode D
C2Naturally turn-off.
8. switch mode 8[t
6, t
7] [corresponding to accompanying drawing 11]
t
6Constantly begin voltage V
InStill be added in the resonant inductance two ends, the resonant inductance current i
LrWith current i
pDrop to zero also negative sense increase with the slope that equates, the conductings simultaneously of two rectifying tubes of secondary provide load current.At t
7Constantly, current i
pReach the load current-I of conversion to former limit
Lf(t
7)/K, this switch mode finishes, at this moment rectifying tube D
R1Turn-off rectifying tube D
R2Flow through whole load currents.
9. switch mode 9[t
7, t
8] [corresponding to accompanying drawing 12]
At t
7Constantly, resonant inductance L
rWith junction capacitance C
DR1Rectifying tube D is promptly given in resonance work
R1Junction capacitance C
DR1Charging, current i
pAnd i
LrContinuing increases.
During this period of time, the A point is fixed on zero potential, and the former limit of transformer winding voltage v
CABecause junction capacitance C
DR1Charging also rise simultaneously, so C point current potential is rising always.To t
8Constantly, junction capacitance C
DR1Voltage rise to 2V
InN
2/ n
1, this moment, the C point voltage rose to V
In, diode D
C1Conducting is with voltage v
CAAt voltage V
In, so junction capacitance C
DR1Voltage by pincers at 2V
InN
2/ n
1
10. switch mode 10[t
8, t
9] [corresponding to accompanying drawing 13]
As diode D
C1After the conducting, current i
pStep drops to the filter inductance electric current of converting former limit, and negative sense increases.Voltage is V on the at this moment auxiliary winding
InN
3/ n
1, voltage direction is that the right side is just being born in a left side, promptly C point current potential is low, because C point and B point current potential are V
In, so bear the positive right negative voltage in a left side on the resonant inductance, size is V
InN
3/ n
1, so the resonant inductance current i
LrReduce fast.It and primary current i
pDifference from diode D
C1In flow through.To t
9Constantly, primary current i
pWith resonance inductive current i
LrEquate that this mode finishes, diode D
C1Turn-off.
11. switch mode 11[t
9, t
10] [corresponding to accompanying drawing 14]
Diode D
C1Have no progeny in the pass, C point current potential descends voltage v gradually
CADescend voltage v after the rectification of transformer secondary
RectCorresponding decline is when reducing to V
InN
2/ (n
1+ n
3) time circuit enter steady operation, former limit provides energy to secondary, primary current i
pWith the resonant inductance current i
LrEquate.This mode is corresponding with switch mode 1.
By accompanying drawing 3 as can be known whole converter switch periods in the 2L pattern 20 kinds of switch mode are also arranged, wherein, [t
0In the past, t
9] be the preceding half period, [t
9, t
19] be the later half cycle.In the preceding half period, [t
0In the past, t
5] [t under the working condition of period and the 3L pattern
2, t
7] identical no longer repetition here of period.Below to [t
5, t
9] working condition of four switch mode of period makes a concrete analysis of.
1. switch mode 1[t
5, t
6] [corresponding to accompanying drawing 15]
At t
5Constantly, current i
pOppositely increase by zero, to capacitor C
4Charging is simultaneously by striding capacitance C
Ss1Give capacitor C
1Discharge.Because the former secondary voltage of transformer is zero, voltage v
ABDirectly be added in resonant inductance L
rOn, so resonant inductance L
rWith capacitor C
1, C
4Resonance work.As voltage v
CA=V
In/ 2 o'clock, diode D
F2Conducting.
2. switch mode 2[t
6, t
7] [corresponding to accompanying drawing 16]
Voltage v
AB=-V
In/ 2, because the former secondary voltage of transformer still is zero, so voltage v
ABAll be added in resonant inductance L
rTwo ends, current i
pLinear growth.At t
7Constantly, current i
pReach the load current-I of conversion to former limit
Lf(t
7)/K, this switch mode finishes, at this moment rectifying tube D
R1Turn-off rectifying tube D
R2Flow through whole load currents.
3. switch mode 3[t
7, t
8] [corresponding to accompanying drawing 17]
At t7 constantly, resonant inductance L
rWith junction capacitance C
DR1Rectifying tube D is promptly given in resonance work
R1Junction capacitance C
DR1Charging, current i
pWith resonance inductive current i
LrContinuing increases.
During this period of time, the A point is fixed on V
In/ 2 current potentials, and the former limit of transformer winding voltage v
CABecause junction capacitance C
DR1Charging also rise simultaneously, so C point current potential is rising always.To t
8Constantly, junction capacitance C
DR1Voltage rise to V
InN
2/ n
1, this moment, the C point voltage rose to V
In, diode D
C1Conducting is with voltage v
CAPincers is at voltage V
In, so junction capacitance C
DR1Voltage by pincers at V
InN
2/ n
1
4. switch mode 4[t
8, t
9] [corresponding to accompanying drawing 18]
As diode D
C1After the conducting, current i
pStep drops to the filter inductance electric current of converting former limit, and negative sense increases.Voltage is V on the at this moment auxiliary winding
InN
3/ 2n
1, voltage direction is that the right side is just being born in a left side, promptly C point current potential is low, because C point and B point voltage are V
In, so bear the positive right negative voltage in a left side on the resonant inductance, size is V
InN
3/ 2n
1, so the resonant inductance current i
LrReduce fast.It and primary current i
pDifference from diode D
C1In flow through.To t
9Constantly, primary current i
pWith resonance inductive current i
LrEquate that this mode finishes, diode D
C1Turn-off.
5. switch mode 5[t
9, t
10] [corresponding to accompanying drawing 19]
Diode D
C1Have no progeny in the pass, C point current potential descends voltage v gradually
CADescend voltage v after the rectification of transformer secondary
RectCorresponding decline is when reducing to V
InN
2/ 2 (n
1+ n
3) time circuit enter steady operation, former limit provides energy to secondary, primary current i
pWith the resonant inductance current i
LrEquate.
From the above analysis, the Zero-voltage switch combined full-bridge three-level direct current converter of the auxiliary winding of band transformer, no matter be in the 3L pattern or in the 2L pattern, can well eliminate the peak voltage of output rectifying tube, can reduce to flow through electric current in the clamping diode effectively fast, improve the operational environment of clamping diode under the underloading situation.
As seen from the above description, the Zero-voltage switch combined full-bridge three-level direct current converter of the auxiliary winding of band transformer of the present invention's proposition has following advantage:
Owing to added clamping diode, no matter be in the 3L pattern or in the 2L pattern, voltage oscillation and due to voltage spikes that the secondary rectifier diode does not all exist reverse recovery to cause.
Owing to increased the auxiliary winding of transformer, can reduce fast effectively to flow through electric current in the clamping diode, reduce loss, improve the operational environment of clamping diode under the underloading situation simultaneously.
The switch tube voltage stress of three level brachium pontis is half of input direct voltage, is beneficial to select suitable switching tube;
Output rectified waveform medium-high frequency component is little, can reduce output filter, thereby reduce the weight and volume of filtering, and improve the dynamic characteristic of converter;
Can in very wide loading range, realize the zero voltage switch of all switching tubes,
The input current pulsation of this converter is very little, therefore can reduce input filter.
Claims (1)
1. a Zero-voltage switch combined full-bridge three-level direct current converter comprises DC power supply (V
In), form bridge circuit, isolating transformer (3), resonant inductance (4), clamp circuit (5) and current rectifying and wave filtering circuit (6) by tri-level inversion brachium pontis (1) and two-level inverter arm (2), wherein tri-level inversion brachium pontis (1) comprises and is connected in parallel on DC power supply (V
In) positive-negative output end by input dividing potential drop electric capacity (C
D1) and input dividing potential drop electric capacity (C
D2) the input dividing potential drop condenser network that is connected into; By the first switching tube (Q
1), second switch pipe (Q
2), the 3rd switching tube (Q
3), the 4th switching tube (Q
4) inverter bridge leg that is connected into successively is connected in parallel on input dividing potential drop condenser network two outputs, above-mentioned four switching tube (Q
1, Q
2, Q
3, Q
4) individual diodes in parallel separately and a parasitic capacitance, at the first switching tube (Q
1) and second switch pipe (Q
2) series connection point and the 3rd switching tube (Q
3) and the 4th switching tube (Q
4) series connection point between striding capacitance (C in parallel
Ss1) and one by the first fly-wheel diode (D
F1) and the second fly-wheel diode (D
F2) freewheeling circuit that is connected into, wherein two fly-wheel diode (D
F1, D
F2) series connection point be connected two input dividing potential drop electric capacity (C
D1, C
D2) series connection point on; Two-level inverter arm (2) is by the 5th switching tube (Q
5) and the 6th switching tube (Q
6) inverter bridge leg that is connected into is connected in parallel on input dividing potential drop condenser network two outputs equally; By two clamping diode (D
C1, D
C2) clamp circuit (5) that is connected into is connected in parallel on tri-level inversion brachium pontis (1) two ends and two-level inverter arm (2) two ends simultaneously; Two secondary winding non-same polarities with the number of turn of isolating transformer (3) secondary are in series, the end of the same name of one of them secondary winding other end is connected in current rectifying and wave filtering circuit (6) anode, the different name end of another secondary winding other end is connected in current rectifying and wave filtering circuit (6) anode equally, the series connection point of two secondary windings links to each other with the negative terminal of current rectifying and wave filtering circuit (6), it is characterized in that, the former limit winding (n1) of described isolating transformer (3) links to each other with auxiliary winding (n3) non-same polarity in former limit, former limit assists winding (n3) other end to be connected in resonant inductance (4) one ends, and this resonant inductance (4) other end is connected in two switching tube (Q of two-level inverter arm (2)
5, Q
6) series connection point on, former limit winding (n1) other end is connected in second switch pipe (Q in the tri-level inversion brachium pontis (1)
2) and the 3rd switching tube (Q
3) series connection point on; Two clamping diode (D of described clamp circuit (5)
C1, D
C2) series connection point be connected in the series connection point of the auxiliary winding (n3) in isolating transformer (3) former limit winding (n1) and former limit.
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| CNB200610096759XA CN100539374C (en) | 2006-10-13 | 2006-10-13 | Zero-voltage switch combined full-bridge three-level direct current converter |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CNB200610096759XA CN100539374C (en) | 2006-10-13 | 2006-10-13 | Zero-voltage switch combined full-bridge three-level direct current converter |
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| CN1937382A true CN1937382A (en) | 2007-03-28 |
| CN100539374C CN100539374C (en) | 2009-09-09 |
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Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101818247A (en) * | 2010-04-09 | 2010-09-01 | 紫金矿业集团股份有限公司 | Selective heap leaching gold extraction process for gold mine containing copper |
| CN101860217A (en) * | 2010-06-11 | 2010-10-13 | 哈尔滨工业大学 | ZVS full-bridge three-level converter with bilateral buffer network |
| CN108631604A (en) * | 2018-05-28 | 2018-10-09 | 瀚润特环保设备（江苏）有限公司 | A kind of environmental protection dual transformer type zero current resonance three-level DC converter |
| CN111934576A (en) * | 2020-04-16 | 2020-11-13 | 山西大学 | Auxiliary resonance converter pole inverter with phase-correlated magnetizing current symmetric reset |
| CN112234829A (en) * | 2020-09-27 | 2021-01-15 | 陕西航空电气有限责任公司 | Soft switching circuit of phase-shifted full-bridge converter |
| CN114006535A (en) * | 2021-10-21 | 2022-02-01 | 福州大学 | Novel bidirectional three-level current-doubling LCL-T resonant converter circuit |
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2006
- 2006-10-13 CN CNB200610096759XA patent/CN100539374C/en not_active Expired - Fee Related
Cited By (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101818247A (en) * | 2010-04-09 | 2010-09-01 | 紫金矿业集团股份有限公司 | Selective heap leaching gold extraction process for gold mine containing copper |
| CN101818247B (en) * | 2010-04-09 | 2012-03-21 | 紫金矿业集团股份有限公司 | Selective heap leaching gold extraction process for gold mine containing copper |
| CN101860217A (en) * | 2010-06-11 | 2010-10-13 | 哈尔滨工业大学 | ZVS full-bridge three-level converter with bilateral buffer network |
| CN108631604A (en) * | 2018-05-28 | 2018-10-09 | 瀚润特环保设备（江苏）有限公司 | A kind of environmental protection dual transformer type zero current resonance three-level DC converter |
| CN108631604B (en) * | 2018-05-28 | 2020-06-16 | 瀚润特环保设备（江苏）有限公司 | Environment-friendly double-transformer type zero-current resonance three-level direct current converter |
| CN111934576A (en) * | 2020-04-16 | 2020-11-13 | 山西大学 | Auxiliary resonance converter pole inverter with phase-correlated magnetizing current symmetric reset |
| CN112234829A (en) * | 2020-09-27 | 2021-01-15 | 陕西航空电气有限责任公司 | Soft switching circuit of phase-shifted full-bridge converter |
| CN114006535A (en) * | 2021-10-21 | 2022-02-01 | 福州大学 | Novel bidirectional three-level current-doubling LCL-T resonant converter circuit |
| CN114006535B (en) * | 2021-10-21 | 2024-03-29 | 福州大学 | Bidirectional three-level current-doubling LCL-T resonant converter circuit |
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|---|---|
| CN100539374C (en) | 2009-09-09 |
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