CN113708678B - Magnetic damping control method based on harmonic generator - Google Patents
Magnetic damping control method based on harmonic generator Download PDFInfo
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- CN113708678B CN113708678B CN202010435459.XA CN202010435459A CN113708678B CN 113708678 B CN113708678 B CN 113708678B CN 202010435459 A CN202010435459 A CN 202010435459A CN 113708678 B CN113708678 B CN 113708678B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
- H02P9/14—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of field
- H02P9/26—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of field using discharge tubes or semiconductor devices
- H02P9/30—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of field using discharge tubes or semiconductor devices using semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P9/00—Arrangements for controlling electric generators for the purpose of obtaining a desired output
- H02P9/40—Arrangements for controlling electric generators for the purpose of obtaining a desired output by variation of reluctance of magnetic circuit of generator
Abstract
The application relates to the technical field of magnetic damping control, and discloses a magnetic damping control method based on a harmonic generator. The method comprises the following steps: rectifying alternating current of the harmonic generator into direct current by utilizing a three-phase four-bridge arm converter; the energy storage unit is used for storing direct current through a capacitor; collecting the current of each phase collecting coil of the harmonic generator by using a current sampler; calculating the zero sequence current value of each phase according to the collected current of each phase collector coil; obtaining a zero sequence voltage command value of each phase through PI control according to the zero sequence current value of each phase and the zero sequence current command value of each phase; obtaining PWM converter modulation waves according to the zero sequence voltage command values of the phases and the power generation control voltage command values of the harmonic generator of the phases; PWM modulation is carried out on the modulated wave to generate PWM wave; the power stored in the energy storage unit is converted into zero sequence current damping control values of each phase through the on-off of the PWM wave control power electronic switching device, and the zero sequence current damping control values of each phase are injected into the collecting coils of each phase to realize magnetic damping control.
Description
Technical Field
The application relates to the technical field of magnetic damping control, in particular to a magnetic damping control method based on a harmonic generator.
Background
The superconducting electric suspension type magnetic suspension train generates a strong magnetic field through a vehicle-mounted superconductor, and generates propulsion, suspension and guiding forces through interaction with a ground coil. The superconducting suspension technology has the advantages that: 1. the suspension height is large and is generally more than 100 mm; 2. the suspension does not need global control; 3. the outside is powered off, so long as the speed is available, the vehicle can not suddenly lose the levitation force; 4. no on-board excitation power supply is needed; 5. the superconducting coil is hollow and has light weight. The superconducting levitation technology is suitable for high-speed magnetic levitation because of the advantages.
Since the levitation characteristic of this levitation technology is a negative damping characteristic, in order to reduce vibration during train traveling, it is necessary to install a damping coil, and control an inverter to inject a control current into the damping coil by a control algorithm to generate attractive force and repulsive force in the damping coil, and further generate damping force to reduce vibration during train traveling.
The Japanese sorbitol test line adopts the mode that zero sequence current is injected into a collector coil through a power generation PWM converter to realize the magnetic damping function, so that the negative damping characteristic of superconducting electric levitation is improved, and the power generation and the magnetic damping functions are realized simultaneously through a harmonic generator power generation coil and the PWM converter. The zero sequence currents are all currents which are not related to three phases in the three phases, and the current amounts are obtained by summing and averaging the three-phase balance currents. In the japanese sorbitol test line, in the control magnetic damping control strategy (as shown in fig. 1), the zero sequence current value (the current independent of the power of each phase, obtained by the average value of the current of each phase) is obtained by taking the sampled current of the three-phase collector coil into the following formula.
Then pass through zero sequence current I 0 With a zero sequence current command value obtained by a vehicle body state operationAnd comparing, controlling through PI, outputting a voltage signal of zero sequence control, and adding the voltage signal of each phase output by the harmonic generation controller to obtain a PWM converter output voltage modulation wave.
When the three phases are balanced, the existing control strategy in Japan can meet the magnetic damping control requirement, but when the collector coil generates counter potential three-phase unbalance, the three-phase current can be in the same phase with the counter potential of the three-phase collector coil in order to ensure the high internal power factor output energy of the collector coil due to the control effect of the harmonic generation controller, so that the three-phase current of the collector coil at the moment is three-phase unbalanced current, and the actual zero sequence current value of each phase cannot be obtained through the formula (1), namely, the magnetic damping control during the three-phase unbalance cannot be performed.
Disclosure of Invention
The application provides a magnetic damping control method based on a harmonic generator, which can solve the problems in the prior art.
The application provides a magnetic damping control method based on a harmonic generator, wherein the method comprises the following steps:
rectifying alternating current of a harmonic generator into direct current by utilizing a three-phase four-leg converter, wherein a converter U-phase leg, a converter V-phase leg and a converter W-phase leg of the three-phase four-leg converter are respectively connected with a U-phase collecting coil, a V-phase collecting coil and a W-phase collecting coil of the harmonic generator, a converter N-phase leg of the three-phase four-leg converter is connected with a neutral point of the harmonic generator, and the converter U-phase leg, the converter V-phase leg, the converter W-phase leg and the converter N-phase leg of the three-phase four-leg converter all comprise power electronic devices and diodes which are reversely connected in parallel with the power electronic devices;
the direct current is stored by an energy storage unit through a capacitor, and the capacitor and the energy storage unit are connected in parallel to the output side of the three-phase four-bridge arm converter;
collecting the current of each phase collecting coil of the harmonic generator by using a current sampler, wherein the current sampler is arranged between the harmonic generator and the three-phase four-bridge arm converter;
calculating the zero sequence current value of each phase according to the collected current of each phase collector coil;
obtaining a zero sequence voltage command value of each phase through PI control according to the zero sequence current value of each phase and the zero sequence current command value of each phase;
obtaining PWM converter modulation waves according to the zero sequence voltage command values of the phases and the power generation control voltage command values of the harmonic generator of the phases;
PWM modulation is carried out on the modulation wave to generate a PWM wave;
and the PWM waves control the power electronic switching device to be turned on and off, the electric energy stored in the energy storage unit is converted into zero sequence current damping control values of all phases, and the zero sequence current damping control values of all phases are injected into the collector coils of all phases, so that the magnetic damping control is realized.
Preferably, calculating the zero sequence current value of each phase according to the collected current of each phase collector coil comprises:
establishing a virtual three-phase balance current of a U phase by taking the current of the U phase collector coil as a reference, establishing a virtual three-phase balance current of a V phase by taking the current of the V phase collector coil as a reference, and establishing a virtual three-phase balance current of a W phase by taking the current of the W phase collector coil as a reference;
and calculating a U-phase zero-sequence current value according to the virtual three-phase balance current of the U-phase, calculating a V-phase zero-sequence current value according to the virtual three-phase balance current of the V-phase, and calculating a W-phase zero-sequence current value according to the virtual three-phase balance current of the W-phase.
Preferably, the U-phase zero sequence current value is calculated from the virtual three-phase balance current of the U-phase by:
wherein I is u0 For the U-phase zero sequence current value, I ua Balance current for virtual a phase of U phase, I ub Balance current for virtual b phase of U phase, I uc Balancing current for virtual c-phase of the U-phase;
calculating a V-phase zero-sequence current value according to the virtual three-phase balance current of the V phase by the following steps:
wherein I is v0 For the V-phase zero sequence current value, I va Balance current for virtual a phase of V phase, I vb Balance current for virtual b phase of V phase, I vc Virtual c-phase leveling for V-phaseBalance current;
calculating a W-phase zero-sequence current value according to the virtual three-phase balance current of the W phase by the following steps:
wherein I is w0 For the W phase zero sequence current value, I wa Balance current for virtual a phase of W phase, I wb Balance current for virtual b phase of W phase, I wc The current is balanced for the virtual c-phase of the W-phase.
Preferably, obtaining the zero sequence voltage command value of each phase through PI control according to the zero sequence current value of each phase and the zero sequence current command value of each phase includes:
subtracting the zero sequence current value of each phase from the zero sequence current instruction value of each phase according to the phase to obtain corresponding difference values;
and (3) obtaining the zero sequence voltage command value of each phase by PI control on each corresponding difference value.
Preferably, obtaining the PWM converter modulation wave according to the zero sequence voltage command value of each phase and the generation control voltage command value of each phase of the harmonic generator includes:
and adding the zero sequence voltage command values of all phases and the power generation control voltage command values of all phases of the harmonic generator according to the phases to obtain PWM converter modulation waves.
Preferably, PWM modulating the modulated wave to generate a PWM wave includes:
and comparing the modulated wave with a carrier wave to generate a PWM wave.
Preferably, the carrier wave is a triangular wave.
Through the technical scheme, the magnetic damping control and the non-contact power supply can be realized simultaneously by utilizing the harmonic generator and the current transformer, and the damping controller is matched without additionally adding a damping coil; and for counter electromotive force generated by the harmonic generator, the application can realize effective magnetic damping control under three-phase balance and three-phase unbalance.
Drawings
The accompanying drawings, which are included to provide a further understanding of embodiments of the application and are incorporated in and constitute a part of this specification, illustrate embodiments of the application and together with the description serve to explain the principles of the application. It is evident that the drawings in the following description are only some embodiments of the present application and that other drawings may be obtained from these drawings without inventive effort for a person of ordinary skill in the art.
FIG. 1 shows a schematic diagram of a prior art magnetic damping control strategy;
FIG. 2 illustrates a flow chart of a method of magnetic damping control based on a harmonic generator in accordance with one embodiment of the application;
FIG. 3 illustrates a schematic diagram of a harmonic generation converter based on a harmonic generator in accordance with an embodiment of the application;
FIG. 4 shows a schematic diagram of a magnetic damping control strategy according to one embodiment of the application.
Detailed Description
It should be noted that, without conflict, the embodiments of the present application and features of the embodiments may be combined with each other. The following description of the embodiments of the present application will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present application, but not all embodiments. The following description of at least one exemplary embodiment is merely exemplary in nature and is in no way intended to limit the application, its application, or uses. All other embodiments, which can be made by those skilled in the art based on the embodiments of the application without making any inventive effort, are intended to be within the scope of the application.
It is noted that the terminology used herein is for the purpose of describing particular embodiments only and is not intended to be limiting of exemplary embodiments according to the present application. As used herein, the singular is also intended to include the plural unless the context clearly indicates otherwise, and furthermore, it is to be understood that the terms "comprises" and/or "comprising" when used in this specification are taken to specify the presence of stated features, steps, operations, devices, components, and/or combinations thereof.
The relative arrangement of the components and steps, numerical expressions and numerical values set forth in these embodiments do not limit the scope of the present application unless it is specifically stated otherwise. Meanwhile, it should be understood that the sizes of the respective parts shown in the drawings are not drawn in actual scale for convenience of description. Techniques, methods, and apparatus known to one of ordinary skill in the relevant art may not be discussed in detail, but should be considered part of the specification where appropriate. In all examples shown and discussed herein, any specific values should be construed as merely illustrative, and not a limitation. Thus, other examples of the exemplary embodiments may have different values. It should be noted that: like reference numerals and letters denote like items in the following figures, and thus once an item is defined in one figure, no further discussion thereof is necessary in subsequent figures.
Fig. 2 shows a flow chart of a method of controlling magnetic damping based on a harmonic generator according to an embodiment of the application.
For example, the method may be applied to magnetic damping control of a magnetic levitation train.
Fig. 3 shows a schematic diagram of a harmonic generation converter based on a harmonic generator according to an embodiment of the application.
As shown in fig. 2, an embodiment of the present application provides a magnetic damping control method based on a harmonic generator, wherein the method includes:
s100, utilizing a three-phase four-bridge arm converter to rectify alternating current of a harmonic generator into direct current,
as shown in fig. 3, a converter U-phase bridge arm 3, a converter V-phase bridge arm 4, and a converter W-phase bridge arm 5 of the three-phase four-bridge arm converter (PWM converter) are respectively connected with a U-phase collector coil, a V-phase collector coil, and a W-phase collector coil of the harmonic generator 1, a converter N-phase bridge arm 6 of the three-phase four-bridge arm converter is connected with a neutral point of the harmonic generator, and the converter U-phase bridge arm, the converter V-phase bridge arm, the converter W-phase bridge arm, and the converter N-phase bridge arm all include a power electronic device 2 and a diode connected in anti-parallel with the power electronic device 2;
wherein, the connecting line between the converter N-phase bridge arm 6 of the three-phase four-bridge arm converter and the neutral point of the harmonic generator forms a neutral line 10. Each phase leg may comprise two power electronics 2 and two diodes, one diode being connected in anti-parallel to each power electronics 2.
For example, harmonic generator-based harmonic generation converters including three-phase four-leg converters and harmonic generators may be used to achieve non-contact power supply for a magnetic levitation train.
S102, an energy storage unit is used for storing the direct current through a capacitor, and the capacitor 7 and the energy storage unit 8 are connected in parallel to the output side (direct current side) of the three-phase four-bridge arm converter, as shown in FIG. 3;
that is, the ac side of the three-phase four-leg converter is three-phase ac independent from each other, and the dc side has 1 dc power supply (energy storage unit).
S104, collecting the current of each phase of collector coil of the harmonic generator by using a current sampler, wherein the current sampler 11 is arranged between the harmonic generator 1 and the three-phase four-bridge arm converter, as shown in FIG. 3;
for example, a current sampler 11 may be disposed between the U-phase bridge arm 3 and the U-phase collector coil of the current transformer for collecting the current of the U-phase collector coil, a current sampler 11 may be disposed between the V-phase bridge arm 4 and the V-phase collector coil for collecting the current of the V-phase collector coil, and a current sampler 11 may be disposed between the W-phase bridge arm 5 and the W-phase collector coil of the current transformer for collecting the current of the W-phase collector coil.
S106, calculating zero sequence current values of all phases according to the collected currents of all phases of collector coils;
s108, obtaining a zero sequence voltage command value of each phase through PI control according to the zero sequence current value of each phase and the zero sequence current command value of each phase;
the zero sequence current command value of each phase can be calculated in advance based on, for example, a measured value of a vehicle body vibration sensor (for example, a speed sensor, an acceleration sensor, or a position sensor).
S110, obtaining PWM converter modulation waves according to the zero sequence voltage command values of all phases and the power generation control voltage command values of all phases of the harmonic generator;
the power generation control voltage command value of each phase of the harmonic generator can be obtained through an existing power generation control strategy (power generation control algorithm), and the application is not limited to this.
S112, PWM modulation is carried out on the modulation wave to generate a PWM wave;
s114, the power electronic switching device is controlled to be turned on and off through the PWM wave, electric energy stored in the energy storage unit is converted into zero sequence current damping control values of all phases, and the zero sequence current damping control values of all phases are injected into the collector coils of all phases, so that magnetic damping control is realized.
Through the technical scheme, the magnetic damping control and the non-contact power supply (for example, the non-contact power supply is carried out on the vehicle-mounted electric equipment of the magnetic suspension train) can be simultaneously realized by utilizing the harmonic generator and the converter, and a damping coil is not required to be additionally added, namely, a damping controller is matched; and for counter electromotive force generated by the harmonic generator, the application can realize effective magnetic damping control under three-phase balance and three-phase unbalance.
That is, the present application is applicable not only to an ac-side three-phase balanced power supply but also to control of a three-phase unbalanced power supply. And the three-phase four-bridge arm converter can be adopted to rectify the electric energy generated by the harmonic generator, and the converter is used for rectifying the alternating current with the frequency and amplitude changing along with the change of the vehicle speed generated by the harmonic generator into direct current to supply power for the vehicle-mounted electric load (connected with the energy storage unit in parallel) 9.
With continued reference to fig. 3, the circuit shown in fig. 3 may include a U-phase bridge arm, a V-phase bridge arm, a W-phase bridge arm, and an N-phase bridge arm, respectively sample three-phase currents, respectively and individually control three phases, and simultaneously, by controlling the N-phase bridge arm, the sum of three-phase unbalanced currents and three-phase zero-sequence currents may flow through the N-phase communication path, so as to implement zero-sequence current control under three-phase unbalanced conditions.
As shown in fig. 3, the collector coils of each phase of the harmonic generator 1 may adopt a star connection mode.
Wherein the power electronic device 2 is an insulated gate transistor IGBT or a metal oxide semiconductor field effect transistor MOSFET. For example, the MOSFET may be a SiC-MOSFET (silicon carbide MOSFET). The energy storage unit 9 may be a battery pack.
It will be appreciated by persons skilled in the art that the above description of the power electronics 2 is merely exemplary and is not intended to limit the present application.
According to one embodiment of the application, calculating the zero sequence current value of each phase according to the collected current of each phase collector coil comprises:
establishing a virtual three-phase balance current of a U phase by taking the current of the U phase collector coil as a reference, establishing a virtual three-phase balance current of a V phase by taking the current of the V phase collector coil as a reference, and establishing a virtual three-phase balance current of a W phase by taking the current of the W phase collector coil as a reference;
and calculating a U-phase zero-sequence current value according to the virtual three-phase balance current of the U-phase, calculating a V-phase zero-sequence current value according to the virtual three-phase balance current of the V-phase, and calculating a W-phase zero-sequence current value according to the virtual three-phase balance current of the W-phase.
In accordance with one embodiment of the present application,
calculating a U-phase zero-sequence current value according to the virtual three-phase balance current of the U phase by the following steps:
wherein I is u0 For the U-phase zero sequence current value, I ua Balance current for virtual a phase of U phase, I ub Balance current for virtual b phase of U phase, I uc Balancing current for virtual c-phase of the U-phase;
calculating a V-phase zero-sequence current value according to the virtual three-phase balance current of the V phase by the following steps:
wherein I is v0 For the V-phase zero sequence current value, I va Balance current for virtual a phase of V phase, I vb Balance current for virtual b phase of V phase, I vc Balancing current for virtual c-phase of V-phase;
calculating a W-phase zero-sequence current value according to the virtual three-phase balance current of the W phase by the following steps:
wherein I is w0 For the W phase zero sequence current value, I wa Balance current for virtual a phase of W phase, I wb Balance current for virtual b phase of W phase, I wc The current is balanced for the virtual c-phase of the W-phase.
According to one embodiment of the present application, obtaining the zero sequence voltage command value of each phase through PI control according to the zero sequence current value of each phase and the zero sequence current command value of each phase includes:
subtracting the zero sequence current value of each phase from the zero sequence current instruction value of each phase according to the phase to obtain corresponding difference values;
and (3) obtaining the zero sequence voltage command value of each phase by PI control on each corresponding difference value.
According to one embodiment of the present application, obtaining a PWM converter modulation wave according to each phase zero sequence voltage command value and each phase power generation control voltage command value of a harmonic generator includes:
and adding the zero sequence voltage command values of all phases and the power generation control voltage command values of all phases of the harmonic generator according to the phases to obtain PWM converter modulation waves.
According to an embodiment of the present application, PWM modulating the modulated wave to generate a PWM wave includes:
and comparing the modulated wave with a carrier wave to generate a PWM wave.
Wherein, the carrier wave can be triangular wave.
FIG. 4 shows a schematic diagram of a magnetic damping control strategy according to one embodiment of the application.
As shown in fig. 4, by sampling a three-phase unbalanced current (I u ，I v ，I w ) Each of the three phases is calculated by performing calculation, and a three-phase balance current (U-phase: i ua ，I ub ，I uc The method comprises the steps of carrying out a first treatment on the surface of the V phase: i va ，I vb ，I vc The method comprises the steps of carrying out a first treatment on the surface of the W phase: i wa ，I wb ，I wc The method comprises the steps of carrying out a first treatment on the surface of the ) Then the zero sequence current value (I) of each phase of the three phases is calculated in real time through the formulas (2), (3) and (4) u0 ；I v0 ；I w0 ) And respectively with the zero sequence current command value (I 0_ref ) Calculating the difference, and then respectively generating three-phase zero sequence voltage command values through a PI controllerThen the generated zero sequence voltage command value and each phase of power generation control voltage command value generated by a harmonic generator power generation control algorithm are combinedThe PWM modulated waves are obtained by addition.
The generation of the power generation control voltage command value for each phase of the harmonic generator can be performed, for example, as follows: the current collected by the current sampler 11 can be used as a control quantity to participate in control, the output voltage required when the requirements of high power factor and output power are met can be obtained based on the control quantity and a corresponding control strategy, PWM waves can be obtained by comparing the output voltage with carrier waves (triangular waves) as modulation waves, and the power electronic devices are controlled to be turned on and off through the PWM waves, so that the output voltage of the alternating current side of the three-phase four-bridge arm converter is controlled, and therefore the U phase, the V phase and the W phase of the three-phase four-bridge arm converter are respectively equivalent to a controllable three-phase alternating current power supply. That is, high power factor on the ac side and meeting the output power requirement on the dc side can be achieved by the corresponding control algorithm.
It will be appreciated by those skilled in the art that while the above embodiments of the present application have been described in terms of three phases only, they are merely exemplary and not intended to limit the present application. For example, for four equal more phases, either three-phase balancing or three-phase imbalance is equally applicable.
From the above embodiments, it can be seen that the harmonic generator controls the PWM converter according to the power generation control algorithm to complete the power generation function of the harmonic generator, rectifies the ac power generated by each collector coil of the harmonic generator into dc power, charges the dc power, and flows the power flow from the ac side to the dc power. Therefore, non-contact power supply to the electric equipment can be realized. The zero sequence current control algorithm controls the PWM converter to complete the magnetic damping function, electric energy of the direct current power supply is converted into zero sequence current which is respectively injected into each collector coil of the harmonic generator, damping force is generated on the collector coils through zero sequence current injection, so that damping control is achieved, and power flows from the direct current power supply to the harmonic generator. Therefore, the acquisition of the zero sequence current of each phase can be realized under the three-phase imbalance of the harmonic generator, and the zero sequence current injection is carried out to realize the magnetic damping function.
The harmonic generator is connected with the power supply device, and the power supply device is connected with the power supply device.
In the description of the present application, it should be understood that the azimuth or positional relationships indicated by the azimuth terms such as "front, rear, upper, lower, left, right", "lateral, vertical, horizontal", and "top, bottom", etc., are generally based on the azimuth or positional relationships shown in the drawings, merely to facilitate description of the present application and simplify the description, and these azimuth terms do not indicate and imply that the apparatus or elements referred to must have a specific azimuth or be constructed and operated in a specific azimuth, and thus should not be construed as limiting the scope of protection of the present application; the orientation word "inner and outer" refers to inner and outer relative to the contour of the respective component itself.
Spatially relative terms, such as "above … …," "above … …," "upper surface at … …," "above," and the like, may be used herein for ease of description to describe one device or feature's spatial location relative to another device or feature as illustrated in the figures. It will be understood that the spatially relative terms are intended to encompass different orientations in use or operation in addition to the orientation depicted in the figures. For example, if the device in the figures is turned over, elements described as "above" or "over" other devices or structures would then be oriented "below" or "beneath" the other devices or structures. Thus, the exemplary term "above … …" may include both orientations of "above … …" and "below … …". The device may also be positioned in other different ways (rotated 90 degrees or at other orientations) and the spatially relative descriptors used herein interpreted accordingly.
In addition, the terms "first", "second", etc. are used to define the components, and are only for convenience of distinguishing the corresponding components, and the terms have no special meaning unless otherwise stated, and therefore should not be construed as limiting the scope of the present application.
The above description is only of the preferred embodiments of the present application and is not intended to limit the present application, but various modifications and variations can be made to the present application by those skilled in the art. Any modification, equivalent replacement, improvement, etc. made within the spirit and principle of the present application should be included in the protection scope of the present application.
Claims (7)
1. A method for controlling magnetic damping based on a harmonic generator, the method comprising:
rectifying alternating current of a harmonic generator into direct current by utilizing a three-phase four-leg converter, wherein a converter U-phase leg, a converter V-phase leg and a converter W-phase leg of the three-phase four-leg converter are respectively connected with a U-phase collecting coil, a V-phase collecting coil and a W-phase collecting coil of the harmonic generator, a converter N-phase leg of the three-phase four-leg converter is connected with a neutral point of the harmonic generator, and the converter U-phase leg, the converter V-phase leg, the converter W-phase leg and the converter N-phase leg of the three-phase four-leg converter all comprise power electronic devices and diodes which are reversely connected in parallel with the power electronic devices;
the direct current is stored by an energy storage unit through a capacitor, and the capacitor and the energy storage unit are connected in parallel to the output side of the three-phase four-bridge arm converter;
collecting the current of each phase collecting coil of the harmonic generator by using a current sampler, wherein the current sampler is arranged between the harmonic generator and the three-phase four-bridge arm converter;
calculating the zero sequence current value of each phase according to the collected current of each phase collector coil;
obtaining a zero sequence voltage command value of each phase through PI control according to the zero sequence current value of each phase and the zero sequence current command value of each phase;
obtaining PWM converter modulation waves according to the zero sequence voltage command values of the phases and the power generation control voltage command values of the harmonic generator of the phases;
PWM modulation is carried out on the modulation wave to generate a PWM wave;
and the PWM waves control the power electronic switching device to be turned on and off, the electric energy stored in the energy storage unit is converted into zero sequence current damping control values of all phases, and the zero sequence current damping control values of all phases are injected into the collector coils of all phases, so that the magnetic damping control is realized.
2. The method of claim 1, wherein calculating the phase zero sequence current values from the collected phase collector coil currents comprises:
establishing a virtual three-phase balance current of a U phase by taking the current of the U phase collector coil as a reference, establishing a virtual three-phase balance current of a V phase by taking the current of the V phase collector coil as a reference, and establishing a virtual three-phase balance current of a W phase by taking the current of the W phase collector coil as a reference;
and calculating a U-phase zero-sequence current value according to the virtual three-phase balance current of the U-phase, calculating a V-phase zero-sequence current value according to the virtual three-phase balance current of the V-phase, and calculating a W-phase zero-sequence current value according to the virtual three-phase balance current of the W-phase.
3. The method of claim 2, wherein the step of determining the position of the substrate comprises,
calculating a U-phase zero-sequence current value according to the virtual three-phase balance current of the U phase by the following steps:
wherein I is u0 For the U-phase zero sequence current value, I ua Balance current for virtual a phase of U phase, I ub Balance current for virtual b phase of U phase, I uc Balancing current for virtual c-phase of the U-phase;
calculating a V-phase zero-sequence current value according to the virtual three-phase balance current of the V phase by the following steps:
wherein I is v0 For the V-phase zero sequence current value, I va Balance current for virtual a phase of V phase, I vb Balance current for virtual b phase of V phase, I vc Balancing current for virtual c-phase of V-phase;
calculating a W-phase zero-sequence current value according to the virtual three-phase balance current of the W phase by the following steps:
wherein I is w0 For the W phase zero sequence current value, I wa Balance current for virtual a phase of W phase, I wb Balance current for virtual b phase of W phase, I wc The current is balanced for the virtual c-phase of the W-phase.
4. A method according to claim 3, characterized in that deriving the phase zero sequence voltage command value by PI control from the phase zero sequence current value and the phase zero sequence current command value comprises:
subtracting the zero sequence current value of each phase from the zero sequence current instruction value of each phase according to the phase to obtain corresponding difference values;
and (3) obtaining the zero sequence voltage command value of each phase by PI control on each corresponding difference value.
5. The method of claim 4, wherein deriving the PWM converter modulation wave from the zero sequence voltage command value for each phase and the generation control voltage command value for each phase of the harmonic generator comprises:
and adding the zero sequence voltage command values of all phases and the power generation control voltage command values of all phases of the harmonic generator according to the phases to obtain PWM converter modulation waves.
6. The method of claim 5, wherein PWM modulating the modulated wave to generate a PWM wave comprises:
and comparing the modulated wave with a carrier wave to generate a PWM wave.
7. The method of claim 6, wherein the carrier wave is a triangular wave.
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| CN109861564A (en) * | 2019-01-10 | 2019-06-07 | 中国电力科学研究院有限公司 | A kind of energy storage load net-side rectifier voltage balance control method and system |
| WO2019136784A1 (en) * | 2018-01-11 | 2019-07-18 | 江苏大学 | One-phase open-circuit fault-tolerant direct thrust control method for five-phase permanent magnet linear motor |
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| WO2019136784A1 (en) * | 2018-01-11 | 2019-07-18 | 江苏大学 | One-phase open-circuit fault-tolerant direct thrust control method for five-phase permanent magnet linear motor |
| CN109861564A (en) * | 2019-01-10 | 2019-06-07 | 中国电力科学研究院有限公司 | A kind of energy storage load net-side rectifier voltage balance control method and system |
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