CN112986653B - Modular multi-cascade NIBB (network interface bus) based inductor current average value sampling filtering method - Google Patents

Modular multi-cascade NIBB (network interface bus) based inductor current average value sampling filtering method Download PDF

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CN112986653B
CN112986653B CN202110167262.7A CN202110167262A CN112986653B CN 112986653 B CN112986653 B CN 112986653B CN 202110167262 A CN202110167262 A CN 202110167262A CN 112986653 B CN112986653 B CN 112986653B
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CN112986653A (en
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翁幸
赵争鸣
陈凯楠
袁立强
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Tsinghua University
State Grid Hubei Electric Power Co Ltd
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Abstract

The invention discloses an inductance current average value sampling filtering method of a modular multi-cascade NIBB (network interface bus) converter, belonging to the technical field of sampling filtering of DC-DC converters. The method comprises the following steps: judging a current modulation mode according to the duty ratio and the phase shift ratio of each non-reverse Buck-Boost circuit through a modulation mode judging module; the accurate calculation module of the inductive current sampling moment is designed according to a mathematical model of the non-reverse Buck-Boost circuit and a current modulation mode; and the inductive current sampling value filtering and dead pixel eliminating module is designed according to the current modulation mode of the non-reverse Buck-Boost circuit. Therefore, the control method can improve the sampling accuracy of the average value of the inductive current of the modularized multi-parallel non-reverse Buck-Boost circuit, thereby improving the control performance of the converter.

Description

Modular multi-cascade NIBB (network interface bus) based inductor current average value sampling filtering method
Technical Field
The invention relates to the technical field of sampling and filtering of DC-DC converters, in particular to an inductive current average value sampling and filtering method of a modular multi-cascade NIBB.
Background
A non-inverting Buck-Boost converter (NIBB) is a non-isolated DC-DC converter capable of realizing DC voltage up-down conversion, and has been applied to occasions such as an electric vehicle charging system, a photovoltaic power generation grid-connected system, an uninterruptible power supply system, and a power factor correction converter. FIG. 1 is a schematic diagram of the NIBB circuit topology. Setting a switching tube Q in a bridge arm at the input end of the converter (hereinafter referred to as a Buck bridge arm)1Duty ratio of d1(ii) a Switching tube Q in converter output end bridge arm (hereinafter referred to as Boost bridge arm)3Duty ratio of d2(ii) a Switch tube Q1Leading switch tube Q3Has a shift ratio of d3. With the difference of duty ratio combination and shift ratio of the Buck bridge arm and the Boost bridge arm, the NIBB circuit has a plurality of different modulation modes, and the inductive current of the NIBB circuit also has different waveforms. In practical application, the NIBB circuit is often operated in the switching tube Q in consideration of efficiency and electrical stress1Rising edge of and Q3Rising edge of (2) aligning or switching the transistor Q1Falling edge of and Q3And a modulation pattern such that the falling edges of the two pulses are aligned and the duty cycle d is made to be1、d2As large as possible as shown in fig. 2,3,4, 5.
In a large-capacity electric energy conversion system, a structure of a modular multi-parallel NIBB converter as shown in fig. 6 is often adopted; in order to reduce the volume of passive components and improve the power density, the carrier stacking or carrier phase-shifting control mode is also adopted to reduce the total output ripple of the system. This makes the inductance current ripple of each NIBB circuit module relatively large with respect to its average value, and the inductance current value obtained by sampling varies greatly with the sampling time. The conventional sampling method is relatively random in sampling time selection, the average value of the inductive current of each NIBB circuit module is difficult to accurately obtain, and the control of each module and the voltage-sharing and power-sharing control among a plurality of cascade modules are not facilitated. In addition, at the moment of and for a period of time after the switching action of the power semiconductor device, the switching process of the power semiconductor device generates large electromagnetic interference to the sampling circuit, which affects the sampling precision and even causes dead spots. The conventional sampling method cannot ensure that the sampling point always avoids the switching action moment of the power semiconductor, and may cause serious sampling error of the average value of the inductive current.
Aiming at the problems of poor sampling precision, easy electromagnetic interference in the switching process and the like existing in the prior art when the average value of the inductance current of the modular multi-parallel non-reverse Buck-Boost converter is sampled, an effective solution is not provided at present.
Disclosure of Invention
The invention aims to provide a modular multi-cascade NIBB (network interface bus) inductance current average value sampling filtering method which is characterized in that a mathematical model of a non-reverse Buck-Boost circuit is used for accurately calculating the sampling time of each sub-module inductance current average value, and different dead pixel removing methods are designed according to the modulation mode of the circuit, and the method comprises the following steps:
step 1: through a modulation mode judging module, according to the duty ratio d of the tubes on the Buck bridge arm of each non-reverse Buck-Boost circuit1And the on-bridge-arm duty ratio d of Boost2Phase shift ratio d of Buck bridge arm upper tube leading Boost bridge arm upper tube3Judging the current modulation mode of the non-reverse Buck-Boost circuit;
step 2: calculating the average value sampling time of the inductive current of each non-reverse Buck-Boost circuit submodule through a sampling time calculation module; a sampling moment calculation module designed according to a mathematical model of the non-reverse Buck-Boost circuit and the current modulation mode and based on each d1、d2、d3According to the modulation mode of the current circuit, calculating the sampling time of the average value of the inductive current in a switching period by using different calculation methods;
and step 3: calculating the average value of the inductive current of the period through a sampling value filtering module; and an inductive current sampling value filtering module designed according to the current modulation mode of the non-reverse Buck-Boost circuit calculates the average value of the inductive current in each period by using different filtering and dead pixel removing methods according to the modulation mode of the current circuit based on all sampling values in each switching period.
The method for judging the current modulation mode of the non-inverting Buck-Boost circuit in the step 1 is as follows:
if d is1<d2And d is3If the voltage of the non-reverse Buck-Boost circuit is equal to 0, the non-reverse Buck-Boost circuit is in a voltage reduction trailing edge pulse modulation mode currently;
if d is1≥d2And d is3If the voltage is equal to 0, the non-reverse Buck-Boost circuit is in a Boost trailing edge pulse modulation mode currently;
if d is1<d2And d is3＝1-d2+d1If the Buck-Boost circuit is in the step-down leading edge pulse modulation mode, the non-reverse Buck-Boost circuit is in the step-down leading edge pulse modulation mode;
if d is1≥d2And d is3＝d1-d2If the non-reverse Buck-Boost circuit is in the Boost leading edge pulse modulation mode currently;
if d is1、d2And d3If either of the above conditions is not met, the non-inverting Buck-Boost circuit is currently in a complex modulation mode.
The method for calculating the sampling time of the average value of the inductor current in the step 2 in one switching period is as follows:
(a) if the current circuit is in the pulse modulation mode after voltage reduction, sampling is carried out for 2 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure BDA0002937887830000021
(b) if the current circuit is in the pulse modulation mode after boosting, sampling is carried out for 2 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure BDA0002937887830000022
(c) if the current circuit is in the step-down leading edge pulse modulation mode, sampling is carried out for 2 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure BDA0002937887830000031
(d) if the current circuit is in the boost leading edge pulse modulation mode, sampling is carried out for 2 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure BDA0002937887830000032
(e) if the current circuit is in a complex modulation mode, sampling is carried out for 5 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure BDA0002937887830000033
wherein, TsFor a switching cycle, sampling time tsThe subscript number of (a) represents the sample number of the switching cycle, DminThe shortest time from the receiving of the driving signal of the switching action to the no generation of the excessive electromagnetic interference of the used power semiconductor device; (a) the starting time of the sampling time in the step (b) is the same as the pulse rising edge time of the upper tube of the Buck bridge arm, the starting time of the sampling time in the step (c) is the same as the pulse falling edge time of the upper tube of the Buck bridge arm, and the starting time of the sampling time in the step (e) selects the pulse rising edge or falling edge time of any one power semiconductor device.
The method for calculating the average value of the inductive current in the step 3 is as follows:
if the current circuit is in a buck trailing edge pulse modulation mode or a boost trailing edge pulse modulation mode, the average value I of the inductive currentLThe calculation is performed according to the following expression:
Figure BDA0002937887830000034
if the current circuit is in the buck leading edge pulse modulation mode or the boost leading edge pulse modulation mode, the average value I of the inductive currentLThe calculation is performed according to the following expression:
Figure BDA0002937887830000035
if the current circuit is in a complex modulation mode, the average value of the inductive current ILThe calculation is performed according to the following expression:
Figure BDA0002937887830000041
wherein iL(tsi) I is 1,2,3,4,5, which represents the ith inductor current sampling value in the switching period, ItolFor acceptable inductor current mean sampling error, iLmaxIs the maximum value, i, of all inductor current sampling values in the switching cycleLminThe sampling value is the minimum value of all the inductance current sampling values in the switching period.
The invention has the beneficial effects that:
1. the inductive current sampling time calculation module is designed by using a mathematical model of a non-reverse Buck-Boost circuit, accurately calculates the sampling time of the average value of the inductive current of each submodule, and reduces the sampling times in each switching period under most common modulation modes;
2. the filtering module of the inductive current sampling value is designed according to the modulation mode of the non-reverse Buck-Boost circuit, different modulation modes have different dead pixel removing methods, error sampling data near the action moment of the power semiconductor switch are removed under most common modulation modes, and sampling accuracy is improved.
Drawings
FIG. 1 is a schematic diagram of a single NIBB circuit module topology according to an embodiment of the present invention;
FIG. 2 is a waveform diagram of an NIBB circuit module operating in a buck pulse trailing edge modulation mode;
FIG. 3 is a waveform diagram of an NIBB circuit module operating in a boost pulse trailing edge modulation mode;
FIG. 4 is a waveform schematic diagram of the NIBB circuit block operating in a buck pulse leading edge modulation mode;
FIG. 5 is a waveform diagram of the NIBB circuit module operating in a boost pulse leading edge modulation mode;
FIG. 6 is a schematic diagram of a modular two-parallel NIBB circuit topology according to an embodiment of the present invention;
FIG. 7 is a graph of voltage and current waveforms for a single NIBB circuit block using a conventional 4-fold oversampling averaging method at equal intervals;
FIG. 8 shows the voltage and current waveforms of a single NIBB circuit module when the sampling filtering method of the present invention is applied.
Detailed Description
The invention provides a modular multi-cascade NIBB (network interface bus) inductor current average value sampling filtering method, which is further explained by combining the attached drawings and specific embodiments.
Figure 1 is a single NIBB circuit that is one sub-module of the two parallel NIBB circuits shown in figure 6. The topological structure of a single NIBB circuit is formed by connecting a group of Buck bridge arms at an input end and a group of Boost bridge arms at an output end through an inductor L, and the circuit is provided with a filter capacitor at the input end and the output end respectively. The following describes an embodiment of the present invention in detail by taking an example of an average current sampling method of the inductance L of the submodule.
Analyzing different modulation modes of NIBB circuit
Defining the duty ratio of a tube on a Buck bridge arm of an NIBB circuit as d1And the duty ratio of the upper tube of the bridge arm of the Boost is d2The phase shift ratio of the Buck bridge arm upper pipe leading the Boost bridge arm upper pipe is d3. Under steady state conditions, the output voltage, the input voltage and the two duty cycles of the NIBB circuit have the following relationship:
Figure BDA0002937887830000051
according to the relationship between the duty ratio and the phase shift ratio, the modulation modes of the NIBB circuit can be divided into the following modes:
1. voltage-reduced back porch pulse modulation mode
If d is1<d2And d is30, i.e. Q1Tube and Q3The rising edges of the tubes are aligned, the DC conversion ratio and the inductor current waveform of the NIBB circuit are changed by modulating the falling edge time of the tubes, the output voltage is smaller than the input voltage, the circuit is in a buck trailing edge pulse modulation mode, and the inductor current waveform in the mode is shown in FIG. 2.
2. Back porch pulse modulation mode after boosting
If d is1≥d2And d is30, i.e. Q1Tube and Q3The rising edges of the tubes are aligned, the DC conversion ratio and the inductor current waveform of the NIBB circuit are changed by modulating the falling edge time of the tubes, the output voltage is larger than the input voltage, the circuit is in a boost trailing edge pulse modulation mode, and the inductor current waveform in the mode is shown in FIG. 3.
3. Reduced voltage leading edge pulse modulation mode
If d is1<d2And d is3＝1-d2+d1I.e. Q1Tube and Q3The falling edges of the tubes are aligned, the DC conversion ratio and the inductor current waveform of the NIBB circuit are changed by modulating the rising edge time of the tubes, the output voltage is smaller than the input voltage, the circuit is in a step-down leading edge pulse modulation mode, and the inductor current waveform in the mode is shown in FIG. 4.
4. Boosted leading edge pulse modulation mode
If d is1≥d2And d is3＝d1-d2I.e. Q1Tube and Q3The falling edges of the tubes are aligned, the direct current transformation ratio and the inductance current waveform of the NIBB circuit are changed by modulating the rising edge time of the tubes, the output voltage is larger than the input voltage, the non-reverse Buck-Boost circuit is in a Boost leading edge pulse modulation mode, and the inductance current waveform in the mode is shown in figure 5.
5. Complex modulation modes
If d is1、d2And d3Not conforming to any of the above cases, i.e. Q1Tube and Q3And if the rising edge and the falling edge of the tube are not aligned, the non-reverse Buck-Boost circuit is in a complex modulation mode at present. This modulation mode is generally not common due to losses, electrical stress, etc.
Secondly, accurately calculating sampling time
1. Voltage-reduced back porch pulse modulation mode
When the NIBB circuit is in this mode, the analytical expression for the inductor current in one switching cycle can be calculated from fig. 2 as:
Figure BDA0002937887830000061
the average value of the inductance current is:
Figure BDA0002937887830000062
thus when sampling at time tsWhen the mean value can be just acquired, two accurate sampling moments can be calculated, and the expression is as follows:
Figure BDA0002937887830000063
2. back porch pulse modulation mode after boosting
When the NIBB circuit is in this mode, the analytical expression for the inductor current in one switching cycle can be calculated from fig. 3 as:
Figure BDA0002937887830000064
the average value of the inductance current is:
Figure BDA0002937887830000065
thus when sampling at time tsWhen the mean value can be just acquired, two accurate sampling moments can be calculated, and the expression is as follows:
Figure BDA0002937887830000066
3. reduced voltage leading edge pulse modulation mode
When the NIBB circuit is in this mode, the analytical expression for the inductor current in one switching cycle can be calculated from fig. 4 as:
Figure BDA0002937887830000071
the average value of the inductance current is:
Figure BDA0002937887830000072
thus when sampling at time tsWhen the mean value can be just acquired, two accurate sampling moments can be calculated, and the expression is as follows:
Figure BDA0002937887830000073
4. boosted leading edge pulse modulation mode
When the NIBB circuit is in this mode, the analytical expression for the inductor current in one switching cycle can be calculated from fig. 5 as:
Figure BDA0002937887830000074
the average value of the inductance current is:
Figure BDA0002937887830000075
thus when sampling at time tsWhen the mean value can be just acquired, two accurate sampling moments can be calculated, and the expression is as follows:
Figure BDA0002937887830000076
5. complex modulation modes
At this time, because the modulation mode is complex, the accurate sampling time of the average value of the inductive current is difficult to calculate, a method of sampling 5 points and avoiding known switch action points is adopted, and the time of 5 sampling points is as follows:
Figure BDA0002937887830000081
third, designing filtering and asymmetric dead pixel eliminating method according to circuit modulation mode
1. Voltage rising/falling back porch pulse modulation mode
In the modulation mode, 2 sampling points exist, and when the two sampling points have a small difference, the average value of the two sampling points is taken as a final sampling result. When the difference between the two is large, the general NIBB circuit works at d1、d2The larger and the smaller difference between the two states, as can be seen from fig. 2 and 3, t0、t1The first sampling point is far away from the two switching actions before and after, so the sampling time is ts1The result of the inductor current sampling.
2. Step-up/step-down leading edge pulse modulation mode
Similarly, there are 2 sampling points in this modulation mode, and when the two sampling points are not very different, the average value of the two sampling points is taken as the final sampling result. When the difference between the two is large, the general NIBB circuit works at d1、d2The larger and the smaller difference between the two is, as can be seen from fig. 4 and 5, t2、TsThe second sampling point is far away from the two switching actions before and after, so the sampling time is ts2The result of the inductor current sampling.
3. Complex modulation modes
The modulation mode is complex, so that the maximum value and the minimum value of 5 points in each switching period are removed to avoid interference, and the rest 3 sampling points are subjected to arithmetic averaging to serve as the sampling result of the inductive current.
The accurate inductance current average value of the non-reverse Buck-Boost circuit can be obtained through the three steps, and the steps are repeatedly applied to each sub-module circuit in the modularized multi-parallel non-reverse Buck-Boost circuit, so that the inductance current average value sampling filtering method for the modularized multi-parallel non-reverse Buck-Boost circuit can be realized.
Fig. 7 and 8 show a set of comparative experimental results using the sampling filtering method proposed by the present invention. When a sub-module in the modularized multi-parallel non-inverse Buck-Boost circuit works under the working conditions of 350V of input voltage, 400V of output voltage and 19.1A of average inductive current, FIG. 7 shows the input and output voltage and inductive current waveforms of the sub-module when a conventional equal-interval oversampling averaging method is adopted. It can be seen that the waveforms of the output voltage and the inductor current in the figure are seriously distorted due to the interference of the sampling link. Fig. 8 is an experimental waveform of the sub-module when the sub-module operates under the same working condition by using the same closed-loop control strategy and by using the sampling time calculation method provided by the present invention. The output voltage and the inductive current of the controller both show good steady-state characteristics, the number of sampling points is greatly reduced, and the calculation pressure of the controller is reduced.
The present invention is not limited to the above embodiments, and any changes or substitutions that can be easily made by those skilled in the art within the technical scope of the present invention are also within the scope of the present invention. Therefore, the protection scope of the present invention shall be subject to the protection scope of the claims.

Claims (1)

1. The method for sampling and filtering the average value of the inductive current of the modularized multi-cascade non-reverse Buck-Boost converter is characterized in that a mathematical model of a non-reverse Buck-Boost circuit is used for accurately calculating the sampling time of the average value of the inductive current of each sub-module, and different dead pixel removing methods are designed according to the modulation mode of the circuit, and the method comprises the following steps:
step 1: through a modulation mode judging module, according to the duty ratio d of the tubes on the Buck bridge arm of each non-reverse Buck-Boost circuit1And the on-bridge-arm duty ratio d of Boost2Phase shift ratio d of Buck bridge arm upper tube leading Boost bridge arm upper tube3Judging the current modulation mode of the non-reverse Buck-Boost circuit;
the method for judging the current modulation mode of the non-inverting Buck-Boost circuit in the step 1 is as follows:
if d is1<d2And d is3If the voltage of the non-reverse Buck-Boost circuit is equal to 0, the non-reverse Buck-Boost circuit is in a voltage reduction trailing edge pulse modulation mode currently;
if d is1≥d2And d is3If the voltage is equal to 0, the non-reverse Buck-Boost circuit is in a Boost trailing edge pulse modulation mode currently;
if d is1<d2And d is3＝1-d2+d1If the Buck-Boost circuit is in the step-down leading edge pulse modulation mode, the non-reverse Buck-Boost circuit is in the step-down leading edge pulse modulation mode;
if d is1≥d2And d is3＝d1-d2If the non-reverse Buck-Boost circuit is in the Boost leading edge pulse modulation mode currently;
if d is1、d2And d3If the situation is not met, the non-reverse Buck-Boost circuit is in a complex modulation mode currently;
step 2: calculating the average value sampling time of the inductive current of each non-reverse Buck-Boost circuit submodule through a sampling time calculation module; a sampling moment calculation module designed according to a mathematical model of the non-reverse Buck-Boost circuit and the current modulation mode and based on each d1、d2、d3According to the modulation mode of the current circuit, calculating the sampling time of the average value of the inductive current in a switching period by using different calculation methods;
the method for calculating the sampling time of the average value of the inductor current in the step 2 in one switching period is as follows:
(a) if the current circuit is in the pulse modulation mode after voltage reduction, sampling is carried out for 2 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure FDA0003313804950000011
(b) if the current circuit is atIn the boost trailing edge pulse modulation mode, the switching cycle is sampled 2 times, each time at a sampling time tsThe calculation is performed according to the following expressions respectively:
Figure FDA0003313804950000012
(c) if the current circuit is in the step-down leading edge pulse modulation mode, sampling is carried out for 2 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure FDA0003313804950000013
(d) if the current circuit is in the boost leading edge pulse modulation mode, sampling is carried out for 2 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure FDA0003313804950000021
(e) if the current circuit is in a complex modulation mode, sampling is carried out for 5 times in the switching period, and each sampling time tsThe calculation is performed according to the following expressions respectively:
Figure FDA0003313804950000022
wherein, TsFor a switching cycle, sampling time tsThe subscript number of (a) represents the sample number of the switching cycle, DminThe shortest time from the receiving of the driving signal of the switching action to the no generation of the excessive electromagnetic interference of the used power semiconductor device; (a) the initial time of the sampling time in (b) is the same as the pulse rising edge time of the upper tube of the Buck bridge arm, (c) the initial time of the sampling time in (d) is the same as the pulse falling edge time of the upper tube of the Buck bridge arm, and (e) the initial time of the sampling time in (e) is selected from any timeMeaning the pulse rising edge or falling edge time of the power semiconductor device;
and step 3: calculating the average value of the inductive current of the period through a sampling value filtering module; an inductive current sampling value filtering module designed according to the current modulation mode of the non-reverse Buck-Boost circuit calculates the average value of the inductive current in each switching period by using different filtering and dead pixel removing methods according to the modulation mode of the current circuit based on all sampling values in each switching period;
the method for calculating the average value of the inductive current in the step 3 is as follows:
if the current circuit is in a buck trailing edge pulse modulation mode or a boost trailing edge pulse modulation mode, the average value I of the inductive currentLThe calculation is performed according to the following expression:
Figure FDA0003313804950000023
if the current circuit is in the buck leading edge pulse modulation mode or the boost leading edge pulse modulation mode, the average value I of the inductive currentLThe calculation is performed according to the following expression:
Figure FDA0003313804950000024
if the current circuit is in a complex modulation mode, the average value of the inductive current ILThe calculation is performed according to the following expression:
Figure FDA0003313804950000031
wherein iL(tsi) I is 1,2,3,4,5, which represents the ith inductor current sampling value in the switching period, ItolFor acceptable inductor current mean sampling error, iLmaxIs the maximum value, i, of all inductor current sampling values in the switching cycleLminFor all inductor current sampling in the switching cycleThe minimum value among the samples.
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