CN109995264A - Two-way DC-AC converter and its control method - Google Patents

Two-way DC-AC converter and its control method Download PDF

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Publication number
CN109995264A
CN109995264A CN201711474737.7A CN201711474737A CN109995264A CN 109995264 A CN109995264 A CN 109995264A CN 201711474737 A CN201711474737 A CN 201711474737A CN 109995264 A CN109995264 A CN 109995264A
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CN
China
Prior art keywords
switching tube
pulse
width signal
period
mosfet
Prior art date
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Pending
Application number
CN201711474737.7A
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Chinese (zh)
Inventor
江添洋
李晗
冯波
忻慧婷
罗成
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Eaton Manufacturing LP Glasgow succursale de Morges
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Eaton Manufacturing LP Glasgow succursale de Morges
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Application filed by Eaton Manufacturing LP Glasgow succursale de Morges filed Critical Eaton Manufacturing LP Glasgow succursale de Morges
Priority to CN201711474737.7A priority Critical patent/CN109995264A/en
Priority to TW107144080A priority patent/TWI816719B/en
Publication of CN109995264A publication Critical patent/CN109995264A/en
Pending legal-status Critical Current

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/66—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal
    • H02M7/68—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters
    • H02M7/72—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/79—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/797—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0067—Converter structures employing plural converter units, other than for parallel operation of the units on a single load

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Inverter Devices (AREA)
  • Dc-Dc Converters (AREA)
  • Control Of Eletrric Generators (AREA)

Abstract

The present invention provides a kind of two-way DC-AC converter and its control method, the two-way DC-AC converter includes: full-bridge or half-bridge inverter；Transformer, the primary side of the transformer are connected to the exchange end of the full-bridge or half-bridge inverter；There is AC-AC converter the first exchange end exchange end with second, and first exchange end is connected to the secondary side of the transformer, and described second, which exchanges end, is configured as and loads or AC power source is connected；And inductance, it is connected to exchanging between end for the primary side of the transformer and the full-bridge or half-bridge inverter, or be connected to the secondary side of the transformer and exchange between end with the first of the AC-AC converter.Two-way DC-AC converter of the invention improves power density and transfer efficiency, and reduces costs.

Description

Two-way DC-AC converter and its control method
Technical field
The present invention relates to electronic circuit fields, and in particular to a kind of two-way DC-AC converter and its control method.
Background technique
Uninterruptible power supply can be continuously powered to load, have been widely used in every field.
It usually all include DC-DC converter, inverter and charger in existing uninterruptible power supply.Wherein in battery Under mode, the direct current of rechargeable battery is converted to required alternating current by DC-DC converter and inverter；In charge mode Under, charger is for charging to rechargeable battery.
However, existing DC-DC converter, inverter and charger are three independent devices.Between consequently leading to not Power-off source has lower power density, lower efficiency and higher cost.
Summary of the invention
For above-mentioned technical problem of the existing technology, the embodiment provides a kind of two-way DC-AC to convert Device, comprising:
Full-bridge or half-bridge inverter；
Transformer, the primary side of the transformer are connected to the exchange end of the full-bridge or half-bridge inverter；
AC-AC converter, there is the first exchange end to exchange end with second, and first exchange end is connected to the transformation The secondary side of device, second exchange end are configured as and load or AC power source is connected；And
Inductance, the secondary side for being connected to the transformer exchange between end with the first of the AC-AC converter.
Preferably, the AC-AC converter is that the two-way controlled tr tube of two series connections and two are connected in series The half-bridge AC-AC converter that capacitor is constituted, the two-way controlled tr tube of described two series connections are formed by node and described The capacitor of two series connections is formed by node as first exchange end.
Preferably, two of each of two-way controlled tr tube of described two series connections including differential concatenation open Guan Guan.
Preferably, the half-bridge AC-AC converter includes: the 5th switching tube and the 6th switching tube of differential concatenation, and 7th switching tube of differential concatenation and the 8th switching tube；Wherein when the 5th switching tube and the 7th switching tube are controlled as being connected When, the 6th switching tube, the 8th switching tube and two capacitors constitute the first half-bridge inverter, and work as the 6th switching tube When being controlled as conducting with the 8th switching tube, it is inverse that the 5th switching tube, the 7th switching tube and two capacitors constitute the second half-bridge Become device.
Preferably, the AC-AC converter is the full-bridge AC-AC converter that four two-way controlled tr tubes are constituted, described The node of two bridge arms of full-bridge AC-AC converter is as first exchange end.
Preferably, each of described four two-way controlled tr tubes include two switching tubes of differential concatenation.
Preferably, the full-bridge AC-AC converter includes: the 5th switching tube and the 6th switching tube of differential concatenation, reversely Concatenated 7th switching tube and the 8th switching tube, the 9th switching tube of differential concatenation and the tenth switching tube, the tenth of differential concatenation the One switching tube and the 12nd switching tube；Wherein when described five, the seven, the 9th and the 11st switching tube be controlled as conducting when, Described six, the eight, the tenth and the 12nd switching tube constitute the first full-bridge inverter, and work as the six, the eight, the tenth and 12nd switching tube be controlled as conducting when, described five, the seven, the 9th and the 11st switching tube constitute the second full-bridge inverting Device.
Preferably, the two-way DC-AC converter further include be connected to the full-bridge or half-bridge inverter DC terminal it Between filter capacitor.
Preferably, the two-way DC-AC converter further includes control device, is used for: when AC power failure, control The full-bridge or half-bridge inverter are to be converted to the first ac square wave, and the control AC-AC for the direct current of its DC terminal Converter is to be converted to industrial-frequency alternating current for second ac square wave at its first exchange end, wherein first ac square wave and the The period of two ac square waves is the period for being supplied to the pulse-width signal of the full-bridge or half-bridge inverter；When AC power source just Chang Shi controls the AC-AC converter so that the industrial-frequency alternating current at its second exchange end is converted to third ac square wave, and control The full-bridge or half-bridge inverter are made to be exchanged the 4th ac square wave at end and be converted to direct current, the third ac square wave Period with the 4th ac square wave is the period for being supplied to the pulse-width signal of the full-bridge or half-bridge inverter.
The present invention also provides a kind of control method for two-way DC-AC converter as described above, the full-bridge is inverse Becoming device includes the first switch tube and second switch for being connected to its DC terminal in turn, and is connected to the of its DC terminal in turn Three switching tubes and the 4th switching tube, the half-bridge AC-AC converter include: the 5th switching tube and the 6th switch of differential concatenation The 7th switching tube and the 8th switching tube of pipe and differential concatenation；Wherein when the 5th switching tube and the 7th switching tube are controlled When being made as conducting, the 6th switching tube, the 8th switching tube and two capacitors constitute the first half-bridge inverters, and when described the When six switching tubes and the 8th switching tube are controlled as conducting, the 5th switching tube, the 7th switching tube and two capacitors constitute the Two half-bridge inverters, the control method include:
In just half power frequency period, the first switch tube and second switch alternate conduction are controlled, controls the third Switching tube and the 4th switching tube alternate conduction, control the 5th and the 7th switching tube conducting, and control the described 6th and the 8th is opened Close pipe alternate conduction；
In minus half power frequency period, the first switch tube and second switch alternate conduction are controlled, controls the third Switching tube and the 4th switching tube alternate conduction, control the 5th and the 7th switching tube alternate conduction, control the described 6th and the The conducting of eight switching tubes.
Preferably, in just half power frequency period, the pulse-width signal ratio provided to the 6th switching tube is to described the The pulse-width signal that four switching tubes provide postpones first time period, the pulse-width signal ratio provided to the 4th switching tube Postpone second time period to the pulse-width signal that the first switch tube provides；And to the pulsewidth that the 8th switching tube provides Modulated signal postpones first time period than the pulse-width signal provided to the third switching tube, mentions to the third switching tube The pulse-width signal of confession postpones second time period than the pulse-width signal provided to the second switch；In minus half power frequency In period, the pulse-width signal provided to the 7th switching tube is than the pulse-width signal that provides to the 4th switching tube Postpone first time period, the pulse-width signal provided to the 4th switching tube is than the pulsewidth that provides to the first switch tube Modulated signal postpones second time period；And to the pulse-width signal ratio of the 5th switching tube offer to the third switching tube The pulse-width signal of offer postpones first time period, and the pulse-width signal ratio provided to the third switching tube is to described the The pulse-width signal that two switching tubes provide postpones second time period.
Preferably, in just half power frequency period, the pulse-width signal ratio provided to the second switch is to described the The pulse-width signal that eight switching tubes provide postpones the third period, the pulse-width signal ratio provided to the 8th switching tube Postpone for the 4th period to the pulse-width signal that the 4th switching tube provides；And to the pulsewidth that the first switch tube provides Modulated signal postpones the third period than the pulse-width signal provided to the 6th switching tube, mentions to the 6th switching tube The pulse-width signal of confession postponed for the 4th period than the pulse-width signal provided to the third switching tube；In minus half power frequency In period, the pulse-width signal provided to the second switch is than the pulse-width signal that provides to the 5th switching tube Postpone the third period, the pulse-width signal provided to the 5th switching tube is than the pulsewidth that provides to the 4th switching tube Modulated signal postponed for the 4th period；And to the pulse-width signal ratio of first switch tube offer to the 7th switching tube The pulse-width signal of offer postpones the third period, and the pulse-width signal ratio provided to the 7th switching tube is to described the The pulse-width signal that three switching tubes provide postponed for the 4th period.
Preferably, the pulse-width signal that delay inequality is zero is provided to the first switch tube and the 4th switching tube, gives institute It states second switch and third switching tube provides the pulse-width signal that delay inequality is zero；And in just half power frequency period, institute is given When the pulse-width signal of the 6th switching tube offer being provided postponing the 5th than the pulse-width signal that provides to the first switch tube Between section, to the 8th switching tube provide pulse-width signal prolong than the pulse-width signal provided to the second switch Slow 5th period；In minus half power frequency period, to the 7th switching tube provide pulse-width signal ratio to described first Switching tube provide pulse-width signal postpone the 5th period, to the 5th switching tube provide pulse-width signal ratio to The pulse-width signal that the second switch provides postponed for the 5th period.
Preferably, the pulse-width signal that delay inequality is zero is provided to the first switch tube and the 4th switching tube, gives institute It states second switch and third switching tube provides the pulse-width signal that delay inequality is zero；And in just half power frequency period, institute is given When the pulse-width signal of first switch tube offer being provided postponing the 6th than the pulse-width signal that provides to the 6th switching tube Between section, to the 6th switching tube provide pulse-width signal prolong than the pulse-width signal provided to the second switch Slow 7th period；The pulse-width signal provided to the second switch is than the pulsewidth tune that provides to the 8th switching tube The 6th period of signal delay processed provides to the pulse-width signal ratio that the 8th switching tube provides to the first switch tube Pulse-width signal postpone the 7th period；In minus half power frequency period, to the pulsewidth modulation of first switch tube offer Signal postponed for the 6th period than the pulse-width signal provided to the 7th switching tube, provided to the 7th switching tube Pulse-width signal postponed for the 7th period than the pulse-width signal provided to the second switch；To the second switch The pulse-width signal that pipe provides postponed for the 6th period than the pulse-width signal provided to the 5th switching tube, to described The pulse-width signal that 5th switching tube provides postponed for the 7th time than the pulse-width signal provided to the first switch tube Section.
Preferably, the half-bridge inverter includes the first switch tube and second switch for being connected to its DC terminal in turn, The half-bridge AC-AC converter includes: that the 5th switching tube of differential concatenation and the 7th of the 6th switching tube and differential concatenation open Close pipe and the 8th switching tube；Wherein when the 5th switching tube and the 7th switching tube are controlled as conducting, the 6th switch Pipe, the 8th switching tube and two capacitors constitute the first half-bridge inverter, and work as the 6th switching tube and the 8th switching tube quilt When control is is connected, the 5th switching tube, the 7th switching tube and two capacitors constitute the second half-bridge inverters, the controlling party Method includes: to control the first switch tube and second switch alternate conduction in just half power frequency period, controls the 5th He The conducting of 7th switching tube, controls the 6th and the 8th switching tube alternate conduction；In minus half power frequency period, control described first Switching tube and second switch alternate conduction, control the 5th and the 7th switching tube alternate conduction, control the described 6th and the The conducting of eight switching tubes.
Preferably, in just half power frequency period, the pulse-width signal ratio provided to the 6th switching tube is to described the The pulse-width signal that one switching tube provides postponed for the 8th period, the pulse-width signal ratio provided to the 8th switching tube Postpone for the 8th period to the pulse-width signal that the second switch provides；In minus half power frequency period, the described 7th is given The pulse-width signal that switching tube provides postponed for the 8th period than the pulse-width signal provided to the first switch tube, gave The pulse-width signal that 5th switching tube provides postpones the 8th than the pulse-width signal provided to the second switch Period.
Preferably, in just half power frequency period, the pulse-width signal ratio provided to the first switch tube is to described the The pulse-width signal that six switching tubes provide postponed for the 9th period, the pulse-width signal ratio provided to the 6th switching tube Postpone for the tenth period to the pulse-width signal that the second switch provides；The pulsewidth tune provided to the second switch Signal processed postponed for the 9th period than the pulse-width signal provided to the 8th switching tube, provided to the 8th switching tube Pulse-width signal than to the first switch tube provide pulse-width signal postpone the tenth period；In minus half power frequency week In phase, the pulse-width signal provided to the first switch tube prolongs than the pulse-width signal provided to the 7th switching tube Slow 9th period, the pulse-width signal provided to the 7th switching tube is than the pulsewidth tune that provides to the second switch The tenth period of signal delay processed；The pulse-width signal ratio provided to the second switch is provided to the 5th switching tube Pulse-width signal postpone the 9th period, to the 5th switching tube provide pulse-width signal ratio opened to described first It closes the pulse-width signal that pipe provides and postponed for the tenth period.
Needed for two-way DC-AC converter of the invention can be converted to the direct current of rechargeable battery under battery mode Alternating current, and can charge in charging mode to rechargeable battery, charge power and charging current are big, and can be real Existing PFC.Two-way DC-AC converter of the invention improves power density and transfer efficiency, and reduces costs.
Detailed description of the invention
Embodiments of the present invention is further illustrated referring to the drawings, in which:
Fig. 1 is the circuit diagram of the two-way DC-AC converter of one embodiment according to the present invention.
Fig. 2 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.
Fig. 3 is partial enlarged view of the pulse-width signal in just half power frequency period in Fig. 2.
Fig. 4 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 30-t1Equivalent circuit diagram.
Fig. 5 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 31-t2Equivalent circuit diagram.
Fig. 6 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 32-t3Equivalent circuit diagram.
Fig. 7 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 33-t4Equivalent circuit diagram.
Fig. 8 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 34-t5Equivalent circuit diagram.
Fig. 9 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 35-t6Equivalent circuit diagram.
Figure 10 is partial enlarged view of the pulse-width signal in minus half power frequency period in Fig. 2.
Figure 11 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 100-t1Equivalent circuit diagram.
Figure 12 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 101-t2Equivalent circuit diagram.
Figure 13 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 102-t3Equivalent circuit diagram.
Figure 14 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 103-t4Equivalent circuit diagram.
Figure 15 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 104-t5Equivalent circuit diagram.
Figure 16 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 105-t6Equivalent circuit diagram.
Figure 17 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.
Figure 18 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 17.
T at the time of Figure 19 is two-way DC-AC converter shown in FIG. 1 shown in Figure 180-t1Equivalent circuit diagram.
T at the time of Figure 20 is two-way DC-AC converter shown in FIG. 1 shown in Figure 181-t2Equivalent circuit diagram.
T at the time of Figure 21 is two-way DC-AC converter shown in FIG. 1 shown in Figure 182-t3Equivalent circuit diagram.
T at the time of Figure 22 is two-way DC-AC converter shown in FIG. 1 shown in Figure 183-t4Equivalent circuit diagram.
T at the time of Figure 23 is two-way DC-AC converter shown in FIG. 1 shown in Figure 184-t5Equivalent circuit diagram.
T at the time of Figure 24 is two-way DC-AC converter shown in FIG. 1 shown in Figure 185-t6Equivalent circuit diagram.
Figure 25 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 17.
T at the time of Figure 26 is two-way DC-AC converter shown in FIG. 1 shown in Figure 250-t1Equivalent circuit diagram.
T at the time of Figure 27 is two-way DC-AC converter shown in FIG. 1 shown in Figure 251-t2Equivalent circuit diagram.
T at the time of Figure 28 is two-way DC-AC converter shown in FIG. 1 shown in Figure 252-t3Equivalent circuit diagram.
T at the time of Figure 29 is two-way DC-AC converter shown in FIG. 1 shown in Figure 253-t4Equivalent circuit diagram.
T at the time of Figure 30 is two-way DC-AC converter shown in FIG. 1 shown in Figure 254-t5Equivalent circuit diagram.
T at the time of Figure 31 is two-way DC-AC converter shown in FIG. 1 shown in Figure 255-t6Equivalent circuit diagram.
Figure 32 is the waveform diagram of the voltage and current of AC power source under battery charging mode according to user.
Figure 33 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.
Figure 34 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 33.
Figure 35 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 33.
Figure 36 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.
Figure 37 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 36.
Figure 38 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 36.
Figure 39 is the circuit diagram of the two-way DC-AC converter of second embodiment according to the present invention.
Figure 40 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in Figure 39 Waveform diagram.
Figure 41 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 40.
Figure 42 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 40.
Figure 43 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in Figure 39 Waveform diagram.
Figure 44 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 43.
Figure 45 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 43.
Figure 46 is the circuit diagram of the two-way DC-AC converter of third embodiment according to the present invention.
Specific embodiment
In order to make the objectives, technical solutions, and advantages of the present invention clearer, pass through below in conjunction with attached drawing specific real Applying example, the present invention is described in more detail.
Fig. 1 is the circuit diagram of the two-way DC-AC converter of one embodiment according to the present invention.As shown in Figure 1, two-way DC-AC converter 1 includes full-bridge inverter 11, transformer Tr, inductance 14, half-bridge AC-AC converter 12 and control device 17.
Full-bridge inverter 11 includes metal-oxide half field effect transistor (MOSFET) S1、MOSFET S2、MOSFET S3And MOSFET S4.Wherein MOSFET S1With MOSFET S2It is connected in series between the anode and cathode of rechargeable battery 13, and forms node A, MOSFET S3With MOSFET S4It is connected in series between the anode and cathode of rechargeable battery 13, and forms node B.
Half-bridge AC-AC converter 12 includes capacitor C1With capacitor C2And it two-way controlled tr tube 121 and two-way controllably opens Pipe 122 is closed, wherein capacitor C1With capacitor C2The both ends of load 15 or AC power source are connected in series in, and form node D.It is two-way can Control switching tube 121 and two-way controlled tr tube 122 are connected in series in concatenated capacitor C1With capacitor C2Both ends, and form node What C, interior joint C and D constituted half-bridge AC-AC converter 12 first exchanges end, concatenated capacitor C1With capacitor C2Both ends structure End is exchanged at the second of half-bridge AC-AC converter 12.Two-way controlled tr tube 121 further includes the MOSFET S of differential concatenation5 With MOSFET S6, two-way controlled tr tube 122 further includes the MOSFET S of differential concatenation7With MOSFET S8.As MOSFET S5 With MOSFET S7When being controlled as conducting, MOSFET S6、MOSFET S8, capacitor C1With capacitor C2Constitute a half-bridge inverter； Equally work as MOSFET S6With MOSFET S8When being controlled as conducting, MOSFET S5、MOSFET S7Capacitor C1With capacitor C2It constitutes Another half-bridge inverter.
The primary side of transformer Tr is connected between node A and node B, secondary side be connected to node C and node D it Between.Inductance 14 is connected between one end of the secondary side of transformer Tr and node C.
The working principle of its battery discharge mode is described below in conjunction with the equivalent circuit diagram of two-way DC-AC converter 1.
Fig. 2 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.As shown in Fig. 2, VoIt is the voltage for loading 15 both ends, MOSFET S1With MOSFET S2Alternate conduction is controlled as, MOSFET S3With MOSFET S4It is also controlled by as alternate conduction.In just half power frequency period, MOSFET S5With MOSFET S7Quilt Control is constant conduction, MOSFET S6With MOSFET S8It is controlled as alternate conduction；In minus half power frequency period, MOSFET S5 With MOSFET S7It is controlled as alternate conduction, MOSFET S6With MOSFET S8It is controlled as constant conduction.
Fig. 3 is partial enlarged view of the pulse-width signal in just half power frequency period in Fig. 2, and Fig. 3 also shows node A, the voltage between B, the waveform diagram of the electric current in voltage and inductance between node C, D.Wherein: being supplied to MOSFET S4's Pulse-width signal is relative to MOSFET S1Pulse-width signal be delayed d2T (period that T is pulse-width signal), is supplied to MOSFET S3Pulse-width signal relative to MOSFET S2Pulse-width signal be delayed d2T；Additionally, it is provided giving MOSFET S6Pulse-width signal relative to MOSFET S4Pulse-width signal be delayed d1T is supplied to MOSFET S8Pulsewidth modulation Signal is relative to MOSFET S3Pulse-width signal be delayed d1T。
Fig. 4 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 30-t1Equivalent circuit diagram.At the moment t0-t1, MOSFET S1With MOSFET S4Conducting, and MOSFET S5、MOSFET S6With MOSFET S7Conducting, the electric current of formation Direction is as shown in the dotted arrow in Fig. 4.In the primary side of transformer Tr, electric current successively from the anode of rechargeable battery 13, MOSFET S1, node A, the primary side of transformer Tr, node B, MOSFET S4To the cathode of rechargeable battery 13, can fill at this time Battery 13 discharges, and the voltage V between node A, BABFor | Vb|.In the secondary side of transformer Tr, electric current is successively from transformer Secondary side, inductance 14, the node C, MOSFET S of Tr6、MOSFET S5, a portion electric current is by capacitor C1To node D, separately One part of current is through loading 15 and capacitor C2To node D, 14 energy storage of inductance at this time, and the voltage V between node C, DCDIt is 0.5 | VO|。
Fig. 5 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 31-t2Equivalent circuit diagram.At the moment t1-t2, MOSFET S2With MOSFET S4Conducting, and MOSFET S5、MOSFET S6With MOSFET S7Conducting, the electric current of formation Direction is as shown in the dotted arrow in Fig. 5.In the secondary side of transformer Tr, current direction is same as shown in Figure 4, at this time node C, Voltage V between DCDIt is 0.5 | VO|.In the primary side of transformer Tr, electric current is successively from node A, the primary side of transformer Tr, section Point B, MOSFET S4To MOSFET S2, the voltage V between node A and B at this timeABIt is 0.
Fig. 6 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 32-t3Equivalent circuit diagram.At the moment t2-t3, MOSFET S2With MOSFET S3Conducting, and MOSFET S5、MOSFET S6With MOSFET S7Conducting, the electric current of formation Direction is as shown in the dotted arrow in Fig. 6.In the secondary side of transformer Tr, current direction is same as shown in Figure 4, at this time node C, Voltage V between DCDIt is 0.5 | VO|.In the primary side of transformer Tr, the electric current successively cathode from rechargeable battery 13, MOSFET S2, node A, the primary side of transformer Tr, node B, MOSFET S3To the anode of rechargeable battery 13, at this time between node A and B Voltage VABFor-| Vb|。
Fig. 7 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 33-t4Equivalent circuit diagram.At the moment t3-t4, MOSFET S2With MOSFET S3Conducting, and MOSFET S5、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Fig. 7.In the primary side of transformer, electric current successively from the anode of rechargeable battery 13, MOSFET S3, node B, the primary side of transformer Tr, node A, MOSFET S2To the cathode of rechargeable battery 13, can fill at this time Battery 13 discharges, and the voltage V between node A and BABFor-| Vb|.In the secondary side of transformer Tr, electric current is successively from transformation Secondary side, the node D of device Tr, a portion electric current is through capacitor C1With load 15, another part electric current is through capacitor C2Afterwards again successively Through MOSFET S8、MOSFET S7, node C to inductance 14,14 energy storage of inductance at this time, and the voltage V between node C, DCDFor- 0.5|VO|。
Fig. 8 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 34-t5Equivalent circuit diagram.At the moment t4-t5, MOSFET S1With MOSFET S3Conducting, and MOSFET S5、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Fig. 8.In the secondary side of transformer Tr, current direction is same as shown in Figure 7, at this time inductance 14 It releases and can and be supplied to load 15, and the voltage V between node C, DCDIt is -0.5 | VO|.In the primary side of transformer Tr, electric current according to The secondary primary side from transformer Tr, node A, MOSFET S1、MOSFET S3To node B, the voltage V between node A, B at this timeAB It is 0.
Fig. 9 is t at the time of two-way DC-AC converter shown in FIG. 1 is shown in Fig. 35-t6Equivalent circuit diagram.At the moment t5-t6, MOSFET S1With MOSFET S4Conducting, and MOSFET S5、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Fig. 9.In the secondary side of transformer Tr, current direction is same as shown in Figure 7, at this time inductance 14 It releases and can and be supplied to load 15, and the voltage V between node C, DCDIt is -0.5 | VO|.In the primary side of transformer Tr, electric current according to The secondary primary side from transformer Tr, node A, MOSFET S1, rechargeable battery 13 anode and cathode, MOSFET S4To contact B, at this time the voltage V between node A, BABFor | Vb|。
Figure 10 is partial enlarged view of the pulse-width signal in minus half power frequency period in Fig. 2, and Figure 10 also shows section Voltage between point A, B, the waveform diagram of the electric current in voltage and inductance between node C, D.Wherein, it is supplied to MOSFET S7 Pulse-width signal relative to MOSFET S4Pulse-width signal be delayed d1T；It is supplied to MOSFET S5Pulsewidth modulation letter Number relative to MOSFET S3Pulse-width signal be delayed d1T。
Figure 11 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 100-t1Equivalent circuit diagram.At the moment t0-t1, MOSFET S1With MOSFET S4Conducting, and MOSFET S6、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as the dotted line in Figure 11 arrows.In the primary side of transformer Tr, current direction is same as shown in Figure 4, herein no longer It repeats, at this time the voltage V between node A, BABFor | Vb|.In the secondary side of transformer Tr, electric current is successively from the two of transformer Tr Secondary side, inductance 14, node C, MOSFET S7、MOSFET S8, a portion electric current is through capacitor C2To node D, another part electricity Flow through 15 and capacitor C of load1To node D, 14 energy storage of inductance at this time, and the voltage V between node C, DCDIt is 0.5 | VO|。
Figure 12 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 101-t2Equivalent circuit diagram.At the moment t1-t2, MOSFET S2With MOSFET S4Conducting, and MOSFET S6、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 12.In the primary side of transformer Tr, current direction is same as shown in Figure 5, in transformer The secondary side of Tr, current direction is same as shown in Figure 11, and details are not described herein.
Figure 13 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 102-t3Equivalent circuit diagram.At the moment t2-t3, MOSFET S2With MOSFET S3Conducting, and MOSFET S6、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 13.In the primary side of transformer Tr, current direction is same as shown in Figure 7, in transformer The secondary side of Tr, electric current is successively from inductance 14, the secondary side of transformer Tr, node D, capacitor C2、MOSFET S8、MOSFET S7 To node C.Wherein in capacitor C2, load 15 and capacitor C1There is also reactive currents.
Figure 14 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 103-t4Equivalent circuit diagram.At the moment t3-t4, MOSFET S2With MOSFET S3Conducting, and MOSFET S5、MOSFET S6With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 14.In the primary side of transformer Tr, current direction is same as shown in Figure 7, in transformer The secondary side of Tr, electric current is successively from the secondary side of transformer Tr, node D, and one part of current is through capacitor C2With load 15, another portion Divide electric current through capacitor C1Afterwards again successively through MOSFET S5、MOSFET S6, node C to inductance 14.14 energy storage of inductance at this time, and save Voltage V between point C, DCDIt is -0.5 | VO|。
Figure 15 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 104-t5Equivalent circuit diagram.At the moment t4-t5, MOSFET S1With MOSFET S3Conducting, and MOSFET S5、MOSFET S6With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 15.In the secondary side of transformer Tr, current direction is same as shown in Figure 14, in transformer The primary side of Tr, current direction is same as shown in Figure 8, and details are not described herein.
Figure 16 is two-way DC-AC converter shown in FIG. 1 in moment t shown in Fig. 105-t6Equivalent circuit diagram.At the moment t5-t6, MOSFET S1With MOSFET S4Conducting, and MOSFET S5、MOSFET S6With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 16.In the secondary side of transformer Tr, current direction successively from the secondary side of transformer Tr, Inductance 14, node C, MOSFET S6、MOSFET S5, capacitor C1To node D, wherein capacitor C2, load 15 and capacitor C1In also deposit In reactive current.In the primary side of transformer Tr, current direction is same as shown in Figure 9, and details are not described herein.
Due to Fig. 3 and i shown in Fig. 10LWaveform it is identical, i.e., the electric current i in inductance 14LAt the time of just half power frequency period t0-t6With t at the time of minus half power frequency period0-t6It is identical.Just half power frequency period and minus half power frequency period, inductance are not distinguished below Electric current i in 14LIt is indicated by following equation:
Wherein, n is the primary side of transformer Tr and the turn ratio of secondary side, and L is the inductance value of inductance 14.
t0~t6Relationship indicated by following equation:
According to aforesaid equation it can be concluded that d1And d2Restrictive condition are as follows:
In addition, the electric current i in inductance 14LIn moment t0-t3Waveform in moment t3-t6Waveform symmetry, that is, meet: iL (t0)=- iL(t3)=iL(t6)。
So as to obtain the electric current i in inductance 14LIt is indicated by following equation:
Thus calculate output power P is indicated by following equation:
Wherein fsFor the frequency of pulse-width signal.If the resistance of load 15 is R, as satisfaction (- 4d1 2-2d2 2-4d1d2+ 2d1+d2) > 4fsL/R, rechargeable battery 13 realize step-up discharge.As satisfaction (- 4d1 2-2d2 2-4d1d2+2d1+d2) < 4fsL/R, Rechargeable battery 13 realizes step-down discharge.It follows that the two-way DC-AC converter 1 of the present embodiment can be realized boosting or drop Press electricity.
The working principle of its battery charging mode according to user is described below in conjunction with the equivalent circuit diagram of two-way DC-AC converter 1.
Figure 17 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.As shown in figure 17, MOSFET S1With MOSFET S2It is controlled as alternate conduction, MOSFET S3With MOSFET S4 It is also controlled by as alternate conduction.In just half power frequency period, MOSFET S5With MOSFET S7Constant conduction is controlled as, MOSFET S6With MOSFET S8It is controlled as alternate conduction；In minus half power frequency period, MOSFET S5With MOSFET S7It is controlled It is made as alternate conduction, MOSFET S6With MOSFET S8It is controlled as constant conduction.
Figure 18 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 17, and Figure 18 also shows section Voltage between point A, B, the waveform diagram of the electric current in voltage and inductance between node C, D.Wherein, it is supplied to MOSFET S8 Pulse-width signal relative to MOSFET S4Pulse-width signal be delayed d2' T, it is supplied to MOSFET S2Pulsewidth modulation Signal is relative to MOSFET S8Pulse-width signal be delayed d1'T；Equally, it is supplied to MOSFET S6Pulse-width signal phase For MOSFET S3Pulse-width signal be delayed d2' T, it is supplied to MOSFET S1Pulse-width signal relative to MOSFET S6Pulse-width signal be delayed d1’T。
T at the time of Figure 19 is two-way DC-AC converter shown in FIG. 1 shown in Figure 180-t1Equivalent circuit diagram.At the moment t0-t1, MOSFET S1With MOSFET S4Conducting, and MOSFET S5、MOSFET S6With MOSFET S7Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 19.One part of current in the secondary side of transformer Tr, AC power source 16 successively passes through MOSFET S5、MOSFET S6, node C, inductance 14, transformer Tr secondary side to node D, another part electric current is through capacitor C1 To node D, most afterwards through capacitor C2To AC power source 16, the voltage V between node C, D at this timeCDIt is 0.5 | VO|.In transformer Tr Primary side, electric current is successively from the cathode of rechargeable battery 13, MOSFET S4, node B, the primary side of transformer Tr, node A, MOSFET S1To the anode of rechargeable battery 13, the voltage V between node A, B at this timeABFor | Vb|。
T at the time of Figure 20 is two-way DC-AC converter shown in FIG. 1 shown in Figure 181-t2Equivalent circuit diagram.At the moment t1-t2, MOSFET S1With MOSFET S4Conducting, and MOSFET S5、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 20.In the secondary side of transformer Tr, electric current is successively from AC power source 16, capacitor C1To section Point D, secondary side, inductance 14, node C, MOSFET S of a portion electric current successively through transformer Tr7、MOSFET S8To friendship Galvanic electricity source 16, another part electric current is directly through capacitor C2AC power source 16 is returned to, at this time the voltage V between node C, DCDIt is -0.5 |VO|.In the primary side of transformer Tr, electric current is successively from the anode of rechargeable battery 13, MOSFET S1, node A, transformer Tr Primary side, node B, MOSFET S4To the cathode of rechargeable battery 13, the voltage V between node A and B at this timeABFor | Vb|。
T at the time of Figure 21 is two-way DC-AC converter shown in FIG. 1 shown in Figure 182-t3Equivalent circuit diagram.At the moment t2-t3, MOSFET S2With MOSFET S4Conducting, and MOSFET S5、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 21.In the secondary side of transformer Tr, current direction is same as shown in Figure 20, at this time node C, the voltage V between DCDIt is -0.5 | VO|.In the primary side of transformer Tr, the electric current successively primary side from transformer Tr, node B、MOSFET S4、MOSFET S2To node A, the voltage V between node A and B at this timeABIt is 0.
T at the time of Figure 22 is two-way DC-AC converter shown in FIG. 1 shown in Figure 183-t4Equivalent circuit diagram.At the moment t3-t4, MOSFET S2With MOSFET S3Conducting, and MOSFET S5、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 22.In the secondary side of transformer Tr, current direction is identical as Figure 20, at this time node C, D Between voltage VCDIt is -0.5 | VO|.In the primary side of transformer Tr, the electric current successively cathode from rechargeable battery 13, MOSFET S2, node A, the primary side of transformer Tr, node B, MOSFET S3To the anode of rechargeable battery 13, at this time between node A, B Voltage VABFor-| Vb|。
T at the time of Figure 23 is two-way DC-AC converter shown in FIG. 1 shown in Figure 184-t5Equivalent circuit diagram.When Carve t4-t5, MOSFET S2With MOSFET S3Conducting, and MOSFET S5、MOSFET S6With MOSFET S7Conducting, the electricity of formation Direction is flowed as shown in the dotted arrow in Figure 23.In the secondary side of transformer Tr, current direction is identical as Figure 19, at this time node C, Voltage V between DCDIt is 0.5 | VO|.In the primary side of transformer Tr, the electric current successively anode from rechargeable battery 13, MOSFET S3, node B, the primary side of transformer Tr, node A, MOSFET S2To the cathode of rechargeable battery 13, at this time between node A, B Voltage VABFor-| Vb|。
T at the time of Figure 24 is two-way DC-AC converter shown in FIG. 1 shown in Figure 185-t6Equivalent circuit diagram.When Carve t5-t6, MOSFET S1With MOSFET S3Conducting, and MOSFET S5、MOSFET S6With MOSFET S7Conducting, the electricity of formation Direction is flowed as shown in the dotted arrow in Figure 24.In the secondary side of transformer Tr, current direction is identical as Figure 19, at this time node C, Voltage V between DCDIt is 0.5 | VO|.In the primary side of transformer Tr, electric current successively from the primary side of transformer Tr, node A, MOSFET S1、MOSFET S3To node B, the voltage V between node A, B at this timeABIt is 0.
Figure 25 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 17, and Figure 25 also shows section Voltage between point A, B, the waveform diagram of the electric current in voltage and inductance between node C, D.Wherein, it is supplied to MOSFET S5 Pulse-width signal relative to MOSFET S4Pulse-width signal be delayed d2' T, it is supplied to MOSFET S2Pulsewidth modulation Signal is relative to MOSFET S5Pulse-width signal be delayed d1'T；Equally, it is supplied to MOSFET S7Pulse-width signal phase For MOSFET S3Pulse-width signal be delayed d2' T, it is supplied to MOSFET S1Pulse-width signal relative to MOSFET S7Pulse-width signal be delayed d1’T。
T at the time of Figure 26 is two-way DC-AC converter shown in FIG. 1 shown in Figure 250-t1Equivalent circuit diagram.At the moment t0-t1, MOSFET S1With MOSFET S4Conducting, and MOSFET S6、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 26.In the secondary side of transformer Tr, the electric current successively secondary side from transformer Tr, node D, a portion electric current is successively through capacitor C1AC power source 16 is returned to, another part electric current is through capacitor C2It successively passes through again afterwards MOSFET S8、MOSFET S7, node C to inductance 14, at this time the voltage V between node C, DCDIt is 0.5 | VO|.In transformer Tr Primary side, current direction is same as shown in Figure 19, at this time the voltage V between node A, BABFor | Vb|。
T at the time of Figure 27 is two-way DC-AC converter shown in FIG. 1 shown in Figure 251-t2Equivalent circuit diagram.At the moment t1-t2, MOSFET S1With MOSFET S4Conducting, and MOSFET S5、MOSFET S6With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 27.In the secondary side of transformer Tr, the electric current successively secondary side from transformer Tr, inductance 14, node C, MOSFET S6To MOSFET S5, a portion electric current is through capacitor C1To node D, another part electric current is through exchanging Power supply 16 and capacitor C2To node D, the voltage V between node C, D at this timeCDIt is -0.5 | VO|.In the primary side of transformer Tr, electricity It is same as shown in Figure 20 to flow direction, at this time the voltage V between node A and BABFor | Vb|。
T at the time of Figure 28 is two-way DC-AC converter shown in FIG. 1 shown in Figure 252-t3Equivalent circuit diagram.At the moment t2-t3, MOSFET S2With MOSFET S4Conducting, and MOSFET S5、MOSFET S6With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 28.In the secondary side of transformer Tr, current direction is same as shown in Figure 27, at this time node C, the voltage V between DCDIt is -0.5 | VO|.In the primary side of transformer Tr, electric current is successively from MOSFET S2, node A, transformer Primary side, node B to the MOSFET S of Tr4, the voltage V between node A, B at this timeABIt is 0.
T at the time of Figure 29 is two-way DC-AC converter shown in FIG. 1 shown in Figure 253-t4Equivalent circuit diagram.At the moment t3-t4, MOSFET S2With MOSFET S3Conducting, and MOSFET S5、MOSFET S6With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 29.In the secondary side of transformer Tr, current direction is identical as Figure 27, at this time node C, D Between voltage VCDIt is -0.5 | VO|.In the primary side of transformer Tr, the electric current successively cathode from rechargeable battery 13, MOSFET S2, node A, the primary side of transformer Tr, node B, MOSFET S3To the anode of rechargeable battery 13, at this time between node A, B Voltage VABFor-| Vb|。
T at the time of Figure 30 is two-way DC-AC converter shown in FIG. 1 shown in Figure 254-t5Equivalent circuit diagram.At the moment t4-t5, MOSFET S2With MOSFET S3Conducting, and MOSFET S6、MOSFET S7With MOSFET S8Conducting, the electric current of formation Direction is as shown in the dotted arrow in Figure 30.In the secondary side of transformer Tr, current direction is identical as Figure 26, at this time node C, D Between voltage VCDIt is 0.5 | VO|.In the primary side of transformer Tr, the electric current successively anode from rechargeable battery 13, MOSFET S3, node B, the primary side of transformer Tr, node A, MOSFET S2To the cathode of rechargeable battery 13, at this time between node A, B Voltage VABFor-| Vb|。
T at the time of Figure 31 is two-way DC-AC converter shown in FIG. 1 shown in Figure 255-t6Equivalent circuit diagram.At the moment t5-t6, MOSFET S1With MOSFET S3Conducting, and MOSFET S6、MOSFET S7With MOSFET S8Conducting, the electric current of formation Shown in the dotted arrow as in Fig. 31 of direction.In the secondary side of transformer Tr, current direction is identical as Figure 26, at this time node C, D Between voltage VCDIt is 0.5 | VO|.In the primary side of transformer Tr, electric current successively from the primary side of transformer Tr, node A, MOSFET S1、MOSFET S3To node B, the voltage V between node A, B at this timeABIt is 0.
Under battery charging mode according to user, the expression formula that can equally calculate output power P is as follows:
According to above-mentioned conclusion it is found that under battery charging mode according to user, the two-way DC-AC converter 1 of above-described embodiment equally may be used To realize boosting work or decompression work.The expression formula class of the discharge power under charge power and discharge mode under charge mode Seemingly, it follows that two-way DC-AC converter 1 has biggish charge power and charging current.And in the UPS of the prior art Charger is an individual circuit of reversed excitation, and charge power is much smaller than the rated output power of UPS.Therefore with the prior art Charger in UPS is compared, and charge power and charging current dramatically increase.
Figure 32 is the waveform diagram of the voltage and current of AC power source under battery charging mode according to user.Wherein Figure 32 also shows electricity Electric current i in sense 14LWith the electric current i in capacitor C1 or C2CWaveform diagram, and the electric current i in AC power sourceOEqual to iL-iC, thus Electric current i in AC power sourceOWith the voltage V of AC power sourceOSame-phase, it is achieved that the function of PFC.
No matter in battery discharge mode or under battery charging mode according to user, MOSFET S1~MOSFET S4Voltage all by Clamp is in VbHereinafter, and MOSFET S5~MOSFET S8Voltage be all clamped at 0.5 | VO| hereinafter, therefore there is no overshoots Voltage avoids the failure of component in circuit.
Discharge mode or charge mode, conversion effect can be realized by linear transformation in two-way DC-AC converter of the invention Rate is high.And charger is omitted, component number is few, and at low cost, power density is big.
The embodiments of the present invention also provide another battery discharging methods for being used for two-way DC-AC converter 1.Below will The working principle of its battery discharge mode is described in conjunction with Figure 33-35.
Figure 33 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.As shown in figure 33, MOSFET S1With MOSFET S2It is controlled as alternate conduction, MOSFET S3With MOSFET S4 It is also controlled by as alternate conduction, gives MOSFET S1With MOSFET S4The delay inequality of the pulse-width signal of offer is zero, is equally given MOSFET S2With MOSFET S3The delay inequality of the pulse-width signal of offer is zero.In just half power frequency period, MOSFET S5 With MOSFET S7It is controlled as constant conduction, MOSFET S6With MOSFET S8It is controlled as alternate conduction；In minus half power frequency week In phase, MOSFET S5With MOSFET S7It is controlled as alternate conduction, MOSFET S6With MOSFET S8It is controlled as persistently leading It is logical.
Figure 34 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 33, and Figure 34 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein give MOSFET S6The arteries and veins of offer Wide modulated signal is relative to MOSFET S4Pulse-width signal be delayed d1T is equally provided to MOSFET S8Pulsewidth modulation letter Number relative to MOSFET S3Pulse-width signal be delayed d1T。
Wherein, two-way DC-AC converter 1 t at the time of Figure 340-t1Operating mode at the time of Fig. 3 t0-t1Work Operation mode is identical, t at the time of Figure 341-t3Operating mode at the time of Fig. 3 t1-t3Operating mode it is identical, in Figure 34 At the time of t3-t4Operating mode at the time of Fig. 3 t3-t4Operating mode it is identical, t at the time of Figure 344-t6Working mould Formula and t at the time of Fig. 34-t6Operating mode it is identical, details are not described herein.
Figure 35 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 33, and Figure 35 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein, it is supplied to MOSFET S7's Pulse-width signal is relative to MOSFET S4Pulse-width signal be delayed d1T；It is supplied to MOSFET S5Pulse-width signal Relative to MOSFET S3Pulse-width signal be delayed d1T。
Wherein, two-way DC-AC converter 1 t at the time of Figure 350-t1Operating mode at the time of Figure 10 t0-t1's Operating mode is identical, t at the time of Figure 351-t3Operating mode at the time of Figure 10 t1-t3Operating mode it is identical, scheming T at the time of 353-t4Operating mode at the time of Figure 10 t3-t4Operating mode it is identical, t at the time of Figure 354-t6Work Operation mode and t at the time of Figure 104-t6Operating mode it is identical, details are not described herein.
Under battery discharge mode, due to d2T=0, the expression formula that can equally calculate output power P are as follows:
The working principle of its battery charging mode according to user is described below in conjunction with Figure 36-38.
Figure 36 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in FIG. 1 Waveform diagram.As shown in figure 36, MOSFET S1With MOSFET S2It is controlled as alternate conduction, MOSFET S3With MOSFET S4 It is also controlled by as alternate conduction, gives MOSFET S1With MOSFET S4The delay inequality of the pulse-width signal of offer is zero, is equally given MOSFET S2With MOSFET S3The delay inequality of the pulse-width signal of offer is zero.In just half power frequency period, MOSFET S5 With MOSFET S7It is controlled as constant conduction, MOSFET S6With MOSFET S8It is controlled as alternate conduction；In minus half power frequency week In phase, MOSFET S5With MOSFET S7It is controlled as alternate conduction, MOSFET S6With MOSFET S8It is controlled as persistently leading It is logical.
Figure 37 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 36, and Figure 37 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein, it is supplied to MOSFET S2's Pulse-width signal ratio gives MOSFET S8Pulse-width signal be delayed d1'T；It is supplied to MOSFET S1Pulse-width signal Than giving MOSFET S6Pulse-width signal be delayed d1'T；It is supplied to MOSFET S8Pulse-width signal ratio be supplied to MOSFET S1Pulse-width signal be delayed d2' T, it is supplied to MOSFET S6Pulse-width signal ratio be supplied to MOSFET S2 Pulse-width signal be delayed d2’T。
Wherein, two-way DC-AC converter 1 t at the time of Figure 370-t1Operating mode at the time of Figure 18 t4-t5's Operating mode is identical, t at the time of Figure 371-t2Operating mode at the time of Figure 18 t0-t1Operating mode it is identical, Figure 37 At the time of t2-t3Operating mode at the time of Figure 18 t1-t2Operating mode it is identical, t at the time of Figure 373-t4Working mould Formula and t at the time of Figure 183-t4Operating mode it is identical, details are not described herein.
Figure 38 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 36, and Figure 38 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein, it is supplied to MOSFET S5's Pulse-width signal is relative to MOSFET S4Pulse-width signal be delayed d2' T is equally supplied to MOSFET S7Pulsewidth tune Signal processed is relative to MOSFET S3Pulse-width signal be delayed d2'T.It is supplied to MOSFET S3Pulse-width signal it is opposite In MOSFET S5Pulse-width signal be delayed d1' T, it is supplied to MOSFET S4Pulse-width signal relative to MOSFET S7 Pulse-width signal be delayed d1’T。
Wherein, two-way DC-AC converter 1 t at the time of Figure 380-t1Operating mode at the time of Figure 25 t4-t5's Operating mode is identical, t at the time of Figure 381-t2Operating mode at the time of Figure 25 t0-t1Operating mode it is identical, Figure 38 At the time of t2-t3 operating mode at the time of Figure 25 t1-t2Operating mode it is identical, t at the time of Figure 383-t4Working mould Formula and t at the time of Figure 253-t4Operating mode it is identical, details are not described herein.
Figure 39 is the circuit diagram of the two-way DC-AC converter of second embodiment according to the present invention.The basic phase of Figure 39 and Fig. 1 Together, difference is, using half-bridge inverter 21 instead of the full-bridge inverter 11 in Fig. 1.In i.e. two-way DC-AC converter 2 Capacitor C3With capacitor C4It is connected in turn between the anode and cathode of rechargeable battery 13, and capacitor C3And C4The formation being connected Node B be connected to transformer Tr primary side one end (i.e. non-same polarity).
The working principle of the battery discharge mode of two-way DC-AC converter 2 is described below in conjunction with Figure 40-42.
Figure 40 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in Figure 39 Waveform diagram.As shown in figure 40, to the MOSFET S in Figure 391、MOSFET S2、MOSFET S5~S8The pulsewidth modulation of offer Signal is identical with the pulse-width signal for giving corresponding MOSFET to provide in Figure 33.
Figure 41 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 40, and Figure 41 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein, two-way DC-AC converter 2 exists T at the time of Figure 410-t1、t1-t2、t2-t3、t3-t4Operating mode respectively with two-way DC-AC converter 1 at the time of Figure 34 t0- t1、t1-t3、t3-t4And t4-t6Operating mode it is identical, details are not described herein.
Figure 42 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 40, and Figure 42 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein, two-way DC-AC converter 2 exists T at the time of Figure 420-t1、t1-t2、t2-t3、t3-t4Operating mode respectively with two-way DC-AC converter 1 at the time of Figure 35 t0- t1、t1-t3、t3-t4And t4-t6Operating mode it is identical, details are not described herein.
The working principle of the battery charging mode according to user of two-way DC-AC converter 2 is described below in conjunction with Figure 43-45.
Figure 43 is the pulse-width signal that control device is provided to the switching tube in two-way DC-AC converter shown in Figure 39 Waveform diagram.As shown in figure 43, to the MOSFET S in Figure 391、MOSFET S2、MOSFET S5~S8The pulsewidth modulation of offer Signal is identical with the pulse-width signal for giving corresponding MOSFET to provide in Figure 36.
Figure 44 is partial enlarged view of the pulse-width signal in just half power frequency period in Figure 43, and Figure 44 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein, two-way DC-AC converter 2 exists T at the time of Figure 440-t1、t1-t2、t2-t3、t3-t4Operating mode respectively with two-way DC-AC converter 1 at the time of Figure 37 t0- t1、t1-t2、t2-t3、t3-t4Operating mode it is identical, details are not described herein.
Figure 45 is partial enlarged view of the pulse-width signal in minus half power frequency period in Figure 43, and Figure 45 also shows section Voltage between point A, B, the waveform diagram of the electric current of voltage and inductance between node C, D.Wherein, two-way DC-AC converter 2 exists T at the time of Figure 450-t1、t1-t2、t2-t3、t3-t4Operating mode respectively with two-way DC-AC converter 1 at the time of Figure 38 t0- t1、t1-t2、t2-t3、t3-t4Operating mode it is identical, details are not described herein.
Figure 46 is the circuit diagram of the two-way DC-AC converter of third embodiment according to the present invention.Itself and the basic phase of Fig. 1 Together, difference is, using full-bridge AC-AC converter 32 instead of the half-bridge AC-AC converter 12 in Fig. 1, i.e., by differential concatenation MOSFET S9With MOSFET S10Instead of capacitor C1, and by the MOSFET S of differential concatenation11With MOSFET S12Instead of capacitor C2.Wherein as MOSFET S5、MOSFET S7、MOSFET S9With MOSFET S11When being controlled as conducting, MOSFET S6、 MOSFET S8、MOSFET S10With MOSFET S12Constitute a full-bridge inverter；And work as MOSFET S6、MOSFET S8、 MOSFET S10With MOSFET S12When being controlled as conducting, MOSFET S5、MOSFET S7、MOSFET S9With MOSFET S11Structure At another full-bridge inverter.
Wherein, under battery discharge mode, control device gives MOSFET S1~MOSFET S8Arteries and veins as shown in Figure 2 is provided Wide modulated signal, and give MOSFET S11With MOSFET S12It provides and MOSFET S5With MOSFET S6Identical pulsewidth tune Signal processed gives MOSFET S9With MOSFET S10It provides and MOSFET S7With MOSFET S8Identical pulse-width signal.
Under battery charging mode according to user, control device gives MOSFET S1~MOSFET S8Pulsewidth tune as shown in figure 17 is provided Signal processed gives MOSFET S11With MOSFET S12It provides and MOSFET S5With MOSFET S6Identical pulsewidth modulation letter Number, give MOSFET S9With MOSFET S10It provides and MOSFET S7With MOSFET S8Identical pulse-width signal.
In another two-way DC-AC converter of the invention, the MOSFET S in Figure 46 is replaced using capacitor3With MOSFET S4。
In other embodiments of the invention, inductance 14 is connected between the secondary side of transformer Tr and node D, or connection Between the primary side and node A or B of transformer Tr.
In other embodiments of the invention, two-way DC-AC converter further includes the filtered electrical in parallel with rechargeable battery Hold, for carrying out High frequency filter, effective protection rechargeable battery under battery charging mode according to user.
In other embodiments of the invention, it is replaced in above-described embodiment using insulated gate bipolar transistor MOSFET。
Although the present invention has been described by means of preferred embodiments, the present invention is not limited to described here Embodiment, without departing from the present invention further include made various changes and variation.

Claims (17)

1. a kind of two-way DC-AC converter characterized by comprising
Full-bridge or half-bridge inverter；
Transformer, the primary side of the transformer are connected to the exchange end of the full-bridge or half-bridge inverter；
AC-AC converter, there is the first exchange end to exchange end with second, and first exchange end is connected to the transformer Secondary side, second exchange end are configured as and load or AC power source is connected；And
Inductance is connected to exchanging between end for the primary side of the transformer and the full-bridge or half-bridge inverter, or connection Secondary side to the transformer exchanges between end with the first of the AC-AC converter.
2. two-way DC-AC converter according to claim 1, which is characterized in that the AC-AC converter is two series connection The half-bridge AC-AC converter that the two-way controlled tr tube of connection and the capacitor of two series connections are constituted, described two series connection connect The two-way controlled tr tube connect is formed by node and the capacitor of described two series connections is formed by node as described One exchange end.
3. two-way DC-AC converter according to claim 2, which is characterized in that the two-way of described two series connections can Control two switching tubes that each of switching tube includes differential concatenation.
4. two-way DC-AC converter according to claim 3, which is characterized in that the half-bridge AC-AC converter includes: The 7th switching tube and the 8th switching tube of 5th switching tube of differential concatenation and the 6th switching tube and differential concatenation；Wherein when When 5th switching tube and the 7th switching tube are controlled as conducting, the 6th switching tube, the 8th switching tube and two capacitors Constitute the first half-bridge inverter, and when the 6th switching tube and the 8th switching tube are controlled as conducting, the described 5th is opened Guan Guan, the 7th switching tube and two capacitors constitute the second half-bridge inverter.
5. two-way DC-AC converter according to claim 1, which is characterized in that the AC-AC converter is four two-way The full-bridge AC-AC converter that controlled tr tube is constituted, the nodes of two bridge arms of the full-bridge AC-AC converter is as described the One exchange end.
6. two-way DC-AC converter according to claim 5, which is characterized in that in four two-way controlled tr tubes Each include two switching tubes of differential concatenation.
7. two-way DC-AC converter according to claim 6, which is characterized in that the full-bridge AC-AC converter includes: 5th switching tube of differential concatenation and the 6th switching tube, the 7th switching tube of differential concatenation and the 8th switching tube, differential concatenation 9th switching tube and the tenth switching tube, the 11st switching tube of differential concatenation and the 12nd switching tube；Wherein when the described 5th, Seven, the 9th and the 11st switching tube be controlled as conducting when, described six, the eight, the tenth and the 12nd switching tube constitute first Full-bridge inverter, and when described six, the eight, the tenth and the 12nd switching tube be controlled as conducting when, the described 5th, the Seven, the 9th and the 11st switching tube constitute the second full-bridge inverter.
8. two-way DC-AC converter according to claim 1, which is characterized in that the two-way DC-AC converter further includes The filter capacitor being connected between the full-bridge or the DC terminal of half-bridge inverter.
9. two-way DC-AC converter according to claim 1, which is characterized in that the two-way DC-AC converter further includes Control device is used for:
When AC power failure, the full-bridge or half-bridge inverter are controlled so that the direct current of its DC terminal is converted to the first friendship Flow square wave, and the control AC-AC converter so that second ac square wave at its first exchange end is converted to industrial-frequency alternating current, Wherein the period of first ac square wave and the second ac square wave is the pulsewidth tune for being supplied to the full-bridge or half-bridge inverter The period of signal processed；
When AC power source is normal, the AC-AC converter is controlled so that the industrial-frequency alternating current at its second exchange end is converted to the Three ac square waves, and the control full-bridge or half-bridge inverter are converted to direct current with the 4th ac square wave for being exchanged end The period of electricity, the third ac square wave and the 4th ac square wave is the pulsewidth modulation for being supplied to the full-bridge or half-bridge inverter The period of signal.
10. a kind of control method for two-way DC-AC converter as described in claim 1, the full-bridge inverter include It is connected to the first switch tube and second switch of its DC terminal in turn, and is connected to the third switching tube of its DC terminal in turn With the 4th switching tube, the half-bridge AC-AC converter includes: the 5th switching tube and the 6th switching tube of differential concatenation, and anti- To concatenated 7th switching tube and the 8th switching tube；Wherein when the 5th switching tube and the 7th switching tube are controlled as being connected When, the 6th switching tube, the 8th switching tube and two capacitors constitute the first half-bridge inverter, and work as the 6th switching tube When being controlled as conducting with the 8th switching tube, it is inverse that the 5th switching tube, the 7th switching tube and two capacitors constitute the second half-bridge Become device, which is characterized in that the control method includes:
In just half power frequency period, the first switch tube and second switch alternate conduction are controlled, controls the third switch Pipe and the 4th switching tube alternate conduction control the 5th and the 7th switching tube conducting, control the 6th and the 8th switching tube Alternate conduction；
In minus half power frequency period, the first switch tube and second switch alternate conduction are controlled, controls the third switch Pipe and the 4th switching tube alternate conduction, control the 5th and the 7th switching tube alternate conduction, and control the described 6th and the 8th is opened Close pipe conducting.
11. control method according to claim 10, which is characterized in that
In just half power frequency period, the pulse-width signal ratio provided to the 6th switching tube is provided to the 4th switching tube Pulse-width signal postpone first time period, to the 4th switching tube provide pulse-width signal ratio opened to described first It closes the pulse-width signal that pipe provides and postpones second time period；And to the 8th switching tube provide pulse-width signal ratio to The pulse-width signal that the third switching tube provides postpones first time period, the pulsewidth modulation provided to the third switching tube Signal postpones second time period than the pulse-width signal provided to the second switch；
In minus half power frequency period, the pulse-width signal ratio provided to the 7th switching tube is provided to the 4th switching tube Pulse-width signal postpone first time period, to the 4th switching tube provide pulse-width signal ratio opened to described first It closes the pulse-width signal that pipe provides and postpones second time period；And to the 5th switching tube provide pulse-width signal ratio to The pulse-width signal that the third switching tube provides postpones first time period, the pulsewidth modulation provided to the third switching tube Signal postpones second time period than the pulse-width signal provided to the second switch.
12. control method according to claim 10, which is characterized in that
In just half power frequency period, the pulse-width signal ratio provided to the second switch is provided to the 8th switching tube Pulse-width signal postpone the third period, to the 8th switching tube provide pulse-width signal ratio opened to the described 4th It closes the pulse-width signal that pipe provides and postponed for the 4th period；And to the first switch tube provide pulse-width signal ratio to The pulse-width signal that 6th switching tube provides postpones the third period, the pulsewidth modulation provided to the 6th switching tube Signal postponed for the 4th period than the pulse-width signal provided to the third switching tube；
In minus half power frequency period, the pulse-width signal ratio provided to the second switch is provided to the 5th switching tube Pulse-width signal postpone the third period, to the 5th switching tube provide pulse-width signal ratio opened to the described 4th It closes the pulse-width signal that pipe provides and postponed for the 4th period；And to the first switch tube provide pulse-width signal ratio to The pulse-width signal that 7th switching tube provides postpones the third period, the pulsewidth modulation provided to the 7th switching tube Signal postponed for the 4th period than the pulse-width signal provided to the third switching tube.
13. control method according to claim 10, which is characterized in that mentioned to the first switch tube and the 4th switching tube The pulse-width signal for being zero for delay inequality provides the pulsewidth tune that delay inequality is zero to the second switch and third switching tube Signal processed；And
In just half power frequency period, provided to the pulse-width signal ratio that the 6th switching tube provides to the first switch tube Pulse-width signal postpone the 5th period, to the 8th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the 5th period；
In minus half power frequency period, provided to the pulse-width signal ratio that the 7th switching tube provides to the first switch tube Pulse-width signal postpone the 5th period, to the 5th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the 5th period.
14. control method according to claim 10, which is characterized in that mentioned to the first switch tube and the 4th switching tube The pulse-width signal for being zero for delay inequality provides the pulsewidth tune that delay inequality is zero to the second switch and third switching tube Signal processed；And
In just half power frequency period, the pulse-width signal ratio provided to the first switch tube is provided to the 6th switching tube Pulse-width signal postpone the 6th period, to the 6th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the 7th period；To the second switch provide pulse-width signal ratio to institute The pulse-width signal for stating the offer of the 8th switching tube postponed for the 6th period, believed to the pulsewidth modulation that the 8th switching tube provides Number postponed for the 7th period than the pulse-width signal that provides to the first switch tube；
In minus half power frequency period, the pulse-width signal ratio provided to the first switch tube is provided to the 7th switching tube Pulse-width signal postpone the 6th period, to the 7th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the 7th period；To the second switch provide pulse-width signal ratio to institute The pulse-width signal for stating the offer of the 5th switching tube postponed for the 6th period, believed to the pulsewidth modulation that the 5th switching tube provides Number postponed for the 7th period than the pulse-width signal that provides to the first switch tube.
15. control method according to claim 9, the half-bridge inverter includes be connected to its DC terminal in turn first Switching tube and second switch, the half-bridge AC-AC converter include: the 5th switching tube and the 6th switching tube of differential concatenation, And the 7th switching tube and the 8th switching tube of differential concatenation；Wherein when the 5th switching tube and the 7th switching tube are controlled as When conducting, the 6th switching tube, the 8th switching tube and two capacitors constitute the first half-bridge inverters, and open when the described 6th Close pipe and when the 8th switching tube is controlled as conducting, the 5th switching tube, the 7th switching tube and two capacitors constitute the second half Bridge inverter, which is characterized in that the control method includes:
In just half power frequency period, the first switch tube and second switch alternate conduction are controlled, control the described 5th and the The conducting of seven switching tubes, controls the 6th and the 8th switching tube alternate conduction；
In minus half power frequency period, the first switch tube and second switch alternate conduction are controlled, control the described 5th and the Seven switching tube alternate conductions control the 6th and the 8th switching tube conducting.
16. control method according to claim 15, which is characterized in that
In just half power frequency period, provided to the pulse-width signal ratio that the 6th switching tube provides to the first switch tube Pulse-width signal postpone the 8th period, to the 8th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the 8th period；
In minus half power frequency period, provided to the pulse-width signal ratio that the 7th switching tube provides to the first switch tube Pulse-width signal postpone the 8th period, to the 5th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the 8th period.
17. control method according to claim 15, which is characterized in that
In just half power frequency period, the pulse-width signal ratio provided to the first switch tube is provided to the 6th switching tube Pulse-width signal postpone the 9th period, to the 6th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the tenth period；To the second switch provide pulse-width signal ratio to institute The pulse-width signal for stating the offer of the 8th switching tube postponed for the 9th period, believed to the pulsewidth modulation that the 8th switching tube provides Number postponed for the tenth period than the pulse-width signal that provides to the first switch tube；
In minus half power frequency period, the pulse-width signal ratio provided to the first switch tube is provided to the 7th switching tube Pulse-width signal postpone the 9th period, to the 7th switching tube provide pulse-width signal ratio opened to described second It closes the pulse-width signal that pipe provides and postponed for the tenth period；To the second switch provide pulse-width signal ratio to institute The pulse-width signal for stating the offer of the 5th switching tube postponed for the 9th period, believed to the pulsewidth modulation that the 5th switching tube provides Number postponed for the tenth period than the pulse-width signal that provides to the first switch tube.
CN201711474737.7A 2017-12-29 2017-12-29 Two-way DC-AC converter and its control method Pending CN109995264A (en)

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