CN107425734B - Direct AC-AC frequency converter and control method based on magnetic resonance coupling wireless power transmission - Google Patents
Direct AC-AC frequency converter and control method based on magnetic resonance coupling wireless power transmission Download PDFInfo
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- CN107425734B CN107425734B CN201710547281.6A CN201710547281A CN107425734B CN 107425734 B CN107425734 B CN 107425734B CN 201710547281 A CN201710547281 A CN 201710547281A CN 107425734 B CN107425734 B CN 107425734B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M5/00—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases
- H02M5/02—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc
- H02M5/04—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters
- H02M5/22—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M5/275—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M5/297—Conversion of ac power input into ac power output, e.g. for change of voltage, for change of frequency, for change of number of phases without intermediate conversion into dc by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal for conversion of frequency
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
- H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention discloses a kind of direct AC-AC frequency converters and control method based on magnetic resonance coupling wireless power transmission, direct AC-AC frequency converter includes sequentially connected primary side drive module, magnetic resonance coupling transmission module and direct AC-AC frequency-variable module, the direct AC-AC frequency-variable module includes: two-way full-bridge circuit, it is connected with magnetic resonance coupled transfer module output end, power electronics two-way switch is provided on each bridge arm；Low-pass filter is filtered the output of the two-way full-bridge circuit.The present invention realizes direct AC-AC frequency conversion under the conditions of strong magnetic coupling wireless power transmission, simplifies circuit, improves system effectiveness；Circuit structure is simple, reliable, and control program is novel and practical.The present invention is based on the direct AC-AC frequency converters of magnetic resonance coupling wireless power transmission can be widely applied in fields such as drive and control of electric machine, household electrical appliance.
Description
Technical field
The present invention relates to wireless power transmission and power electronics fields, more particularly to a kind of magnetic resonance that is based on to couple
The direct AC-AC frequency converter and control method of wireless power transmission.
Background technique
Frequency converter has pole extensive use in fields such as drive and control of electric machine, household electrical appliance.Currently, having some researchs is to use
AC-AC is carried out after simple topology transformation directly to convert.Some prior arts utilize bidirectional power electronic switch by Boost DC-
DC converter transform what BoostAC-AC was directly converted as, such as Liu Zhoucheng, flood peak, " Boost type AC-AC direct converter ", electricity
Gas transmission, the 5th phase of volume 38,2008.5, PP:28-30.Some prior arts utilize bidirectional power electronic switch by Buck
DC-DC converter transform BuckAC-AC as and directly converts, such as flood peak, Sun Gang, Wang Huizhen, and " Buck type AC/AC directly becomes
Parallel operation ", electrotechnics journal, the 8th phase of volume 22, in August, 2007, PP:73-76.This two classes topological circuit is suitable for carrying out electricity
Pressure amplitude value is adjusted, and then has limitation for frequency conversion output.
Some prior arts study the source Z AC/AC converter, such as Qiao Xinhui, and " high-frequency resistance source type AC/AC becomes
Flow the research of device ", Master's thesis, Shanghai Communications University, in January, 2010.Some prior arts use high frequency isolation type half-bridge three
Level scheme constructs AC-AC direct converter, such as Zhu Jingsong, Li Lei's " a kind of novel isolated three level AC-AC converter ", electricity
Power automation equipment, in December, 2012,12 phases of volume 32, PP.53-57.
It is the indirect variable-frequency solutions of AC-DC-AC, i.e., inversion after first rectifying that variable-frequency solutions, which are widely used, in another kind.Some are existing
Technology has carried out single-stage high-frequency AC/AC converter research, such as Zou Can, " single-stage high-frequency AC/AC converter for LED drive power
Research ", Master's thesis, University Of Chongqing, in April, 2014.If author illustrates in the text, the converter is " by PFC list
Member and high frequency DC/AC converter unit are integrated by common switch pipe, control and driving circuit simplification ", it still can be considered AC-
DC-AC indirect conversion scheme.
Currently, there is not been reported for the direct AC-AC converter technology scheme under strong magnetic coupling wireless power transmission technology.
Summary of the invention
The present invention propose it is a kind of based on magnetic resonance coupling wireless power transmission direct AC-AC converter circuit and make its tool
The control method that standby sinewave output and pressure-variable frequency conversion export solves real under strong magnetic coupling wireless power transmission technical conditions
Now the problem of direct AC-AC frequency converter.
A kind of direct AC-AC frequency converter based on magnetic resonance coupling wireless power transmission, including sequentially connected primary side are driven
Dynamic model block, magnetic resonance coupled transfer module and direct AC-AC frequency-variable module, the direct AC-AC frequency-variable module include:
Two-way full-bridge circuit is connected with magnetic resonance coupled transfer module output end, is provided with power electronics on each bridge arm
Two-way switch；
Low-pass filter is filtered the output of the two-way full-bridge circuit.
The input of primary side drive module of the invention is power supply, the primary side input of outlet side and magnetic resonance coupled transfer module
Side is connected；Direct AC-AC frequency-variable module, input terminal are connect with the output end of magnetic resonance coupled transfer module, AC-AC frequency conversion mould
The output of block is the entire directly AC-AC frequency converter output of the present invention, exports the alternating current of desired frequency.
In the present invention:
Primary side drive module, the primary side high-frequency drive for the transmission of magnetic resonance manifold type；
Magnetic resonance coupled transfer module, for carrying out the high frequency magnetic resonance manifold type energy transmission on former and deputy side；
Direct AC-AC frequency-variable module, carries out direct AC-AC frequency conversion, exports the alternating current of expected frequency.
The direct AC-AC frequency-variable module of circuit of the present invention, using the direct AC-AC variable-frequency solutions of single-stage, input terminal is high frequency
Input, output end are frequency reducing output, and since input frequency is high frequency, therefore inputting between frequency and output frequency has sizable frequency
Rate ratio K, can be used and carry out direct down-conversion output.
Magnetic resonance coupled transfer module of the present invention can be suitble to shape using serial-parallel topology, actual use for other
The topology of formula, specific choice is according to actual demand.
Preferably, the low-pass filter is LC filter, output end of the capacitor both ends as AC-AC frequency-variable module.
As for low-pass filter in order to realize its function can also use other forms physical circuit.
Preferably, whole system is additionally provided with controller, it is two-way for controlling each power electronics in two-way full-bridge circuit
It switches on-off；It is also used to control primary side drive module to control the amplitude of magnetic resonance coupled transfer module output.
Existing hardware itself can be used with regard to controller, or use the mode of software and hardware combining to configure corresponding control
Algorithm.The hardware components of controller can both be packaged together with other modules, can also by the way of external data line with
Corresponding controlled module is connected.
Preferably, the power electronics two-way switch is formed by two identical MOSFET differential concatenations, and two
MOSFET is controlled by the controller.
Power electronics two-way switch in the present invention not only can be by Metal-Oxide Semiconductor field effect transistor
MOSFET differential concatenation forms, can also be by (no two pole of inverse parallel two reverse blocking insulated gate bipolar transistor RB-IGBT
Pipe) reverse parallel connection forms, further, it is possible to be that can arbitrarily complete the power electronic devices of alternating-current switch task to constitute.
The frequency conversion output control method of direct AC-AC frequency converter of the present invention are as follows: by controlling power electronics two-way opened
It closes and constitutes forward and reverse rectification circuit, the switching cycle for controlling forward and reverse rectification circuit carries out frequency conversion output.
Direct AC-AC frequency-variable module is made of two-way full-bridge circuit with low-pass filter, and two-way full-bridge circuit is by electric power
Electronics two-way switch is constituted, and may be constructed forward and reverse rectification circuit by controlling power electronics two-way switch.By control just,
Frequency conversion output may be implemented in the switching cycle of anti-rectification circuit.
Preferably, by TOTemporally it is divided into multiple periods, input side corresponds to the T of respective numbers within each periodR
Half period；With TRHalf period, according to area equivalence principle, the different periods distributed respective numbers as a basic unit
TRHalf period is fitted, and is filtered to obtain required output waveform by low-pass filter.
Wherein TOFor the outlet side period of AC-AC frequency-variable module；TRFor the input side period of direct AC-AC frequency-variable module.
Area of the present invention is equivalent do not limit strictly it is identical, but in allowable error as close possible to.
Preferably, the TOTemporally it is divided into multiple periods.I.e. multiple period length are identical, convenient for divide with
And it calculates.
Preferably, calculating frequency conversion outlet side voltage waveform u for each periodOIn the period corresponding area,
With half T before frequency conversionRThe area of impulse waveform is that basic unit obtains needed for current slot according to area equivalence principle
Half TRThe quantity x of impulse waveform；On-off by controlling each power electronics two-way switch is rectified, so that the two-way full-bridge
X needed for circuit output half TRImpulse waveform, and frequency conversion output is carried out after low-pass filtered device.
Preferably, being directed to the input side voltage waveform u of direct AC-AC frequency-variable module simultaneouslyRAmplitude be adjusted.
Preferably, by the duty ratio of change primary side drive module output to adjust input side voltage waveform uR。
When being controlled for primary side drive module, primary side drive module can be connected by the controller and be controlled,
Also it can according to need and controller be separately configured for primary side drive module.
Preferably, being directed to frequency conversion outlet side voltage waveform uOEvery half period, when dividing the period, setting is flexible
Period, the flexible time section is with uOIt is symmetrical centered on peak point；Other time section carries out pair in flexible time section two sides
Claim distribution.Under normal circumstances, the control of output sinusoidal waveform will be not suitable for strictly carrying out time equal part, it is contemplated that pair of sinusoidal waveform
Title property extends or shortens the u comprising output sine wave peak point in the interior periodRPeriodicity, keep it in the half period by
According to peak value point symmetry to be segmented.
Preferably, can also adjust the amplitude of the output waveform of magnetic resonance coupling transmission module preferably to make each period
The output waveform area and it is expected obtained sine wave u that internal control is madeOCorresponding period inner area is equal.
The present invention realizes direct AC-AC frequency conversion, simplifies circuit under the conditions of strong magnetic coupling wireless power transmission, improves
System effectiveness；Circuit structure is simple, reliable, and control program is novel and practical.The present invention is based on magnetic resonance coupling radio energies to pass
Defeated direct AC-AC frequency converter can be widely applied in fields such as drive and control of electric machine, household electrical appliance.
Detailed description of the invention
Fig. 1 is the present invention directly AC-AC frequency changer block diagram；
Fig. 2 is the main circuit diagram of the present invention directly AC-AC frequency converter；
Fig. 3 is the equivalent circuit of Fig. 2 forward direction rectification；
Fig. 4 is the equivalent circuit of Fig. 2 negative sense rectification；
Fig. 5 is output waveform control schematic diagram in the T3 period in embodiment 1；
Fig. 6 is T3 period inner area equivalent schematic in embodiment 1；
Fig. 7 is f in embodiment 3R=100kHz, fOOutput waveform control schematic diagram when=495Hz；
Fig. 8 is the partial enlarged view in Fig. 7 near flexible time.
Specific embodiment
Referring to Fig. 1, direct AC-AC frequency converter of the present embodiment based on magnetic resonance coupling wireless power transmission includes for primary side
Drive module, magnetic resonance coupled transfer module, direct AC-AC frequency-variable module and controller (being omitted in figure).
Primary side drive module output connection magnetic resonance coupled transfer module input, magnetic resonance coupled transfer module it is defeated
The input of direct AC-AC frequency-variable module is connected out, and the output of directly AC-AC frequency-variable module is the present invention directly AC-AC frequency conversion
The final output of device.
Referring to fig. 2~Fig. 4, the direct AC-AC frequency converter of the present embodiment use direct conversion scheme, i.e. AC-AC single stage shift
Scheme.
Primary side drive module 1 can be not only restricted to certain specific topological project or control program with flexible design, can be according to
Relevant design is carried out according to the prior art, and will not be described here in detail.
Magnetic resonance coupled transfer module 2 is in series with capacitor Cp and inductance Lp using serial-parallel topology, i.e. input side, defeated
Side is parallel with capacitor Cs and inductance Ls out.Actual use can be any appropriate topology, and specific choice is according to actual demand.
Direct AC-AC frequency-variable module 3 is using full-bridge circuit topology, including what is be made of power electronics two-way switch S1-S4
Full-bridge circuit and inductance LOWith capacitor COThe low-pass filter of composition forms.
Power electronics two-way switch S1-S4 is by two identical Metal-Oxide Semiconductor field effect transistors
MOSFET differential concatenation forms, i.e. the source electrode of upper tube and the drain electrode of down tube is connected, electric based on the drain electrode of upper tube and the source electrode of down tube
The grid grade drive control of flow port and upper and lower two pipe separates.
By taking S1 as an example, when control terminal G11 applies driving signal, upper tube Q11Conducting, electric current can be from Q11、D12From top to bottom
Pass through；When control terminal G12 applies driving signal, down tube Q12 conducting, electric current can be from Q12、D11Pass through from bottom to top.It is other each
The control of power electronics two-way switch S2, S3 and S4 and S1 complete class are same, repeat no more.
Due to magnetic resonance coupling frequency fHUp to tens kHz to 10MHz are even higher, and output frequency is generally less than
100Hz or more low frequency, therefore magnetic resonance coupling frequency fHMuch higher than output frequency fO.For convenience of description, magnetic resonance coupling is defined
Frequency fRWith output frequency fOFrequency ratio fR/fO=K.Such as magnetic resonance coupling frequency fR=100kHz, output frequency fO=
50Hz, then K=2000.
Fig. 3 is that the present invention is based on the forward direction rectification of the direct AC-AC frequency converter of magnetic resonance coupling wireless power transmission is equivalent
Circuit.
It will wish that the AC wave shape exported is divided into positive and negative two parts, when it is desirable that exporting positive half, control terminal G11,
G21, G31, G41 are latched to be exported without driving, Q11、Q21、Q31、Q41It is turned off, and each diode D12、D22、D32、D42Shutdown；Only
Apply driving signal to control terminal G12, G22, G32, G42 to control.Direct AC-AC frequency-variable module work is in forward direction at this time
Working condition is rectified, rectification equivalent circuit is as shown in Figure 3.
Fig. 4 is that the present invention is based on the negative sense rectification of the direct AC-AC frequency converter of magnetic resonance coupling wireless power transmission is equivalent
Circuit.
When it is desirable that exporting negative half part, control terminal G12, G22, G32, G42 are latched to be exported without driving, Q12、Q22、Q32、
Q42It is turned off, and each diode D11、D21、D31、D41Shutdown；Only to control terminal G11, G21, G31 and G41 apply driving signal into
Row control.Direct AC-AC frequency-variable module work rectifies working condition in negative sense at this time, and rectification equivalent circuit is as shown in Figure 4.
The present invention is by controlling each transistor G11, G21, G31, G41 and G12, G22, G32, G42 realize it is of the invention straight
AC-AC output is connect, controlling its switching frequency can realize that frequency conversion exports and its switching frequency is output frequency.
Output frequency of the invention/period control: magnetic resonance coupling frequency fRThe cycle T of known i.e. magnetic resonance couplingR
Know, and desired output frequency fODetermine i.e. output cycle TOIt is known that being rounded frequency ratio K for M=INT (K), and with M magnetic resonance
Coupling period TRCombination constitutes an output cycle TOEvery M magnetic resonance coupling half cycles control is that positive half period exports, every M
The control of magnetic resonance coupling half cycles is that negative half-cycle exports, and realizes output frequency control.
For example, magnetic resonance coupling frequency fR=100kHz, desired output frequency fO=49.5Hz, K=2020.2 is right
It is 2020 that K, which is rounded, every 2020 magnetic resonance coupling periods TRCombination constitutes an output cycle TO.Therefore, every 2020 magnetic resonances
Coupling half cycles control circuit of the present invention as positive half period output, and every 2020 magnetic resonance coupling half cycles control circuit of the present invention
For negative half-cycle output, completion output frequency/period is controlled, actual output frequency 49.505Hz, and error is minimum.
Embodiment 1
When specific control, it would be desirable to waveform u after sinusoidal AC wave form, that is, frequency conversion of outputOTemporally it is divided into 2N equal portions, i.e.,
It is divided into 2N period, then positive and negative half-wave includes N number of period, waveform u before distribution integer frequency conversion in each periodR
Half period, number are denoted as x, x uRU in half period and corresponding periodOWith equivalent area.
The size of x is by u in current slotOArea SP, uRArea S in half periodRIt is determined.
Shown in the calculating of x such as formula (1) (2):
In formula, B uRAmplitude, A uOAmplitude.
φiTo export angle, i.e. angle corresponding to current slot starting point corresponding to each Along ent of sine wave, and
Have
With fR=100kHz, fO=50Hz, K=2000 considers, if N=20, i.e., will export uOHalf period temporally etc.
It is divided into 20 sections, before frequency conversion, each period there are 100 50 uRPeriod, such as with half of uRPeriod as most basic assembled unit,
Then there are 100 u in each periodRHalf period, that is, optional range was 0~100 integer u for utilizingRHalf period is to obtain
U in the periodOEquivalent area.
In view of symmetry, with half of uOPeriod explanation, 20 periods corresponding area are as follows:
S20=[0.0123 0.0366 0.0600 0.0820 0.1019 0.1193 0.1338 0.1450 0.1526
0.1564 0.1564 0.1526 0.1450 0.1338 0.1193 0.1019 0.0820 0.0600 0.0366
0.0123]。
With uOMaximum area needs most u in periodRThe building of number of semi-periods of oscillation 100 calculates, then the u that each period needsR
Half period number are as follows:
x50_20=[8 23 38 52 65 76 86 93 98 100 100 98 93 86 76 65 52 38 23 8]；
The u needed due to each periodRHalf period number is related to rounding processing, therefore actually 20 periods are right respectively
Error (unit u is had between the area answeredRThe area of half period):
e50_20=[0.1298-0.4167-0.3867-0.4114-0.1456-0.2757 0.4723 0.3264
0.4623 0 0 0.4623 0.3264 0.4723 -0.2757 -0.1456 -0.4114 -0.3867 -0.4167
0.1298]。
This embodiment scheme control it is relatively easy, belonging to has poor control, since frequency ratio K is larger, therefore it is available very
Close to sinusoidal waveform output, and frequency ratio K is bigger, closer to sinusoidal.
As shown in figure 5, remark additionally by taking the 3rd period T3 as an example, each time including the T3 period
Duan Jun is corresponding with 100 uRHalf period, wherein period T3 was the 3rd period for control, corresponded to x50_20_3=38, only
Control 38 uRHalf period output, rest part do not export, i.e., except period T central region only remains with 38 u after rectificationR
Outside half period, other times region is not open-minded, and this point can be two-way by controlling each power electronics in two-way full-bridge circuit
Switch on-off realization.
For entire period T3, all u of outputRHalf period is located at the central region of period, other time section
Similarly.
Fig. 6 is area equivalent schematic corresponding in period T3,38 u corresponding to period T3RHalf period face
Hatched area S of the product as corresponding to itr_3, u corresponding to period T3OOutput waveform area corresponds to corresponding shade
Area Sp_3.In period T3, corresponding uOArea be Sp_3, with 38 u in the T3 periodRThe gross area S of half periodr_3Closely
Patibhaga-nimitta etc..
Embodiment 2
Compared with Example 1, the difference of the present embodiment is while equivalent area constructs, in order to reduce error, also
The input control to direct AC-AC frequency-variable module is realized by control primary side drive module, if primary side drive module is using adjusting
The scheme of PWM duty cycle controls uRAmplitude B, and finally control uOOutput waveform.
uRShown in the calculating of amplitude B such as formula (4):
X is u in each period after rectificationRThe number of half period, x uRU in half period and corresponding periodOWith etc.
Imitate area；Define xmaxFor the maximum value of x, and it is equal to u in a periodRHalf period number；N is in frequency conversion second half of the cycle
The period number for including；
With fR=100kHz, fOFor=25Hz, K=4000, N=40, amplitude A, B is normalized to 1.
In this example, u in a periodRHalf period number is 100, xmaxIt is 100.U in each periodRHalf period quantity
Distribution are as follows: x25-40=[4 12 20 27 35 42 49 56 62 68 73 79 83 87 91 94 96 98 99 100 100
99 98 96 94 91 87 83 79 73 68 62 56 49 42 35 27 20 12 4]。
The u needed due to each periodRHalf period number is related to rounding processing, and actually each period is corresponding
Error is had between area, in order to eliminate this error to strictly observe area equation principle, to primary side drive module controlled with
Control the amplitude of the output waveform of magnetic resonance coupled transfer module.Amplitude B is after being normalized in each period, result
Are as follows:
B25-40=[0.9823 0.9802 0.9762 1.0061 0.9897 0.9976 0.9980 0.9929 0.9993
0.9990 1.0067 0.9948 1.0025 1.0036 0.9987 0.9988 1.0033 1.0016 1.0039 1.0000
1.0000 1.0039 1.0016 1.0033 0.9988 0.9987 1.0036 1.0025 0.9948 1.0067 0.9990
0.9993 0.9929 0.9980 0.9976 0.9897 1.0061 0.9762 0.9802 0.9823]。
The variation of amplitude B is smaller, and fluctuation up and down, is advantageously implemented its control substantially near 1, this control program is nothing
Poor control program.
Embodiment 3
This implementation can be in conjunction with the embodiments 1 or embodiment 2, as a further improvement, for after frequency conversion in the present embodiment
Waveform uOEvery half period centered on the half period peak point, be symmetrically segmented in its two sides when dividing the period,
Period is divided into typical time section and flexible time section；
TORemaining time section after being divided into several typical time sections is used as flexible time section, the when appearance of each typical time section
Duration that is same and being greater than flexible time section；
All half T in control sequential, in flexible time sectionRIt is symmetrically distributed in half period uOPeak point two sides.
For under normal circumstances, the control of output sinusoidal waveform will be not suitable for strictly carrying out time equal part, it is contemplated that sine wave
The symmetry of shape extends or shortens the u comprising output sine wave peak point in the interior periodRPeriodicity keeps it in half cycle
According to peak value point symmetry to be segmented in phase.
uRThe calculating of amplitude B is modified on the basis of formula (4).As shown in formula (5):
X is u in each period after rectificationRThe number of half period, x uRU in half period and corresponding periodOWith etc.
Imitate area；H is the u of flexible time sectionRHalf period number defines xmaxFor the maximum value of x, and it is equal to u in a periodRHalf cycle
Phase number；
The period number that N includes by removing flexible time section in frequency conversion second half of the cycle.Such as fR=100kHz, fO=
When 49.5Hz, whole cycle is divided into 42 sections i.e. half period and is divided into 21 sections by K=2020.2.
One of them period is located at peak point middle position as flexible time section, that is, includes 20 uRHalf period and right
Title is distributed in peak point two sides；Remaining 20 period is typical time section T2, includes 100 uRHalf period.
In this example, in addition to for flexible time section, u in a periodRHalf period number is 100, xmaxIt is 100.When each
Between u in sectionRHalf period quantity is distributed as:
x49.5=[8 23 38 52 65 76 85 92 97 100 20 100 97 92 85 76 65 52 38 23
8]。
Amplitude B is after being normalized in each period, variation are as follows:
B49.5=[0.9753 1.0095 1.0020 1.0002 0.9953 0.9975 1.0012 1.0037 1.0035
1.0000 1.0024 1.0000 1.0035 1.0037 1.0012 0.9975 0.9953 1.0002 1.0020 1.0095
0.9753]。
Using integer uRInput half period scheme, which will lead to rate-adaptive pacemaker, error, since time error is up to half
uRPeriod, therefore fRBigger error is smaller.F under wireless power transmissionRGeneral bigger, error can receive, this reality is defeated
Frequency 49.505Hz out, error are only 0.005Hz, can be received.
In order to further illustrate being illustrated by taking the positive half-wave of sine wave as an example, and assume magnetic resonance coupling frequency
fR=100kHz, desired output frequency are fO=495Hz, then frequency ratio K=fR/fO=202.2, actually take M=INT (K)=
202, i.e., with 202 magnetic resonance coupling period TRCombination constitutes an output cycle TO, actual output frequency 495.05Hz, accidentally
Difference is minimum.
Referring to Fig. 7, the entire output waveform period is divided into the 42 periods i.e. half period and was divided into for 21 periods, one of them when
Between section be 2 uRHalf period and the peak point of output waveform is placed on time period, remaining 20 period duration is equal, is
10 uRHalf period.
In this example, in addition to for flexible time section, u in a periodRHalf period number is 10, xmaxIt is 10.Each time
U in sectionRHalf period quantity is distributed as:
x495=[1 2456899 10 10 2 10 10 9986542 1].
The u needed due to each periodRHalf period number is related to rounding processing, and actually each period is corresponding
Error is had between area, in order to eliminate this error to strictly observe area equation principle, to primary side drive module controlled with
Control the amplitude of the output waveform of magnetic resonance coupled transfer module.Amplitude B is after being normalized in each period, result
Are as follows:
B495=[0.7802 1.1609 0.9519 1.0402 1.0782 0.9477 0.9456 1.0260 0.9734
1.0000 1.0024 1.0000 0.9734 1.0260 0.9456 0.9477 1.0782 1.0402 0.9519 1.1609
0.7802]。
Note: output frequency is generally less than and is equal to work frequency 50/60Hz in real work, proposes herein to be schematically illustrate
Output frequency 495Hz.
Disclosed above is only specific embodiments of the present invention, but the present invention is not limited to this, the technology of this field
Various changes and modifications can be made to the invention by personnel without departing from the spirit and scope of the present invention.Obviously these changes and change
Type should belong to the present invention claims protection scope protection in.In addition, although being used some specific terms in this specification,
These terms are merely for convenience of description, does not constitute to the present invention any specifically limited.
Claims (6)
1. a kind of direct AC-AC frequency converter based on magnetic resonance coupling wireless power transmission, including the driving of sequentially connected primary side
Module, magnetic resonance coupled transfer module and direct AC-AC frequency-variable module, which is characterized in that the direct AC-AC frequency-variable module
Include:
Two-way full-bridge circuit is connected with magnetic resonance coupled transfer module output end, and it is two-way to be provided with power electronics on each bridge arm
Switch；
Low-pass filter is filtered the output of the two-way full-bridge circuit；
The frequency converter is for implementing method control as follows:
Forward and reverse rectification circuit is constituted by control power electronics two-way switch, controls the switching cycle of forward and reverse rectification circuit
Carry out frequency conversion output；
By TOTemporally it is divided into multiple periods, input side corresponds to the T of respective numbers within each periodRHalf period；With TRHalf
Period, according to area equivalence principle, the different periods distributed the T of respective numbers as a basic unitRHalf period carries out
Fitting, and be filtered to obtain required output waveform by low-pass filter；Wherein TOFor the outlet side of AC-AC frequency-variable module
Period；TRFor the input side period of direct AC-AC frequency-variable module；
Define magnetic resonance coupling frequency fRWith output frequency fOFrequency ratio fR/fO=K；Integer frequency conversion is distributed in each period
Preceding waveform uRHalf period, number are denoted as x,
The size of x is by u in current slotOArea SP, uRArea S in half periodRIt is determined,
Shown in the calculating of x such as formula (1) (2):
In formula, B uRAmplitude, A uOAmplitude,
φiTo export angle, i.e. angle corresponding to current slot starting point corresponding to each Along ent of sine wave, and have
For frequency conversion outlet side voltage waveform uOEvery half period, when dividing the period, be arranged flexible time section, this flexibly
Period is with uOIt is symmetrical centered on peak point；Other time section carries out symmetrical in flexible time section two sides；
It is directed to the input side voltage waveform u of direct AC-AC frequency-variable module simultaneouslyRAmplitude be adjusted.
2. the direct AC-AC frequency converter as described in claim 1 based on magnetic resonance coupling wireless power transmission, feature exist
In the low-pass filter is LC filter, output end of the capacitor both ends as AC-AC frequency-variable module.
3. the direct AC-AC frequency converter as described in claim 1 based on magnetic resonance coupling wireless power transmission, feature exist
In controller being additionally provided with, for controlling the on-off of each power electronics two-way switch in two-way full-bridge circuit；It is also used to control original
Side drive module is to control the amplitude that magnetic resonance coupled transfer module exports.
4. the direct AC-AC frequency converter as claimed in claim 3 based on magnetic resonance coupling wireless power transmission, feature exist
In the power electronics two-way switch is formed by two identical MOSFET differential concatenations, and two MOSFET difference are controlled
In the controller.
5. the control method of directly AC-AC frequency converter as described in claim 1, which is characterized in that for each period, meter
Calculate frequency conversion outlet side voltage waveform uOIn the period corresponding area, with half T before frequency conversionRThe area of impulse waveform is basic
Unit obtains half T needed for current slot according to area equivalence principleRThe quantity x of impulse waveform；By controlling each electric power
The on-off of electronics two-way switch is rectified, so that x half T needed for the two-way full-bridge circuit outputRImpulse waveform, and pass through
Frequency conversion output is carried out after low-pass filter.
6. the control method of directly AC-AC frequency converter as claimed in claim 5, which is characterized in that the TOTemporally it is divided into
Multiple periods.
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