CN108199602B - Multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter - Google Patents

Multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter Download PDF

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CN108199602B
CN108199602B CN201810019194.8A CN201810019194A CN108199602B CN 108199602 B CN108199602 B CN 108199602B CN 201810019194 A CN201810019194 A CN 201810019194A CN 108199602 B CN108199602 B CN 108199602B
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CN108199602A (en
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陈道炼
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Qingdao University
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Qingdao University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/66—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal
    • H02M7/68—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters
    • H02M7/72—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/79—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/797—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output with possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02J3/382—
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33584—Bidirectional converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/337—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in push-pull configuration
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/0083—Converters characterised by their input or output configuration
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E10/00—Energy generation through renewable energy sources
    • Y02E10/70—Wind energy
    • Y02E10/76—Power conversion electric or electronic aspects

Abstract

The invention relates to a multi-winding time-sharing power supply forward direct current chopping type single-stage multi-input high-frequency chain inverter, which is formed by connecting a plurality of isolated input filters and a shared output filter circuit by a combined multi-input single-output isolated bidirectional forward direct current chopper, wherein each input end of the combined multi-input single-output isolated bidirectional forward direct current chopper is correspondingly connected with each output end of the input filter in a one-to-one mode, and the output end of the combined multi-input single-output isolated bidirectional forward direct current chopper is connected with the output filter circuit. The inverter has the characteristics of multi-input source electrical isolation, time-sharing power supply, output and input high-frequency isolation, simple circuit topology, single-stage power conversion, high power density, high conversion efficiency, high output waveform quality, wide application prospect and the like, and lays a key technology for realizing a medium-high-capacity distributed power supply system for jointly supplying power by various new energy sources.

Description

Multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter
Technical Field
The invention relates to a multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter, belonging to the power electronic conversion technology.
Background
The inverter is a static converter which applies a power semiconductor device to convert unstable and poor direct current electric energy into stable and good alternating current electric energy, and is used for alternating current loads or realizes alternating current grid connection. Inverters with low-frequency electrical isolation or high-frequency electrical isolation are arranged between an output alternating-current load or an alternating-current power grid and an input direct-current power supply and are respectively called low-frequency chain inverters and high-frequency chain inverters. The electrical isolation element plays a major role in the inverter: (1) the electrical isolation between the output and the input of the inverter is realized, and the safety reliability and the electromagnetic compatibility of the operation of the inverter are improved; (2) the matching between the output voltage and the input voltage of the inverter is realized, namely the technical effect that the output voltage of the inverter is higher than, equal to or lower than the input voltage is realized, and the application range of the inverter is greatly widened; (3) when the working frequency of the high-frequency transformer or the high-frequency energy storage type transformer is above 20kHz, the volume and the weight of the transformer are greatly reduced, and audio noise is eliminated. Therefore, the inverter has an important application value in secondary power conversion using a dc generator, a battery, a photovoltaic cell, a fuel cell, or the like as a main dc power source.
The new energy sources (also called green energy sources) such as solar energy, wind energy, tidal energy, geothermal energy and the like have the advantages of cleanness, no pollution, low price, reliability, richness and the like, thereby having wide application prospect. Due to the increasing shortage of traditional fossil energy (non-renewable energy) such as petroleum, coal and natural gas, serious environmental pollution, global warming, nuclear waste generated by nuclear energy production, environmental pollution and the like, the development and utilization of new energy are receiving more and more attention. The new energy power generation mainly comprises photovoltaic, wind power, fuel cells, water power, geothermal energy and the like, and all the types have the defects of unstable and discontinuous power supply, change along with climatic conditions and the like, so that a distributed power supply system adopting various new energy sources for combined power supply is needed.
A traditional new energy distributed power supply system is shown in figures 1 and 2. The system generally adopts a plurality of single-input direct-current converters to convert electric energy of new energy power generation equipment which does not need energy storage, such as photovoltaic cells, fuel cells, wind driven generators and the like, through one unidirectional direct-current converter respectively, and the output ends of the new energy power generation equipment are connected to a direct-current bus of a common inverter in parallel or in series, so that the combined power supply of various new energy sources is ensured, and the coordinated work can be realized. The distributed power generation system realizes the priority utilization of the power supplied by a plurality of input sources to the load and the energy, improves the stability and the flexibility of the system, but has the defects of two-stage power conversion, low power density, low conversion efficiency, high cost and the like, and the practicability of the distributed power generation system is limited by a great degree.
In order to simplify the circuit structure and reduce the number of power conversion stages, a novel single-stage new energy distributed power supply system needs to be formed by replacing the conventional multi-input inverter with a direct-current converter and an inverter two-stage cascade circuit structure shown in fig. 1 and 2 by the novel multi-input inverter with a single-stage circuit structure shown in fig. 3. The single-stage multi-input inverter allows for multiple new energy inputs, and the nature, magnitude and characteristics of the input sources may be the same or may vary widely. The novel single-stage new energy distributed power supply system has the advantages of simple circuit structure, single-stage power conversion, low cost and the like, and a plurality of input sources simultaneously or in time-sharing mode supply power to a load in one high-frequency switching period.
Therefore, the active search for a single-stage multi-input inverter allowing multiple new energy sources to supply power jointly and a new energy source distributed power supply system thereof is urgent, and the active search has a very important significance for improving the stability and flexibility of the system and realizing the prior utilization or the full utilization of the new energy sources.
Disclosure of Invention
The invention aims to provide a multi-winding time-sharing power supply forward DC chopper type single-stage multi-input high-frequency chain inverter which has the characteristics of joint power supply of various new energy sources, mutual isolation of input DC power supplies, multi-input single-output isolation bidirectional forward DC chopper, multiple-input single-output high-frequency transformers, high-frequency isolation between output and input, time-sharing power supply of multiple input power supplies to a load, simple circuit topology, single-stage power conversion, high conversion efficiency, high output waveform quality, large output capacity, wide application prospect and the like.
The technical scheme of the invention is as follows: a multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter is formed by connecting a plurality of mutually isolated input filters and a shared output filter circuit by a combined multi-input single-output isolation bidirectional forward direct current chopper; the combined multi-input single-output isolation bidirectional forward direct current chopper is formed by reversely connecting each input end of two identical multi-input single-output isolation bidirectional forward direct current choppers which respectively output low-frequency positive half-cycle and low-frequency negative half-cycle unipolar pulse width modulation voltage waves in parallel with the output ends in a one-to-one correspondence mode, and the two non-serial output ends of the two multi-input single-output isolation bidirectional forward direct current choppers are the output ends of the combined multi-input single-output isolation bidirectional forward direct current chopper; each multi-input single-output isolation bidirectional forward direct current chopper is formed by connecting a plurality of mutually isolated bidirectional power flow single-input single-output high-frequency inverter circuits and a high-frequency rectifier formed by a shared rectification, follow current and polarity selection two-quadrant high-frequency power switch by a multi-input single-output high-frequency transformer, wherein each input end of the multi-input single-output high-frequency transformer is correspondingly connected with the output end of each high-frequency inverter circuit one by one, and the output end of the multi-input single-output high-frequency transformer is connected with the input end of the high-frequency rectifier; the input end of each high-frequency inverter circuit is the input end of the combined multi-input single-output isolation bidirectional forward direct current chopper, each high-frequency inverter circuit is composed of a four-quadrant high-frequency power switch and a two-quadrant high-frequency power switch or only composed of a four-quadrant high-frequency power switch, and the output filter circuit is composed of a filter inductor and a filter capacitor which are sequentially cascaded or composed of a filter inductor, a filter capacitor and a filter inductor which are sequentially cascaded.
The invention relates to a multi-input inverter circuit structure formed by two-stage cascading of a direct current converter and an inverter of a traditional multi-new-energy combined power supply system, which is constructed into a novel multi-winding time-sharing power supply single-stage multi-input inverter circuit structure, and provides a multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter circuit structure, a topology family and an energy management control strategy thereof, namely the circuit structure is formed by connecting a plurality of mutually isolated input filters and a shared output filter circuit through providing a combined multi-input single-output isolation bidirectional forward direct current chopper.
The multi-winding time-sharing power supply forward direct-current chopper type single-stage multi-input high-frequency chain inverter can invert a plurality of mutually isolated and unstable input direct-current voltages into stable and high-quality output alternating current required by a load, and has the characteristics of mutual isolation of multi-input direct-current power supplies, high output and input high-frequency isolation, time-sharing power supply of the multi-input power supplies to the load, simple circuit topology, single-stage power conversion, high conversion efficiency, high output waveform quality, high output medium capacity, wide application prospect and the like. The comprehensive performance of the multi-winding time-sharing power supply forward direct current chopping type single-stage multi-input high-frequency chain inverter is superior to that of a multi-input inverter formed by two-stage cascading of a traditional direct current converter and an inverter.
Drawings
Fig. 1 shows a conventional two-stage new energy distributed power supply system with a plurality of unidirectional dc converters connected in parallel at output terminals.
Fig. 2 shows a conventional two-stage new energy distributed power supply system with a plurality of unidirectional dc converters connected in series at output terminals.
Fig. 3 is a schematic block diagram of a novel single-stage multiple-input inverter.
Fig. 4 is a schematic block diagram of a multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter.
Fig. 5 is a circuit structure diagram of a multi-winding time-sharing power supply forward direct current chopping type single-stage multi-input high-frequency chain inverter.
Fig. 6 is a waveform diagram of a steady-state principle of the multi-winding time-sharing power supply forward-excitation direct-current chopper type single-stage multi-input high-frequency chain inverter controlled by an output voltage instantaneous value SPWM.
Fig. 7 is a schematic diagram of a single-tube forward dc chopper type circuit as an example of a multi-winding time-sharing power supply forward dc chopper type single-stage multi-input high-frequency-chain inverter circuit topology.
Fig. 8 is a schematic diagram of a circuit topology example of a multi-winding time-sharing power supply forward direct-current chopper type single-stage multi-input high-frequency chain inverter circuit, i.e., a push-pull full-wave direct-current chopper type circuit.
Fig. 9 is a schematic diagram of a three-push-pull bridge type direct current chopper type circuit topology example of a multi-winding time-sharing power supply forward direct current chopper type single-stage multiple-input high-frequency chain inverter.
Fig. 10 is a schematic diagram of a multi-winding time-sharing power supply forward direct-current chopper type single-stage multi-input high-frequency chain inverter circuit topology example four-push-pull forward full-wave direct-current chopper type circuit.
Fig. 11 is a schematic diagram of a circuit topology example of a multi-winding time-sharing power supply forward direct-current chopper type single-stage multi-input high-frequency chain inverter, i.e., a five-push forward bridge direct-current chopper type circuit.
Fig. 12 is a schematic diagram of a six-two-transistor forward dc chopper type circuit topology example of a multi-winding time-sharing power supply forward dc chopper type single-stage multi-input high-frequency chain inverter.
Fig. 13 is a schematic diagram of a circuit topology example of a multi-winding time-sharing power supply forward direct-current chopping type single-stage multi-input high-frequency chain inverter circuit, namely a half-bridge full-wave direct-current chopping type circuit.
Fig. 14 is a schematic diagram of a multi-winding time-sharing power supply forward direct-current chopper type single-stage multi-input high-frequency chain inverter circuit topology example eight-half-bridge direct-current chopper type circuit.
Fig. 15 is a schematic diagram of a multi-winding time-sharing power supply forward direct-current chopper type single-stage multi-input high-frequency chain inverter circuit topology example nine-full-bridge full-wave direct-current chopper type circuit.
Fig. 16 is a schematic diagram of a circuit topology example of a multi-winding time-sharing power supply forward direct-current chopper type single-stage multi-input high-frequency chain inverter, namely a full-bridge direct-current chopper type circuit.
Fig. 17 is a master-slave power distribution energy management control block diagram of an output voltage and an input current instantaneous value SPWM of a multi-winding time-sharing power supply single-tube type and double-tube type forward direct current chopper type single-stage multi-input high-frequency chain inverter.
Fig. 18 is a waveform diagram of the output voltage and input current instantaneous values SPWM master-slave power distribution energy management control principle of the multi-winding time-sharing power supply single-tube and double-tube forward direct current chopper type single-stage multi-input high-frequency chain inverter.
Fig. 19 is a master-slave power distribution energy management control block diagram of an output voltage and input current instantaneous value SPWM of a multi-winding time-sharing power supply push-pull type, push-pull forward type, half-bridge type, full-bridge type forward direct current chopper type single-stage multi-input high-frequency chain inverter.
Fig. 20 is a waveform diagram of the principle of master-slave power distribution energy management control of the output voltage and input current instantaneous values SPWM of the multi-winding time-sharing power supply push-pull type, push-pull forward type, half bridge type, full bridge type forward dc chopper type single-stage multiple-input high-frequency chain inverter.
Fig. 21 shows a multi-winding time-sharing power supply forward dc chopper type single-stage multiple-input high-frequency-chain independent power supply system with a single-stage isolated bidirectional charging/discharging converter connected in parallel at the output end.
Fig. 22, maximum power output energy management control strategy with single stage isolated bidirectional charge-discharge converter output voltage independent control loop.
FIG. 23, output voltage u of independent power supply systemoAnd outputting the filtered inductor current iLf、iLf' waveform.
Detailed Description
The technical solution of the present invention is further described below with reference to the drawings and examples of the specification.
The multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter is formed by connecting a plurality of mutually isolated input filters and a shared output filter circuit by a combined multi-input single-output isolation bidirectional forward direct current chopper, wherein each input end of the combined multi-input single-output isolation bidirectional forward direct current chopper is correspondingly connected with the output end of each input filter one by one, and the output end of the combined multi-input single-output isolation bidirectional forward direct current chopper is connected with the output filter circuit; the combined multi-input single-output isolation bidirectional forward direct current chopper is formed by reversely connecting each input end of two identical multi-input single-output isolation bidirectional forward direct current choppers which respectively output low-frequency positive half-cycle and low-frequency negative half-cycle unipolar pulse width modulation voltage waves in parallel with the output ends in a one-to-one correspondence mode, and the two non-serial output ends of the two multi-input single-output isolation bidirectional forward direct current choppers are the output ends of the combined multi-input single-output isolation bidirectional forward direct current chopper; each multi-input single-output isolation bidirectional forward direct current chopper is formed by connecting a plurality of mutually isolated bidirectional power flow single-input single-output high-frequency inverter circuits and a high-frequency rectifier formed by a shared rectification, follow current and polarity selection two-quadrant high-frequency power switch by a multi-input single-output high-frequency transformer, wherein each input end of the multi-input single-output high-frequency transformer is correspondingly connected with the output end of each high-frequency inverter circuit one by one, and the output end of the multi-input single-output high-frequency transformer is connected with the input end of the high-frequency rectifier; the input end of each high-frequency inverter circuit is the input end of the combined multi-input single-output isolation bidirectional forward direct current chopper, each high-frequency inverter circuit consists of a four-quadrant high-frequency power switch and a two-quadrant high-frequency power switch or only consists of a four-quadrant high-frequency power switch, and the output filter circuit consists of a filter inductor and a filter capacitor which are sequentially cascaded or consists of a filter inductor, a filter capacitor and a filter inductor which are sequentially cascaded; the multiple input sources of the inverter time-share power to the load during a high frequency switching cycle.
The schematic block diagram, the circuit structure and the steady-state principle waveform of the multi-winding time-sharing power supply forward DC chopper type single-stage multi-input high-frequency chain inverter during the control of the output voltage instantaneous value SPWM are respectively shown in FIGS. 4, 5 and 6. In FIGS. 4, 5 and 6, Ui1、Ui2、…、UinInputting a DC voltage source (n is a natural number greater than 1) for n paths, ZLFor single-phase output of AC loads, uo、ioRespectively a single phase output ac voltage (including ac grid voltage) and an ac current. The combined multi-input single-output isolated bidirectional forward DC chopper consists of two identical unipolar pulse width modulation voltage waves u which respectively output a low-frequency positive half cycle and a low-frequency negative half cycleo1、uo2Each input end of the multi-input single-output isolation bidirectional forward direct current chopper is in one-to-one correspondence and is formed by connecting output ends in reverse series, two non-serial output ends of the two multi-input single-output isolation bidirectional forward direct current choppers are the output ends of the combined multi-input single-output isolation bidirectional forward direct current chopper, two same multi-input single-output isolation bidirectional forward direct current choppers are respectively formed by connecting a plurality of mutually isolated bidirectional power flow single-input single-output high-frequency inverter circuits and a high-frequency rectifier formed by a shared rectification, follow current and polarity selection two-quadrant high-frequency power switch through a multi-input single-output high-frequency transformer, and are formed by sequentially cascading the plurality of single-input single-output high-frequency inverter circuits, the multi-input single-output high-frequency transformer, the shared rectification, follow current and polarity selection high-frequency rectifier, any time is equivalent to a bidirectional power flow single-input single-output isolation bidirectional forward direct current chopper. Two identical multi-input single-output isolation bidirectional forward direct current choppers work for half a low-frequency period in turn in a low-frequency output voltage period, namely when one direct current chopper works to output u of the low-frequency positive half periodo1While the other DC chopper is deactivated and the polarity selection is conducted with the two-quadrant power switch, uo2When it is equal to 0, the meridian goes throughSine alternating current u output after filterO、iOPositive half-cycle of (c); on the contrary, when a DC chopper works to output u of low-frequency negative half cycleo2While the other DC chopper is deactivated and the polarity selection is conducted with the two-quadrant power switch, u o10, and outputting sine alternating current u after passing through an output filterO、iONegative half cycles of (c). Each single-input single-output high-frequency inverter circuit consists of a four-quadrant high-frequency power switch and a two-quadrant high-frequency power switch or only consists of the four-quadrant high-frequency power switch, the shared high-frequency rectifier for rectification, follow current and polarity selection consists of the two-quadrant high-frequency power switches, and power devices such as an MOSFET (metal oxide semiconductor field effect transistor), an IGBT (insulated gate bipolar transistor), a GTR (thyristor controlled thyristor) and the like can be selected. The output filter circuit is formed by sequentially cascading a filter inductor and a filter capacitor or formed by sequentially cascading the filter inductor, the filter capacitor and the filter inductor, and a circuit diagram of an output LC filter suitable for a passive alternating current load and an output LCL filter suitable for an alternating current power grid load is drawn in the circuit diagram; the n-path input filter is an LC filter (filter inductor L with an added virtual frame)i1、Li2、…、Lin) Or a capacitor filter (filter inductor L without adding a virtual frame)i1、Li2、…、Lin) When an LC filter is adopted, the n input direct current paths are smoother. The n high-frequency inverter circuits in each multi-input single-output isolation bidirectional forward DC chopper respectively input a DC voltage source Ui1、Ui2、…、UinModulating into bipolar two-state multi-level high-frequency voltage square wave or bipolar three-state multi-level SPWM voltage wave u with amplitude depending on input direct-current voltageN111、uN121、…、uN1n1、uN211、uN221、…、uN2n1High frequency transformer T1、T2Isolation and high-frequency rectifier rectified into unipolar tri-state multi-level SPWM voltage wave uo1、uo2After output LC filtering, high quality sine AC voltage u is obtained on single-phase AC passive load or single-phase AC networkoOr sinusoidal alternating current ioN input pulse currents of each n-input single-output isolated bidirectional forward DC chopperInput filter Li1-Ci1、Li2-Ci2、…、Lin-CinOr Ci1、Ci2、…、CinThen inputting a direct current power supply U in n pathsi1、Ui2、…、UinTo obtain a smooth input direct current Ii1、Ii2、…、Iin. Setting the turns of primary winding of high-frequency transformer as N111＝N211＝N11、N121＝N221＝N21、…、N1n1＝N2n1＝Nn1Number of turns of secondary winding N12＝N22＝N2Bipolar tri-state multi-level SPWM voltage wave u during energy forward transmission and reverse feedback12、u22All the amplitudes are plus or minus (U)i1N2/N11、Ui2N2/N21、…、UinN2/Nn1) Unipolar three-state multilevel SPWM voltage wave uo1、uo2Are all (U)i1N2/N11、Ui2N2/N21、…、UinN2/Nn1). It should be noted that the half-bridge dc chopper circuit has a multilevel voltage uN111、uN121、…、uN1n1、uN211、uN221、…、uN2n1、u12、u22、uo1、uo2Should be 1/2 of the voltage amplitude indicated in fig. 6.
The multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter belongs to a step-down inverter, n input sources supply power to a load in a time-sharing mode, and the principle of the inverter is equivalent to the superposition of voltages of a plurality of voltage type single-input inverters at the output end. Setting power selection switch S111(S111′、S112、S112′、S211、S211′、S212、S212′)、S121(S121′、S122、S122′、S221、S221′、S222、S222′)、…、S1n1(S1n1′、S1n2、S1n2′、S2n1、S2n1′、S2n2、S2n2') has a duty cycle of d1、d2、…、dnThen the voltage u is outputoAnd input direct current voltage (U)i1、Ui2、…、Uin) Turn ratio of high frequency transformer (N)2/N11、N2/N21、…、N2/Nn1) Duty ratio (d)1、d2、…、dn) The relationship between is uo＝d1Ui1N2/N11+d2Ui2N2/N21+…+dnUinN2/Nn1(single, double, half bridge) or uo＝2(d1Ui1N2/N11+d2Ui2N2/N21+…+dnUinN2/Nn1) (push-pull, push-pull forward, full bridge circuits). For a suitable duty cycle (d)1、d2、…、dn) And high frequency transformer turn ratio (N)2/N11、N2/N21、…、N2/Nn1)，uoCan be greater than, equal to or less than the sum U of the input DC voltagesi1+Ui2+…+UinThe high-frequency transformer in the inverter not only improves the safety reliability and the electromagnetic compatibility of the operation of the inverter, but also plays a role in matching the output voltage with the input voltage, namely, the output voltage of the inverter is higher than, equal to or lower than the sum U of the input direct-current voltagesi1+Ui2+…+UinThe application range of the method is greatly widened. Due to the existence of 0 < d1+d2+…+dnLess than 0.5 (single-tube type, double-tube type) or 0 less than 2 (d)1+d2+…+dn) < 1.0 (push-pull, push-pull forward, half-bridge, full-bridge), so uo＜Ui1N2/N11+Ui2N2/N21+…+UinN2/Nn1I.e. output electricityPress uoIs always lower than the input DC voltage (U)i1、Ui2、…、Uin) Turns ratio (N) of high frequency transformer2/N11、N2/N21、…、N2/Nn1) Sum of products Ui1N2/N11+Ui2N2/N21+…+UinN2/Nn1(ii) a The inverter belongs to a single-stage circuit structure, the working frequency of a transformer of the inverter is high frequency, and the combined type multi-input single-output isolation bidirectional forward direct-current chopper is provided with a multi-input single-output high-frequency transformer, so the inverter is called a multi-winding time-sharing power supply forward direct-current chopping type (voltage reduction type) single-stage multi-input high-frequency chain inverter. The n input sources of the inverter supply power to the output alternating current load in a time-sharing manner, and the duty ratios can be the same (d)1＝d2＝…＝dn) Or may be different (d)1≠d2≠…≠dn)。
The multi-winding time-sharing power supply forward DC chopper type single-stage multi-input high-frequency chain inverter disclosed by the invention shares a combined multi-input single-output isolation bidirectional forward DC chopper and an output filter circuit, and is essentially different from the circuit structure of the traditional multi-input inverter formed by two-stage cascading of a DC converter and an inverter. Therefore, the inverter has novelty and creativity, has the characteristics of high-frequency electrical isolation between output and input, time-sharing power supply of a multi-input power supply, simple circuit topology, single-stage power conversion, large voltage-boosting and voltage-reducing ratio, flexible input voltage preparation, high conversion efficiency (meaning small energy loss), high output voltage waveform quality, high output capacity, low cost, wide application prospect and the like, is an ideal energy-saving and consumption-reducing single-stage multi-input inverter, and has important value in the modern times of vigorously advocating the construction of energy-saving and conservation-oriented society.
Embodiments of a family of multi-winding time-shared supply forward dc chopper type single-stage multiple-input high-frequency chain inverter circuit topologies are shown in fig. 7-16. In the circuits shown in fig. 7-16, each high-frequency inverter circuit comprises 1-2 four-quadrant high-frequency power switches capable of bearing bidirectional voltage stress and bidirectional current stressAnd 1-2 two-quadrant high-frequency power switches capable of bearing unidirectional voltage stress and bidirectional current stress or only 1-2 four-quadrant high-frequency power switches capable of bearing bidirectional voltage stress and bidirectional current stress, and the high-frequency rectifier for rectification, follow current and polarity selection is realized by a plurality of two-quadrant high-frequency power switches capable of bearing unidirectional voltage stress and bidirectional current stress; two multi-input single-output isolation bidirectional forward direct current choppers in the combined multi-input single-output isolation bidirectional forward direct current choppers work for half a low-frequency output period in turn; each multi-input single-output isolated bidirectional forward DC chopper output is connected in parallel with an active clamp circuit for suppressing the voltage spike of the high frequency rectifier power switch, the active clamp circuit is composed of a clamp switch Sc1And a clamp capacitor Cc1Or a clamping switch Sc2And a clamp capacitor Cc2Are connected in series; r in FIG. 711、C11、D11、R12、C12、D12、…、R1n、C1n、D1nAnd R21、C21、D21、R22、C22、D22、…、R2n、C2n、D2nClamping circuits, R, forming two multi-input single-output single-tube forward DC choppers, respectively1n、C1n、D1nAnd R2n、C2n、D2nFor implementing high-frequency transformers T1、T2Magnetic reset and suppression high frequency power switch S1n1、S2n1The remaining clamp circuits are only used to suppress the high frequency power switch S111、S121、…、S1(n-1)1、S211、S221、…、S2(n-1)1The turn-off voltage spike of (2) can also adopt magnetic reset technologies such as a reset winding, LCD clamping, active clamping and the like. Specifically, the single-tube forward DC chopper type circuit shown in FIG. 7 is implemented by 2n four-quadrant high-frequency power switches capable of withstanding bidirectional voltage stress and bidirectional current stress and 4 two-quadrant high-frequency power switches capable of withstanding unidirectional voltage stress and bidirectional current stress, and the single-tube forward DC chopper type circuit shown in FIGS. 8, 10, and 13 includes push-pull full-wave, push-pull forward full-wave, and two-way current stress,The half-bridge full-wave DC chopper type circuit is realized by 4n four-quadrant high-frequency power switches capable of bearing bidirectional voltage stress and bidirectional current stress and 4 two-quadrant high-frequency power switches capable of bearing unidirectional voltage stress and bidirectional current stress, the bridge type push-pull forward bridge type and half-bridge type DC chopper type circuits shown in figures 9, 11 and 14 are realized by 4n four-quadrant high-frequency power switches capable of bearing bidirectional voltage stress and bidirectional current stress and 8 two-quadrant high-frequency power switches capable of bearing unidirectional voltage stress and bidirectional current stress, the double-tube forward DC chopper type circuit shown in figure 12 is realized by 2n four-quadrant high-frequency power switches capable of bearing bidirectional voltage stress and bidirectional current stress and 2(n +2) two-quadrant high-frequency power switches capable of bearing unidirectional voltage stress and bidirectional current stress, and the circuits are respectively shown in figures 15, The full-bridge full-wave and full-bridge direct-current chopper type circuit shown by 16 is realized by 4n four-quadrant high-frequency power switches capable of bearing bidirectional voltage stress and bidirectional current stress and 4(n +1) and 4(n +2) two-quadrant high-frequency power switches capable of bearing unidirectional voltage stress and bidirectional current stress respectively. 7-16 are for the case of LC input filters, the circuits are for the case of capacitive input filters, not shown for space; the circuits shown in fig. 7-16 only show the output LC filter circuit for passive ac loads and not the output LCL filter circuit for ac grid loads. The power switch voltage stress of the multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter topology embodiment is shown in table 1. In Table 1, UN11max＝max(Ui1,Ui2N111/N121,…,UinN111/N1n1),UN12max＝max(Ui1N121/N111,Ui2,…,UinN121/N1n1),…,UN1nmax＝max(Ui1N1n1/N111,Ui2N1n1/N121,…,Uin)；UN2max＝max(Ui1N12/N111,Ui2N12/N121,…,UinN12/N1n1). Single-tube type, push-pull forward type forward direct currentThe chopper type circuit is respectively suitable for medium-power and high-power low-voltage input inversion occasions, and the double-pipe type, half-bridge type and full-bridge type forward direct current chopper type circuits are respectively suitable for medium-power and high-power high-voltage input inversion occasions. The circuit topology family is suitable for converting a plurality of mutually isolated and unstable input direct-current voltages into output alternating-current power with required voltage and stable and high quality, and can be used for realizing a novel single-stage multiple new energy distributed power supply system with excellent performance and wide application prospect, such as photovoltaic cells 40-60VDC/220V50HzAC or115V400HzAC, proton exchange membrane fuel cells 85-120V/220V50HzAC or115V400HzAC, medium and small sized users 24-36-48VDC/220V50HzAC or115V400HzAC, large wind power generation 510VDC/220V50HzAC or115V400HzAC, and the like, to supply power to alternating-current loads or alternating-current power grids.
The energy management control strategy is crucial to various new energy combined power supply systems. Due to the presence of multiple input sources and corresponding power switching units, multiple duty cycles need to be controlled, i.e. there are multiple degrees of freedom of control, which provides the possibility for energy management of multiple new energy sources. An energy management control strategy of the multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter needs to have three functions of energy management of an input source, MPPT (maximum power point tracking) and output voltage (current) control of new energy power generation equipment such as a photovoltaic cell and a wind driven generator, and sometimes, the charging and discharging control of a storage battery and smooth and seamless switching of a system under different power supply modes need to be considered. The multi-winding time-sharing power supply forward DC chopper type single-stage multi-input high-frequency chain inverter adopts two different energy management modes: (1) energy management mode I-master-slave power distribution mode, the power required by the load is known to be output by the 1 st, 2 nd, … th and n-1 st paths of the master power supply equipment as much as possible
TABLE 1 Power switch Voltage stress for Multi-winding time-sharing Power supply Forward DC chopper type Single-stage Multi-input high-frequency chain inverter topology embodiment
Figure BDA0001542999190000091
The input source supply is that the input current of the 1 st, 2 nd, … th and n-1 st input sources is given, which is equivalent to the input power of the 1 st, 2 nd, … th and n-1 st input sources, and the insufficient power needed by the load is provided by the nth input source of the power supply device, so that the storage battery energy storage device is not needed to be added; (2) in the energy management mode II, namely the maximum power output mode, the 1 st input source, the 2 nd input source, the … th input source and the n th input source are all output to a load with the maximum power, storage battery energy storage equipment is omitted, the requirement of a grid-connected power generation system on the full utilization of energy is met, and if an output end is connected with a storage battery charging and discharging device in parallel, the stability of the output voltage (current) of an independent power supply system can be realized. When the input voltage of the n paths of new energy sources is given, the input current of the 1 st, 2 nd, … th and n paths of input sources is controlled, so that the input power of the 1 st, 2 nd, … th and n paths of input sources is controlled.
The multi-winding time-sharing power supply forward DC chopper type single-stage multi-input high-frequency chain inverter adopts an SPWM (sinusoidal pulse width modulation) master-slave power distribution energy management control strategy to form an independent power supply system; or an input current instantaneous value SPWM maximum power output energy management control strategy is adopted to form a grid-connected power generation system. The output voltage and input current instantaneous value SPWM master-slave power distribution energy management control block diagram and the control principle waveform of the output power fixed by the 1 st input source, 2 nd input source, … n-1 st input source and the insufficient power required by the n th input source to supplement the load are respectively shown in the figures 17, 18, 19 and 20. Fig. 17 and 18 are control schemes of multi-winding time-sharing power supply single-tube type and double-tube type forward direct current chopper type circuit topologies, and fig. 19 and 20 are control schemes of multi-winding time-sharing power supply push-pull type, push-pull forward type, half-bridge type and full-bridge type forward direct current chopper type circuit topologies, which are very similar in nature. The basic idea of the control scheme is that n high-frequency inverter circuits in each multi-input single-output isolation bidirectional forward direct-current chopper input n direct-current voltage sources Ui1、Ui2、…、UinModulated into bipolar two-state multi-level high-frequency voltage square wave or bipolar three-state multi-level SPWM voltage wave, the conduction time of the 1 st, 2 nd, … th and n-1 st high-frequency inverter circuit power switch is obtained by cross-capturing the sawtooth wave and the product of the error current and the reference sine synchronous signal(realizing the maximum power output of the 1 st, 2 nd, … th and n-1 st input sources), the conduction time of the nth high-frequency inverter circuit power switch is obtained by intersecting the sawtooth wave according to the error voltage (realizing the complement of the nth input source power), and the conduction time T of the n nth high-frequency inverter circuit power switchon1、Ton2、…、TonnThe sum of which is the total on-time TonHigh frequency transformer T1、T2Isolation and high-frequency rectifier rectified into unipolar tri-state multi-level SPWM voltage wave uo1、uo2Filtering to obtain high-quality sinusoidal AC voltage uoOr sinusoidal alternating current io(ii) a The control strategy is applicable to the circuits shown in fig. 7-16 by adjusting the output voltage error signal to achieve stabilization of the inverter output voltage. The 1 st, 2 nd, … th and n-1 th input sources are calculated by the maximum power point to obtain a reference current signal I＊ i1r、I＊ i2r、…、I＊ i(n-1)rInput current feedback signal I of inverter circuit 1, 2, … and n-1i1f、Ii2f、…、Ii(n-1)fReference current signal I with No. 1, No. 2, No. … and No. n-1i1r、Ii2r、…、Ii(n-1)rThe error signal I is amplified by comparison of a proportional-integral regulator1e、I2e、…、I(n-1)eRespectively multiplied by the reference sine synchronous signals to obtain i1e、i2e、…、i(n-1)eAnd an inverted signal-i1e、-i2e、…、-i(n-1)eOutput voltage feedback signal u of inverterofWith reference sinusoidal voltage urObtaining a voltage error amplification signal u through comparison and amplification of a proportional-integral regulatore，i1e、i2e、…、i(n-1)e、ue、-i1e、-i2e、…、-i(n-1)e、-ueAre respectively matched with the unipolar sawtooth-shaped carrier wave ucIn comparison, after appropriate combinational logic circuit, the power switch control signal u of the single-tube type and double-tube type circuit topologies shown in fig. 7 and 12 is obtainedgs111(ugs′111)、ugs121(ugs′121)、…、ugs1n1(ugs′1n1)、ugs211(ugs′211)、ugs221(ugs′221)、…、ugs2n1(ugs′2n1)、ugs13、ugs23、ugs15、ugs25、ugsc1、ugsc2Or the power switch control signal u of the push-pull, push-pull forward, half-bridge, full-bridge circuit topology shown in fig. 8, 9, 10, 11, 13, 14, 15, 16gs111(ugs′111)、ugs121(ugs′121)、…、ugs1n1(ugs′1n1)、ugs112(ugs′112)、ugs122(ugs′122)、…、ugs1n2(ugs′1n2)、ugs13(ugs′13)、ugs14(ugs′14)、ugs211(ugs′211)、ugs221(ugs′221)、…、ugs2n1(ugs′2n1)、ugs212(ugs′212)、ugs222(ugs′222)、…、ugs2n2(ugs′2n2)、ugs23(ugs′23)、ugs24(ugs′24)、ugsc1、ugsc2. When the load power PoWhen the output voltage is larger than the sum of the maximum powers of the 1 st, 2 nd, … th and n-1 th input sourcesoReducing, the voltage regulator output voltage ueIs greater than the threshold comparison level UtAnd I1e、I2e、…、I(n-1)eAre all greater than zero, diode D1、D2、…、Dn-1Blocking, the 1 st, 2 nd, … th, n-1 th current regulators and the nth voltage regulator work independently, i.e. Ii1r＝I＊ i1r、Ii2r＝I＊ i2r、…、Ii(n-1)r＝I＊ i(n-1)rThe 1 st, 2 nd, … th and n-1 th circuit current regulators are used for realizing the maximum power output of the 1 st, 2 nd, … th and n-1 th input sources, the nth circuit voltage regulator is used for realizing the stability of the output voltage of the inverter, and the n-th input sources supply power to the load in a time-sharing manner; when the load power PoLess than the maximum work of the 1 st, 2 nd, … th and n-1 th input sourcesWhen the sum of the rates is obtained, the voltage u is outputoIncrease when the voltage regulator output voltage ueIs reduced to a threshold comparison level UtWhen following, diode Dn-1On, D1、D2、…、Dn-2When the input voltage is still blocked, the hysteresis comparison circuit n +1 outputs low level, the nth input source stops supplying power, the voltage regulator and the current regulator form a double closed-loop control system, the 1 st, 2 nd, … th and n-1 th input sources supply power to a load in a time-sharing manner in a switching period, and the current regulator supplies reference current Ii(n-1)rDecrease, i.e. Ii(n-1)r＜I＊ i(n-1)rThe output power of the (n-1) th input source is reduced (working at a non-maximum working point), the output power of the (n) th input source is reduced to zero, and the output voltage u of the inverter is reducedoAnd tends to be stable. By regulating the reference voltage u as the input voltage or load variesrOr the feedback voltage uofTo change the error voltage signal ueAnd an error current signal i1e、i2e、…、i(n-1)eThereby changing the duty ratio d of the n-path parallel time-sharing selection switch1、d2、…、dnTherefore, the regulation and stabilization of the output voltage and the input current (output power) of the inverter can be realized.
When the nth input source in fig. 17-20 is designed as input current feedback to control the input current, an input current instantaneous value SPWM maximum power output energy management control strategy is constructed. The 1 st, 2 nd, … th and n-way current regulators respectively work independently and are all used for realizing the maximum power output of respective input sources, and the n-way input sources supply power to a load in a time-sharing manner.
The control principle waveforms shown in fig. 18 and 20 mark the high frequency switching period TSA certain high frequency switching period TSConduction time T of internal 1 st, 2 nd, … th input sourceon1、Ton2、…、TonnAnd total on-time Ton＝Ton1+Ton2+…+TonnTotal on-time TonThe variation in the output voltage period is sinusoidal.
To form an independent power supply system capable of fully utilizing energy of multiple input sourcesThe multiple input sources should operate in the maximum power output mode and energy storage devices should be configured to achieve the stabilization of the output voltage, that is, a single-stage isolation bidirectional charging and discharging converter is connected in parallel to the output end of the inverter, as shown in fig. 21. The single-stage isolation bidirectional charge-discharge converter consists of an input filter (L)i、CiOr Ci) High-frequency inverter, high-frequency transformer, cycle converter, output filter (L)f′、Cf') is cascaded in sequence, and the cycle converter is composed of four-quadrant high-frequency power switches capable of bearing bidirectional voltage stress and bidirectional current stress. The single-stage isolation bidirectional charge-discharge converter is respectively equivalent to a single-stage high-frequency link DC-AC converter and a single-stage high-frequency link AC-DC converter when energy is transmitted in the forward direction (energy storage equipment is discharged) and transmitted in the reverse direction (energy storage equipment is charged).
The independent power supply system adopts a maximum power output energy management control strategy with a single-stage isolated bidirectional charge-discharge converter output voltage independent control loop, as shown in fig. 22. When the load power Po＝UoIoGreater than the sum P of the maximum powers of the plurality of input sources1max+P2max+…+PnmaxWhen the power supply is started, energy storage equipment such as a storage battery, a super capacitor and the like provides needed insufficient power to a load through a single-stage isolation bidirectional charge-discharge converter, namely a power supply mode II, and the energy storage equipment independently provides power to the load, namely a power supply mode III, and belongs to the extreme situation of the power supply mode II; when the load power Po＝UoIoLess than the sum P of the maximum powers of the plurality of input sources1max+P2max+…+PnmaxAnd in the time, the residual energy output by the plurality of input sources is used for charging the energy storage equipment through the single-stage isolation bidirectional charging and discharging converter, namely, the power supply mode I. Using the band elimination load as an example, the power flow direction control of the single-stage isolation bidirectional charge-discharge converter is discussed, as shown in fig. 23. For output filter capacitor Cf、Cf' and load ZLIn other words, the parallel connection of the output ends of the multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter and the single-stage isolation bidirectional charge-discharge converter is equivalent to the parallel connection superposition of two current sources. Energy tube shown by figure 22According to the physical control strategy, the output filter inductive current i of the multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverterLfAnd the output voltage uoThe same frequency and the same phase are adopted, and active power is output; the charging and discharging converter outputs a voltage uoAnd a reference voltage uorefError amplified signal uoeControlled by SPWM signal generated by intercepting the high-frequency carrier wave, which outputs a filtered inductor current iLf' and uoThere is a phase difference theta between them, and different phase differences theta mean that active power with different magnitude and direction is output. When P is presento＝P1max+P2max+…+PnmaxWhen theta is equal to 90 degrees, the active power output by the charge-discharge converter is zero, and the charge-discharge converter is in an idle state; when P is presento>P1max+P2max+…+PnmaxWhen u is turned onoThe theta is reduced to be less than 90 degrees, the charging and discharging converter outputs active power, and the energy storage equipment discharges to the load, namely the energy storage equipment provides insufficient power required by the load; when P is presento＜P1max+P2max+…+PnmaxWhen u is turned onoAnd increasing theta to be more than 90 degrees, outputting negative active power by the charging and discharging converter, feeding energy back to the energy storage device by the load, namely charging the energy storage device by residual power output by the plurality of input sources, and feeding the energy back to the energy storage device by the load to be the maximum when the theta is 180 degrees. Thus, the energy management control strategy can be based on PoAnd P1max+P2max+…+PnmaxThe relative size of the single-stage isolation bidirectional charge-discharge converter controls the power flow size and direction of the single-stage isolation bidirectional charge-discharge converter in real time, and smooth and seamless switching of the system under three different power supply modes is realized.

Claims (2)

1. A multi-winding time-sharing power supply forward DC chopper type single-stage multi-input high-frequency chain inverter is characterized in that: the inverter is formed by sequentially cascading n mutually isolated input direct current filters, a combined n-input single-output isolated bidirectional forward direct current chopper and an output alternating current LC or LCL filter, wherein each input end of the combined n-input single-output isolated bidirectional forward direct current chopper is correspondingly connected with the output end of each input direct current filter, n is nThe number of paths of the multiple input sources, n is a natural number greater than 1; the combined n-input single-output isolation bidirectional forward direct current chopper is formed by connecting each input end of two same n-input single-output isolation bidirectional forward direct current choppers which respectively output low-frequency positive half-cycle and low-frequency negative half-cycle unipolar sine pulse width modulation voltage waves in parallel and connecting output ends in a reverse series mode, and two output ends of two non-reverse series of the two n-input single-output isolation bidirectional forward direct current choppers are output ends of the combined n-input single-output isolation bidirectional forward direct current chopper; each n-input single-output isolation bidirectional forward direct current chopper is formed by sequentially cascading n mutually isolated bidirectional power flow single-input single-output high-frequency inverter circuits, an n-input single-output high-frequency transformer, a bidirectional power flow high-frequency rectifier and an active clamping circuit, wherein the active clamping circuit is formed by serially connecting a clamping switch and a clamping capacitor, the output end of each bidirectional power flow single-input single-output high-frequency inverter circuit is correspondingly connected with each input end of the n-input single-output high-frequency transformer one by one, and the input end of each bidirectional power flow single-input single-output high-frequency inverter circuit is each input end of the combined n-input single-output isolation bidirectional forward direct current chopper; the single-tube circuit is composed of a four-quadrant high-frequency power switch bearing bidirectional voltage stress bidirectional current stress, two drains of the single-tube circuit are respectively connected with a non-negative end of a primary winding of the high-frequency transformer and a negative end of an input direct current source of the high-frequency transformer, the' negative end of the primary winding of the high-frequency transformer is connected with an output positive end of an input direct current filter of the high-frequency transformer, the push-pull circuit is composed of two four-quadrant high-frequency power switches bearing bidirectional voltage stress bidirectional current stress, one drains of the two four-quadrant high-frequency power switches are respectively connected with the negative end of the input direct current source of the high-frequency transformer, and the other drains of the two four-quadrant high-frequency power switches are respectively connected with two different ends of the primary winding of the high-frequency transformer, The center tap of the primary winding of the high-frequency transformer is connected with the output positive polarity end of the input DC filter, and the push-pull positiveThe excitation circuit consists of two four-quadrant high-frequency power switches bearing bidirectional voltage stress and bidirectional current stress and a clamping capacitor, two drains of one four-quadrant high-frequency power switch are respectively connected with the non-end of the first primary winding and the non-end of the second primary winding of the high-frequency transformer, the non-end of the first primary winding is connected with the output positive-polarity end of the input direct-current filter, two drains of the other four-quadrant high-frequency power switch are respectively connected with the non-end of the first primary winding and the non-end of the second primary winding of the high-frequency transformer, the non-end of the second primary winding is connected with the negative-polarity end of the input direct-current source of the high-frequency transformer, two ends of the clamping capacitor are respectively connected with the non-ends of the two primary windings of the high-frequency transformer, and the double-tube circuit consists of the four-quadrant high-frequency power switch bearing bidirectional voltage stress and bidirectional current stress of the upper left bridge arm and the power diode of the right bridge arm The half-bridge circuit is composed of two capacitors of a left bridge arm and two four-quadrant high-frequency power switches of a right bridge arm bearing bidirectional voltage stress and bidirectional current stress, and two drains of the two capacitors of the left bridge arm and the two four-quadrant high-frequency power switches of the two right bridge arm bearing bidirectional voltage stress and bidirectional current stress are respectively connected with the capacitor of the left upper bridge arm The positive end is connected with one drain electrode of the right lower bridge arm switch, the other drain electrode of the right lower bridge arm switch and the negative end of the left lower bridge arm capacitor are connected with the negative end of the input direct current source, the positive end of the left upper bridge arm capacitor is connected with the positive output end of the input direct current filter, and two ends of the primary winding of the high-frequency transformer are respectively connected with the positive output end of the input direct current filterThe full-bridge circuit is connected with the middle point of the left bridge arm capacitor and the middle point of the right bridge arm switch, the full-bridge circuit is composed of two four-quadrant high-frequency power switches bearing bidirectional voltage stress and bidirectional current stress of an upper bridge arm and two-quadrant high-frequency power switches bearing unidirectional voltage stress and bidirectional current stress of a lower bridge arm, one drain electrode of each of the two upper bridge arm switches is connected with the positive output end of the input direct current filter, the source electrodes of the two lower bridge arm switches are connected with the negative input end of the input direct current source, the other drain electrode of the upper left bridge arm switch and the drain electrode of the lower left bridge arm switch are connected with one end of the primary winding of the high-frequency transformer, the drain electrode of the upper right bridge arm switch and the drain electrode of the lower right bridge arm switch are connected with, the four-quadrant high-frequency power switch is formed by connecting two-quadrant high-frequency power switches with two source electrodes connected together in a reverse series manner; the bidirectional power flow high-frequency rectifier is a half-wave type, full-wave type or full-bridge type circuit, and is composed of a two-quadrant high-frequency power switch for rectifying and bearing unidirectional voltage stress and bidirectional current stress and a two-quadrant high-frequency power switch for selecting the follow current polarity for bearing unidirectional voltage stress and bidirectional current stress, the sources of the two-quadrant high-frequency power switches are respectively connected with the ends- ' and ' not- ' of the secondary winding of the high-frequency transformer, the drains of the two-quadrant high-frequency power switches are connected, the full-wave type bidirectional power flow high-frequency rectifier is composed of two-quadrant high-frequency power switches for selecting the rectifying follow current polarity for bearing unidirectional voltage stress and bidirectional current stress, the sources of the two-quadrant high-frequency power switches are respectively connected with the two ends of the secondary winding of the high-frequency transformer, the drains of the two-quadrant high-frequency power switches are connected, and the center tap of the secondary winding of the high-frequency transformer The full-bridge bidirectional power flow high-frequency rectifier is composed of left and right bridge arms or upper and lower bridge arms, two-quadrant high-frequency power switches for selecting the polarity of rectifying follow current bearing unidirectional voltage stress and bidirectional current stress, the source electrode of the upper left bridge arm switch and the drain electrode of the lower left bridge arm switch are connected with one end of the secondary winding of the high-frequency transformer, and the source electrode of the upper right bridge arm switch and the drain electrode of the lower right bridge arm switch are connected with the output end of the DC chopperThe pole of the DC chopper is connected with the other end of the secondary winding of the high-frequency transformer, and the drain connection point of the two switches of the upper bridge arm and the source connection point of the two switches of the lower bridge arm are the output end of the DC chopper; the n-path single-input single-output high-frequency inverter circuit of each n-input single-output isolation bidirectional forward direct current chopper in the multi-input inverter respectively inputs a direct current voltage source Ui1、Ui2、…、UinThe amplitude of the modulated bipolar two-state multi-level high-frequency voltage square wave or the bipolar three-state multi-level amplitude is +/-Ui1N2/N11、±Ui2N2/N21、…、±UinN2/Nn1The SPWM voltage wave is rectified into a single-polarity three-state multi-level amplitude value of U respectively by a high-frequency transformer for isolation and transformation and a high-frequency rectifieri1N2/N11、Ui2N2/N21、…、UinN2/Nn1After output filtering, the SPWM voltage wave obtains high-quality sinusoidal alternating current voltage or sinusoidal grid-connected current on a single-phase alternating current load, and only the multilevel voltage amplitude of a half-bridge circuit is multiplied by 1/2, N1、N2The number of turns of a primary winding and the number of turns of a secondary winding of the high-frequency transformer are respectively; the independent power supply system formed by the multiple-input inverter adopts a master-slave power distribution energy management control strategy of SPWM (sinusoidal pulse Width modulation) by fixing output power of input sources of 1 st, 2 nd, … th and n-1 st paths and feeding back instantaneous values of output voltage and input current of insufficient power required by a supplementary load of an input source of an n th path, and the grid-connected power generation system formed by the multiple-input inverter adopts a maximum power output energy management control strategy of SPWM by feeding back instantaneous values of input currents of the input sources of 1 st, 2 nd, … th and n paths; the inverter determines the number of input source circuits needing to be put into operation by controlling the on-off of n paths of bidirectional power flow single-input single-output high-frequency inverter circuits in each n-input single-output isolation bidirectional forward direct-current chopper according to the positive and negative half cycles of the output voltage and the size of an alternating-current load, wherein the n paths of input sources are U-shaped in one high-frequency switching periodi1、Ui2、…、UinThe power is supplied to the AC load in a time-sharing manner in parallel in sequence, so that n input DC voltages which are mutually isolated and unstable are single-stage high-frequencyThe isolated high-efficiency inverter is converted into stable high-quality sine alternating current required by an alternating current load.
2. The multi-winding time-sharing power supply forward direct current chopping type single-stage multi-input high-frequency chain inverter according to claim 1, characterized in that: the output end of the multi-winding time-sharing power supply forward DC chopper type single-stage multi-input high-frequency chain inverter is connected with a single-stage isolation bidirectional charge and discharge converter of the energy storage device in parallel, so that an independent power supply system which can fully utilize the energy of the n input sources and has stable output voltage is formed; the single-stage isolation bidirectional charge-discharge converter is formed by sequentially cascading an input direct current filter, a high-frequency inverter, a high-frequency transformer, a cycle converter and an output alternating current filter, wherein the cycle converter is formed by a four-quadrant high-frequency power switch capable of bearing bidirectional voltage stress and bidirectional current stress, and the single-stage isolation bidirectional charge-discharge converter is respectively equivalent to a single-stage high-frequency link DC-AC converter and a single-stage high-frequency link AC-DC converter when the energy storage equipment is discharged and charged; the independent power supply system adopts a management control strategy of the maximum power output energy of n input sources with a single-stage isolation bidirectional charge-discharge converter output voltage independent control loop, the n input sources all work in a maximum power output mode, the power flow size and direction of the single-stage isolation bidirectional charge-discharge converter are controlled in real time according to the relative size of the sum of the load power and the maximum power of the n input sources, and the smooth seamless switching of the output voltage of the system and the charge and discharge of energy storage equipment is realized; when the load power is greater than the sum of the maximum powers of the n input sources, the system works in a power supply mode II in which the energy storage device provides required insufficient power to the load through the single-stage isolation bidirectional charge-discharge converter, a power supply mode III in which the energy storage device supplies power to the load independently belongs to the extreme situation of the power supply mode II, and when the load power is less than the sum of the maximum powers of the n input sources, the system works in a power supply mode I in which the residual energy output by the n input sources charges the energy storage device through the single-stage isolation bidirectional charge-discharge converter; for the output alternating current filter capacitor and the alternating current load, the parallel connection of the output ends of the multi-winding time-sharing power supply forward direct current chopper type single-stage multi-input high-frequency chain inverter and the single-stage isolation bidirectional charge-discharge converter is equivalent to the parallel connection superposition of two alternating current sources; the method comprises the steps that 1, 2, … and n paths of input source output currents are subjected to error amplification with 1, 2, … and n paths of input source maximum power point reference currents respectively, 1, 2, … and n paths of error amplification signals are multiplied by sinusoidal synchronous signals and then are intersected with the same high-frequency carrier signal respectively to generate 1, 2, … and n paths of signal control n input inverters, the n input inverters output alternating current filter inductive currents which are in the same frequency and the same phase as output voltages and output active power, and the difference theta between the output alternating current filter inductive currents of a charge-discharge converter controlled by the error amplification signals of the system output voltages and the reference voltages and the high-frequency carrier signals is intersected with the high-frequency carrier signals to generate SPWM signals, wherein the difference theta between the output alternating current filter inductive currents and the system output voltages is different in size and direction, and the difference theta means that; when the alternating current load power is equal to the sum of the maximum powers of the n input sources, theta is equal to 90 degrees, the active power output by the charging and discharging converter is zero, when the alternating current load power is larger than the sum of the maximum powers of the n input sources, the output voltage is reduced, theta is smaller than 90 degrees, the charging and discharging converter outputs the active power, namely the insufficient power required by the alternating current load is provided by the energy storage device, when the alternating current load power is smaller than the sum of the maximum powers of the n input sources, the output voltage is increased, theta is larger than 90 degrees, and the charging and discharging converter outputs the negative active power, namely the residual power output by the.
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