CN108153150A - Dual-level matrix frequency converter Model Predictive Control strategy based on space vector modulation - Google Patents
Dual-level matrix frequency converter Model Predictive Control strategy based on space vector modulation Download PDFInfo
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- CN108153150A CN108153150A CN201711161913.1A CN201711161913A CN108153150A CN 108153150 A CN108153150 A CN 108153150A CN 201711161913 A CN201711161913 A CN 201711161913A CN 108153150 A CN108153150 A CN 108153150A
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- G05B—CONTROL OR REGULATING SYSTEMS IN GENERAL; FUNCTIONAL ELEMENTS OF SUCH SYSTEMS; MONITORING OR TESTING ARRANGEMENTS FOR SUCH SYSTEMS OR ELEMENTS
- G05B13/00—Adaptive control systems, i.e. systems automatically adjusting themselves to have a performance which is optimum according to some preassigned criterion
- G05B13/02—Adaptive control systems, i.e. systems automatically adjusting themselves to have a performance which is optimum according to some preassigned criterion electric
- G05B13/04—Adaptive control systems, i.e. systems automatically adjusting themselves to have a performance which is optimum according to some preassigned criterion electric involving the use of models or simulators
- G05B13/042—Adaptive control systems, i.e. systems automatically adjusting themselves to have a performance which is optimum according to some preassigned criterion electric involving the use of models or simulators in which a parameter or coefficient is automatically adjusted to optimise the performance
Abstract
The present invention relates to a kind of dual-level matrix frequency converter Model Predictive Control strategies based on space vector modulation, for the selection of rectification stage effect vector, propose the thought directly to sort to the corresponding cost function of each effective vector, select effect vector of the effective vector corresponding to minimum two cost functions as subsequent time rectification stage, and it is asked for according to cost function and acts on duty ratio, for inverse cascade, desired output voltage will be converted into reference to output current by proposing, according to desired output voltage vector in two-phase stationary coordinate system position distribution, select two effective one zero vectors of vector sum, each vector duty cycle is acquired according to the output phase parallactic angle.This invention simplifies the selection processes of rectification stage effect vector, the traversal optimizing asked for on off state of cost function is not present in inverse cascade, greatly reduce the calculation amount of system, setting and system switching frequency there is no weight factor are fixed, on off state sub-distribution again to selecting realizes the zero current transition of rectification stage.
Description
Technical field
The present invention relates to the Model Predictive Controls of dual-level matrix frequency converter, and in particular to dual-level matrix frequency converter rectification
The traversal optimizing asked for on off state of cost function is not present in the optimization of grade vector selection method, inverse cascade.
Background technology
Be compared to traditional back-to-back type converter, matrix converter (MC) have power density it is high, can four-quadrant fortune
The advantages that row, input current are sinusoidal, and input power factor is adjustable, therefore it is usually used in high power density occasion, if motor drives, electricity
It can many fields such as quality improvement and wind-power electricity generation.Cause the research of lot of domestic and foreign scholar in recent years, be concentrated mainly on modulation
Strategy, stability analysis, change of current method and raising voltage transfer ratio etc..
Indirect type matrixing (Indirect Matrix Converter, IMC) is in direct-type matrix converter
It is derived on the basis of (Direct Matrix Converter, DMC).Its topological structure is divided into rectification stage and inverse cascade,
Rectification stage uses two-way switch to realize the modulation of input side waveform.Compared with DMC, IMC not only inherits all excellent of DMC
Point, and overcome the shortcomings of DMC clamp circuits are huge, commutation mode is complicated.The zero current transition of rectification stage, inversion can be achieved
Grade is there is no special commutation mode, therefore inverse cascade can realize higher switching frequency, and in addition to this, this topology does not need to
More complicated modulation strategy, this is but also IMC has better development potentiality and application prospect.
Due to the introducing of input filter so that conventional DSVPWM modulation can not realize net side unity power factor,
Complicated control method need to be used to be implemented in combination with the control targe of unity power factor and sinusoid output current with DSVPWM.Except this
Except, due to the direct-coupling of input and output, also considerably increase the complexity of modulation strategy and control algolithm.In order to improve
The response speed of system, the 1980s, Campo Peter J proposed Model Predictive Control Algorithm (Model
Predictive Control, MPC).
MPC, which is compared to traditional modulation and control method, has many advantages, such as multiple targets can be achieved at the same time
Control, and possess preferable dynamic property etc..At present, widely used MPC is defeated to obtain sinusoidal input and output electric current by IMC
Enter Reactive Power Control and reduce common-mode voltage, due to traditional MPC choose in each sampling period only choose one it is minimum
On off state corresponding to cost function is modulated due to lacking, being not fixed of switching frequency will cause input, output waveform compared with
Big ripple.In addition, when containing multiple control targes, weight factor it is determining also relatively complicated.
Invention content
It is an object of the invention to simplify the selection process of rectification stage effect vector, asking for for inverse cascade cost function is saved
With the traversal optimizing of on off state, the calculation amount of system is reduced, and eliminates the setting of weight factor, realizes the zero current of rectification stage
The change of current.
To achieve the above object, the present invention uses following technical scheme：
Dual-level matrix frequency converter of the present invention is made of rectification stage and inverse cascade, in the present invention, by rectification
The corresponding cost function sequence of each effective vector of grade, selects effective vector corresponding to minimum two cost functions as lower a period of time
The effect vector of rectification stage is carved, and it is asked for according to cost function and acts on duty ratio, for inverse cascade, it is proposed that output will be referred to
Electric current is converted into desired output voltage, according to desired output voltage vector in two-phase stationary coordinate system position distribution, selection two
One zero vector of effective vector sum, each vector duty cycle is acquired according to the output phase parallactic angle.Then on off state is redistributed, to whole
Grade and inverse cascade are flowed using SVPWM modulation techniques, it is specific as follows：
(1) three-phase current on line side and voltage are detected, detects dual-level matrix frequency converter input side three-phase voltage and stage type
Matrix converter output current predicts three-phase current on line side and three-phase output current by prediction model；
(2) vector of positive DC voltage can be generated by being selected according to constraints in six effective vectors, according to value
The definition of function asks for rectification stage and selects the corresponding cost function of effective vector, is then sorted using sort algorithm to it, selection
The vector that two corresponding effective vectors of cost function minimum are acted on as rectification stage subsequent time；
(3) according to effective vector sum its corresponding cost function chosen, the duty ratio of each vector effect is calculated,
Then the average value of virtual DC voltage is obtained；
(4) three-phase output current reference value is converted into three-phase desired output voltage, is existed according to desired output voltage vector
Two effective one zero vectors of vector sum are chosen in the distribution of two-phase co-ordinate system location；
(5) average value in one period of DC voltage that desired output voltage magnitude can be obtained in basis (4) and (3) are obtained,
And then inverse cascade modulation ratio m can be obtainedinv；
(6) according to power conservation principle, the average value in virtual one period of DC side electric current is calculated, under rectification stage one
The prediction of moment current on line side.
Compared with the prior art the present invention has clear advantage and advantageous effect, by above-mentioned technical proposal, the present invention
A kind of control method of the dual-level matrix frequency converter model prediction based on space vector modulation can reach comparable technological progress
Property and practicability, for based on the dual-level matrix frequency converter of Model Predictive Control practical market application provide it is theoretical according to
According at least with following advantages：
(1) present invention is for the selection of rectification stage effect vector, it is proposed that directly sorts, is not present to vector cost function
Asking for for combination cost function, simplifies the selection process of the effective vector of rectification stage；
(2) present invention is directed to the selection of inverse cascade on off state, it is proposed that will be converted to desired output with reference to output current
Voltage according to its position distribution under two-phase stationary coordinate system, acts on vector, according to the output phase parallactic angle by look-up table selection
Calculating acts on duty ratio, therefore the traversal optimizing of on off state is not present in inverse cascade, greatly reduces system-computed amount；
(3) since model predictive control technique and space vector modulation technique being combined, system switching frequency is consolidated
Fixed, harmonic wave distribution is more concentrated, convenient for the design of wave filter.
Description of the drawings
Fig. 1 is dual-level matrix frequency converter topology diagram
Fig. 2 is bi-directional switch structure
Fig. 3 is that program realizes flow chart
Fig. 4 is distribution map of the desired output voltage vector in α β planes
Specific embodiment
A kind of control method of the dual-level matrix frequency converter model prediction based on space vector modulation, it is characterised in that：
Based on space vector modulation, the choosing method of rectification stage on off state optimizes, inverse cascade traversal optimizing number optimization.
The invention will be further described below in conjunction with the accompanying drawings：
Dual-level matrix frequency converter topological structure is as shown in Figure 1, switch main circuit is divided into two-stage：Rectification stage and inverse cascade.
The current source type rectifier that rectification stage is made of six two-way switch, structure chart is as shown in Fig. 2, inverse cascade is traditional three
Two power level voltage source type inverter of phase.It is coupled by virtual DC side, therefore zero current transition side can be used in rectification stage
Formula reduces switching loss.
According to the characteristic of voltage source and current source, IMC must comply with 3 basic principles during the work time：
(1) cannot be short-circuit between arbitrary two-phase in the three-phase input end of IMC, it avoids that voltage source short circuit is made to cause overcurrent；
(2) the arbitrary one-phase circuit in the three-phase output end of IMC cannot be breaking, is drawn with preventing inductive load open circuit suddenly
Play overvoltage；
(3) DC voltage should be always just, to avoid power supply short circuit.
According to constraints above it is found that effective vector of rectification stage at any time only there are three, and inverse cascade is deposited
In eight effective vectors.Therefore, for traditional MPC, one co-exists in 24 kinds of effective statuses.
Fig. 3 is that the program of the dual-level matrix frequency converter Model Predictive Control based on space vector modulation realizes flow chart,
Implementation step is as follows：
(1) two effective vector sums for choosing the effect of rectification stage subsequent time calculate its duty ratio.The calculating of cost function
Shown in equation below：
G=| iref-i(k+1)|；
In formula：irefFor current reference value；I (k+1) is the predicted value of electric current k+1 sampling instants.
Cost function g according to corresponding to above formula can calculate six effective vectorsI=1 ... 6, then selected using sort algorithm
The effective vector bid corresponding to two of value function minimum.
Assuming that it is I using the vector that sort algorithm is selectedδAnd Iζ, cost function is respectively giδAnd giζ, then each arrow is defined
Amount acts on duty ratio：
(2) desired output voltage will be converted into reference to output current.
When matrix converter band resistance sense loads, the preceding discrete model that load is obtained to Euler method is utilized：
In formula：io(k+1) it is the predicted value at output current k+1 moment, io(k) it is practical output current value, uo(k) it is
Converter output voltage values.
Above formula, which is converted, to be obtained
To realize the tracking to output current, then the output current of subsequent time should be with subsequent time output current reference value
It is equal, i.e.,：io(k+1)=ioref。
Therefore the desired output voltage modulated for inverse cascade can be calculated：
(3) according to desired output voltage vector in the distribution of two-phase co-ordinate system location, two effective vector sums one of selection
Zero vector, and calculate it and act on duty ratio.
Fig. 4 is the distribution map for it is expected output voltage vector in α β planes, and inverse cascade one co-exists in six effective vectors
{V1,...,V6}.Their direction is fixed, is determined by inverse cascade on off state, but the length of six effective vectors is by rectification
Grade determines.α β planes are divided by six sectors according to the distribution of output voltage vector.
After desired output voltage vector is obtained, its phase angle under two-phase stationary coordinate system can be acquired, then under
Formula judges its residing sector：
(2N-3)π/6≤θo≤(2N-1)π/6；
θ in formulaoIt is expected output voltage vector phase angle；N is sector residing for output voltage vector.
Assuming that desired output voltage vector is located at third sector, from V1And V3Vector is nearest, therefore selects V1And V3Vector
Base vector as the synthesis of desired output voltage vector.The specific choice of vector is as shown in table 1.
1 inverse cascade of table effect vector selection table
After determining sector, the effective vector sum zero vector of inverse cascade is then selected according to sector.
(4) calculating of inverse cascade effect duty ratio, output voltage vector phase angle can be obtained according to step (3), it is also necessary to
Inverse cascade modulation ratio is obtained.
Select rectification stage effect vector IδAnd IζAfterwards, effect duty ratio is acquired, and then can acquire entire week by step (1)
Phase mean direct side voltage value：
udc=diδudcδ+diζudcζ；
U in formuladcδAnd udcζFor vector IδAnd IζIndividually act on a period corresponding DC voltage value, udcIt is average
DC voltage value.
Output voltage amplitude can acquire according to the following formula：
Therefore inverse cascade modulation ratio can be calculated is：
Desired output voltage vector is calculated, the SVPWM modulation of inverse cascade can be used for.The modulation of inverse cascade will generate
Average DC current idc, will be used in the PREDICTIVE CONTROL of rectification stage, calculating DC side the present invention is based on the conservation of energy is averaged
Electric current.Assuming that power attenuation is not present in inverse cascade, then virtual DC side power is equal to output power, therefore DC side average current
For：
In formula：IorefTo refer to output current amplitude.
Claims (5)
1. the dual-level matrix frequency converter Model Predictive Control strategy based on space vector modulation, it is characterised in that：Rectification stage pair
The corresponding cost function sequence of each effective vector, selects effective vector corresponding to minimum two cost functions as subsequent time
The effect vector of rectification stage, and it is asked for according to cost function and acts on duty ratio, for inverse cascade, it is proposed that output electricity will be referred to
Circulation turns to desired output voltage, and according to desired output voltage vector in two-phase stationary coordinate system position distribution, selection two has
One zero vector of vector sum is imitated, each vector duty cycle is acquired according to the output phase parallactic angle；Simplify the selection of rectification stage effect vector
The traversal optimizing asked for on off state of cost function is not present in process, inverse cascade, greatly reduces the calculation amount of system, no
Setting and system switching frequency there are weight factor are fixed, and the on off state sub-distribution again to selecting realizes rectification stage
Zero current transition.
2. the dual-level matrix frequency converter Model Predictive Control strategy based on space vector modulation as described in claim 1,
It is characterized in that：Two effective vector sums for choosing the effect of rectification stage subsequent time calculate its duty ratio；The calculating of cost function is such as
Shown in lower formula：
G=| iref-i(k+1)|；
In formula：irefFor current reference value；I (k+1) is the predicted value of electric current k+1 sampling instants；
Cost function g according to corresponding to above formula can calculate six effective vectorsi=1…6, then selected using sort algorithm
Effective vector corresponding to two of cost function minimum；
Assuming that it is I using the vector that sort algorithm is selectedδAnd Iζ, cost function is respectively giδAnd giζ, then define each vector and make
It is with duty ratio：
3. the dual-level matrix frequency converter Model Predictive Control strategy based on space vector modulation as described in claim 1,
It is characterized in that：Desired output voltage will be converted into reference to output current；
When matrix converter band resistance sense loads, the preceding discrete model that load is obtained to Euler method is utilized：
In formula：Io (k+1) is the predicted value at output current k+1 moment, and io (k) is practical output current value, and uo (k) is transformation
Device output voltage values；
Above formula, which is converted, to be obtained：
To realize the tracking to output current, then the output current of subsequent time should be with subsequent time output current reference value phase
Deng that is,：io(k+1)=ioref；
Therefore the desired output voltage modulated for inverse cascade can be calculated：
4. the dual-level matrix frequency converter Model Predictive Control strategy based on space vector modulation as described in claim 1,
It is characterized in that：According to desired output voltage vector in the distribution of two-phase co-ordinate system location, two effective vector sums one zero of selection
Vector, and calculate it and act on duty ratio；
After desired output voltage vector is obtained, its phase angle under two-phase stationary coordinate system can be obtained, is then judged according to the following formula
Its residing sector：
(2N-3)π/6≤θo≤(2N-1)π/6；
θ in formulaoIt is expected output voltage vector phase angle；N is sector residing for output voltage vector；
After determining sector, the effective vector sum zero vector of inverse cascade is then selected according to sector.
5. the dual-level matrix frequency converter Model Predictive Control strategy based on space vector modulation as claimed in claim 4,
It is characterized in that：The calculating of duty ratio is acted on, output voltage phase angle has been obtained, it is also necessary to inverse cascade modulation ratio be obtained；
Select rectification stage effect vector IδAnd IζAfterwards, effect duty ratio is acquired, and then can acquire whole cycle and be averaged by right 2
DC voltage value：
udc=diδudcδ+diζudcζ；
U in formuladcδAnd udcζFor vector IδAnd IζIndividually act on a period corresponding DC voltage value, udcFor mean direct
Side voltage value；
Output voltage amplitude can acquire according to the following formula：
Therefore inverse cascade modulation ratio can be calculated is：
Output voltage vector is calculated, the SVPWM modulation of inverse cascade can be used for；The modulation of inverse cascade will generate mean direct
Electric current idc, will be used in the PREDICTIVE CONTROL of rectification stage, the present invention is based on the conservation of energys to calculate DC side average current；Assuming that
Power attenuation is not present in inverse cascade, then virtual DC side power is equal to output power, therefore DC side average current is：
In formula：IorefTo refer to output current amplitude.
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Cited By (10)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109951092A (en) * | 2019-04-02 | 2019-06-28 | 燕山大学 | Six switch five-power level converters of one kind and its control method |
| CN109995047A (en) * | 2019-01-29 | 2019-07-09 | 西北工业大学 | A kind of non-equilibrium model predictive control method of triangle chain type STATCOM |
| CN111541267A (en) * | 2020-04-07 | 2020-08-14 | 南通大学 | Multi-vector model prediction control method for two-level grid-connected inverter |
| CN111585449A (en) * | 2020-06-01 | 2020-08-25 | 中国矿业大学 | Virtual vector modulation type model prediction algorithm of two-stage matrix converter |
| CN111740632A (en) * | 2020-06-29 | 2020-10-02 | 国网辽宁省电力有限公司电力科学研究院 | quasi-Z-source inverter discrete time average model prediction control device and method |
| CN112713784A (en) * | 2020-12-22 | 2021-04-27 | 华中科技大学 | Control method of back-to-back current source converter |
| CN113346767A (en) * | 2021-06-04 | 2021-09-03 | 西北工业大学 | Indirect filter resonance suppression method of two-stage matrix converter |
| CN113595405A (en) * | 2021-08-02 | 2021-11-02 | 河北工业大学 | Common-mode voltage spike problem suppression method for indirect matrix converter |
| CN113890452A (en) * | 2021-08-27 | 2022-01-04 | 中国华能集团清洁能源技术研究院有限公司 | 3x5 direct matrix converter control device, method and system based on switching frequency adjustment |
| CN114362548A (en) * | 2021-12-20 | 2022-04-15 | 中国矿业大学 | Optimal switch sequence model prediction control algorithm of two-stage matrix converter |
Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN105591549A (en) * | 2016-01-08 | 2016-05-18 | 南京航空航天大学 | Matrix converter prediction control method with active damping function |
| CN106208737A (en) * | 2016-08-24 | 2016-12-07 | 中南大学 | Model prediction current control method based on third-harmonic zero-sequence voltage matrix converter |
| CN106330034A (en) * | 2016-06-14 | 2017-01-11 | 北方工业大学 | Model predictive control method for simplified sampling of indirect matrix converter |
| CN106655937A (en) * | 2016-11-15 | 2017-05-10 | 西安理工大学 | Two-stage matrix converter-driven synchronous reluctance motor model prediction control method |
| CN106788027A (en) * | 2016-12-16 | 2017-05-31 | 华中科技大学 | A kind of model predictive control method and system based on optimal two vectorial combination |
| US20170160760A1 (en) * | 2015-12-07 | 2017-06-08 | Hamilton Sundstrand Corporation | Model predictive control optimization for power electronics |
-
2017
- 2017-11-21 CN CN201711161913.1A patent/CN108153150A/en active Pending
Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20170160760A1 (en) * | 2015-12-07 | 2017-06-08 | Hamilton Sundstrand Corporation | Model predictive control optimization for power electronics |
| CN105591549A (en) * | 2016-01-08 | 2016-05-18 | 南京航空航天大学 | Matrix converter prediction control method with active damping function |
| CN106330034A (en) * | 2016-06-14 | 2017-01-11 | 北方工业大学 | Model predictive control method for simplified sampling of indirect matrix converter |
| CN106208737A (en) * | 2016-08-24 | 2016-12-07 | 中南大学 | Model prediction current control method based on third-harmonic zero-sequence voltage matrix converter |
| CN106655937A (en) * | 2016-11-15 | 2017-05-10 | 西安理工大学 | Two-stage matrix converter-driven synchronous reluctance motor model prediction control method |
| CN106788027A (en) * | 2016-12-16 | 2017-05-31 | 华中科技大学 | A kind of model predictive control method and system based on optimal two vectorial combination |
Non-Patent Citations (3)
| Title |
|---|
| LUCA T等: "Modulated Predictive Control for Indirect Matrix Converter", 《IEEE TRANSACTIONS ON INDUSTRY APPLICATIONS》 * |
| 公铮，等: "模块化多电平换流器的快速电压模型预测控制策略", 《电力系统自动化》 * |
| 高逍男: "用矩阵变换器实现永磁同步电机模型预测控制", 《中国优秀硕士学位论文全文数据库 工程科技Ⅱ辑》 * |
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| CN111585449B (en) * | 2020-06-01 | 2022-05-27 | 中国矿业大学 | Virtual vector modulation type model prediction algorithm of two-stage matrix converter |
| CN111740632B (en) * | 2020-06-29 | 2021-08-24 | 国网辽宁省电力有限公司电力科学研究院 | quasi-Z-source inverter discrete time average model prediction control device and method |
| CN111740632A (en) * | 2020-06-29 | 2020-10-02 | 国网辽宁省电力有限公司电力科学研究院 | quasi-Z-source inverter discrete time average model prediction control device and method |
| CN112713784A (en) * | 2020-12-22 | 2021-04-27 | 华中科技大学 | Control method of back-to-back current source converter |
| CN113346767A (en) * | 2021-06-04 | 2021-09-03 | 西北工业大学 | Indirect filter resonance suppression method of two-stage matrix converter |
| CN113595405A (en) * | 2021-08-02 | 2021-11-02 | 河北工业大学 | Common-mode voltage spike problem suppression method for indirect matrix converter |
| CN113890452A (en) * | 2021-08-27 | 2022-01-04 | 中国华能集团清洁能源技术研究院有限公司 | 3x5 direct matrix converter control device, method and system based on switching frequency adjustment |
| CN114362548A (en) * | 2021-12-20 | 2022-04-15 | 中国矿业大学 | Optimal switch sequence model prediction control algorithm of two-stage matrix converter |
| CN114362548B (en) * | 2021-12-20 | 2023-10-13 | 中国矿业大学 | Optimal switching sequence model predictive control algorithm for two-stage matrix converter |
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Application publication date: 20180612 |