CN107257194B - Resonant converter - Google Patents
Resonant converter Download PDFInfo
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- CN107257194B CN107257194B CN201710703224.2A CN201710703224A CN107257194B CN 107257194 B CN107257194 B CN 107257194B CN 201710703224 A CN201710703224 A CN 201710703224A CN 107257194 B CN107257194 B CN 107257194B
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- 239000003990 capacitor Substances 0.000 claims abstract description 53
- 238000005070 sampling Methods 0.000 claims abstract description 20
- 230000005284 excitation Effects 0.000 claims description 10
- 238000010586 diagram Methods 0.000 description 12
- 238000006243 chemical reaction Methods 0.000 description 2
- 230000003247 decreasing effect Effects 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 230000000750 progressive effect Effects 0.000 description 1
Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
- H02M1/4208—Arrangements for improving power factor of AC input
- H02M1/4241—Arrangements for improving power factor of AC input using a resonant converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/12—Arrangements for reducing harmonics from ac input or output
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The application discloses resonant converter, including rectifier bridge, bus-bar capacitance, switch unit, resonant network, control unit and reposition of redundant personnel unit, wherein: the positive output terminal of the rectifier bridge is connected with one end of the bus capacitor; the input side of the switch unit is connected with a bus capacitor in parallel; the output terminal of the switch unit is connected with the positive input terminal of the resonant network; the negative input terminal of the resonant network is connected with the negative output terminal of the rectifier bridge; the shunt unit shunts the forward resonance current and provides a passage for the reverse resonance current; the control unit generates a driving control signal according to the compensation signal and a sampling signal representing the output parameter of the resonant converter, and outputs the driving control signal to the control end of a switching tube in the switching unit; the compensation signal is a signal that instructs the control unit to raise the operating frequency of the resonant converter at the zero crossing of the input voltage of the rectifier bridge and to lower the operating frequency of the resonant converter at the peaks and troughs of the input voltage of the rectifier bridge. The PF value of the resonant converter is improved.
Description
Technical Field
The invention relates to the technical field of power electronics, in particular to a resonant converter.
Background
Resonant converters have smaller switching losses than conventional PWM converters and are therefore widely used. Specific: the resonant converter takes a resonant circuit as a basic conversion unit, and when the circuit resonates, current or voltage periodically crosses zero, so that a switching device is turned on or off under the condition of zero voltage or zero current, thereby realizing soft switching and achieving the purpose of reducing switching loss.
PFC (Power Factor Correction ) technology of resonant converters is a popular subject of research in the field of power electronics. The lower the PF (Power Factor) value of the resonant converter, the higher the loss of the grid. In the prior art, in order to improve the PF value of the resonant converter, the resonant converter is often designed to have a two-stage structure, the front stage is a PFC circuit, and the rear stage is a resonant conversion circuit.
Disclosure of Invention
In view of the above, the present invention provides a resonant converter, which adopts a single-stage structure and has a high PF value, and the scheme is as follows:
the utility model provides a resonant converter, includes rectifier bridge, bus-bar capacitance, switching unit, resonant network, control unit and reposition of redundant personnel unit, wherein:
the positive output terminal of the rectifier bridge is connected with one end of the bus capacitor;
the input side of the switch unit is connected with the bus capacitor in parallel;
the output terminal of the switch unit is connected with the positive input terminal of the resonant network;
the negative input terminal of the resonant network is connected with the negative output terminal of the rectifier bridge;
the shunt unit is connected between the negative output terminal of the resonant network and the bus capacitor and is used for shunting forward resonant current and providing a passage for reverse resonant current;
the control unit receives a compensation signal and a sampling signal representing an output parameter of the resonant converter, and generates a driving control signal according to the compensation signal and the sampling signal, wherein the driving control signal is output to a control end of a switching tube in the switching unit; wherein the compensation signal is a signal that instructs the control unit to raise the operating frequency of the resonant converter at the zero crossing point of the rectifier bridge input voltage and to lower the operating frequency of the resonant converter at the peak and valley of the rectifier bridge input voltage.
The control unit comprises a frequency control module and a comparison module, and is specifically:
the comparison module receives the sampling signal and is used for comparing the sampling signal with a preset reference signal to generate a feedback signal;
the frequency control module receives the feedback signal and the compensation signal and is used for generating a driving control signal according to the feedback signal and the compensation signal.
The switching unit comprises a first switching tube and a second switching tube which are connected in series, and specifically:
the first end of the first switching tube and the second end of the second switching tube are input sides of the switching unit; the second end of the first switching tube is connected with the first end of the second switching tube, and the third ends of the first switching tube and the second switching tube are control ends of the first switching tube and the second switching tube as output terminals of the switching unit.
Wherein the resonant converter is an LLC resonant converter;
the LLC resonant converter comprises a resonant inductor, a resonant capacitor and an excitation inductor; one end of the resonant inductor is connected with the output terminal of the switch unit, and the other end of the resonant inductor is connected with one end of the excitation inductor; the other end of the excitation inductance is connected with one end of the resonance capacitor, and the other end of the resonance capacitor is connected with the negative output terminal of the rectifier bridge.
The shunt unit comprises a diode and a first capacitor, and specifically:
the cathode of the diode is connected with the negative output terminal of the rectifier bridge, and the anode of the diode is connected with the negative terminal of the bus capacitor; the first capacitor is connected in parallel with the diode.
Alternatively, the shunt unit includes a third capacitor of the diode, specifically:
the cathode of the diode is connected with the negative output terminal of the rectifier bridge, and the anode of the diode is connected with the negative terminal of the bus capacitor;
one end of the third capacitor is connected with the cathode of the diode, and the other end of the third capacitor is connected with the high-potential end of the bus capacitor.
Optionally, the shunt unit further includes a fourth capacitor, and the fourth capacitor is connected in parallel with the diode.
The output result of the frequency control module is the negative correlation between the working frequency of the resonant converter and the amplitude of the compensation signal;
correspondingly, the amplitude of the compensation signal is lowest at the zero crossing point of the input voltage of the rectifier bridge and highest at the peak value and the valley value of the input voltage of the rectifier bridge; the frequency of the compensation signal is the same as the frequency of the resonant converter input voltage.
Or the output result of the frequency control module is positive correlation between the working frequency of the resonant converter and the amplitude of the compensation signal;
correspondingly, the amplitude of the compensation signal is highest at the zero crossing point of the input voltage of the rectifier bridge and lowest at the peak value and the valley value of the input voltage of the rectifier bridge; the frequency of the compensation signal is the same as the frequency of the resonant converter input voltage.
The output result of the frequency control module is positive correlation between the working frequency of the resonant converter and the amplitude of the compensation signal; the compensation signal is taken from the cathode of the diode.
According to the technical scheme, the forward resonant current is split by introducing the splitting unit into the resonant converter and the path is provided for the backward resonant current, so that the input current of the resonant converter is changed from square waves into sine waves with certain distortion, and the distortion is reduced or even eliminated by introducing the compensating signal, so that the input current of the current resonant converter is more similar to the sine waves, and the PF value of the resonant converter is improved.
Drawings
In order to more clearly illustrate the embodiments of the invention or the technical solutions in the prior art, the drawings that are required in the embodiments or the description of the prior art will be briefly described, it being obvious that the drawings in the following description are only some embodiments of the invention, and that other drawings may be obtained according to these drawings without inventive effort for a person skilled in the art.
Fig. 1 is a schematic diagram of a resonant converter according to an embodiment of the present invention;
FIG. 2 is a schematic diagram of a shunt unit applied to the resonant converter shown in FIG. 1 according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a shunt unit applied to the resonant converter shown in FIG. 1 according to another embodiment of the present invention;
FIG. 4 is a schematic diagram of a shunt unit applied to the resonant converter shown in FIG. 1 according to another embodiment of the present invention;
FIG. 5 is a schematic diagram of a resonant converter according to the prior art;
FIG. 6 is a current waveform diagram of the resonant converter of FIG. 5;
FIG. 7 is a voltage and current waveform diagram of the resonant converter of FIG. 5;
FIG. 8 is a schematic diagram of the resonant converter of FIG. 5 after being connected to the shunt unit of FIG. 2;
FIG. 9 is a voltage waveform diagram of the resonant converter of FIG. 8;
FIG. 10 is a current waveform diagram of the resonant converter of FIG. 8;
FIG. 11 is a current waveform diagram of the resonant converter of FIG. 2;
fig. 12 is a schematic diagram of a control unit structure applied to the resonant converter shown in fig. 1 according to an embodiment of the present invention.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
Referring to fig. 1, an embodiment of the present invention discloses a resonant converter, which includes a rectifier bridge 100, a bus capacitor C2, a switch unit 200, a resonant network 300, a control unit 400, and a shunt unit 500, wherein:
the positive output terminal of the rectifier bridge 100 is connected with one end of the bus capacitor C2;
the input side of the switch unit 200 is connected with a bus capacitor C2 in parallel;
an output terminal of the switching unit 200 is connected to a positive input terminal of the resonant network 300;
the negative input terminal of the resonant network 300 is connected to the negative output terminal of the rectifier bridge 100;
the shunt unit 500 is connected between the negative output terminal of the resonant network 300 and the bus capacitor C2 for alignmentResonant current I in the direction Lr (the resonant current is a high-frequency current, and the present embodiment refers to the resonant current at a high-frequency period as I Lr Resonant current I Lr Is shown by the arrow in figure 1; resonant current I Lr Is a forward resonant current I when the actual direction is the same as the forward direction Lr Resonant current I Lr Is opposite to the positive direction, and is opposite to the resonance current I Lr ) Shunt and reverse resonant current I Lr Providing a passage;
the control unit 400 receives the compensation signal Ic and the sampling signal Is representing the output parameter of the resonant converter, and generates a driving control signal according to the compensation signal Ic and the sampling signal Is, and the driving control signal Is output to the control end of the switching tube in the switching unit 200; the compensation signal Ic is a signal that instructs the control unit 400 to increase the operating frequency of the resonant converter at the zero crossing point of the input voltage of the rectifier bridge 100 and decrease the operating frequency of the resonant converter at the peak value and the valley value of the input voltage of the rectifier bridge 100.
It should be noted that, the transformer and the secondary circuit in the resonant converter are in the prior art, and the present invention is not limited and described herein.
In the resonant converter disclosed in the embodiment of the present invention, the switching unit 200 may have a topology structure as shown in fig. 1, and includes a first switching tube and a second switching tube (i.e., an upper tube and a lower tube shown in fig. 1) connected in series, where: the first end of the first switching tube and the second end of the second switching tube are input sides of the switching unit 200; the second end of the first switching tube is connected to the first end of the second switching tube, and the third ends of the first switching tube and the second switching tube are control ends of the first switching tube and the second switching tube as output terminals of the switching unit 200.
In the resonant converter disclosed in the embodiment of the present invention, the topology type of the resonant network 300 is not limited, and may be an LLC resonant network, an LCC resonant network, or other topology types, and fig. 1 only uses an LLC resonant network as an example. In fig. 1, the LLC resonant unit includes a resonant inductance Lr, an excitation inductance Lm, and a resonant capacitance Cr, in which: one end of the resonant inductor Lr is connected to the output terminal of the switching unit 200, and the other end is connected to one end of the excitation inductor Lm; the other end of the excitation inductance Lm is connected to one end of the resonance capacitor Cr, and the other end of the resonance capacitor Cr is connected to the negative output terminal of the rectifier bridge 100. Here, the excitation inductance Lm may be an external inductance or may be integrated in a transformer of the resonant converter.
In the resonant converter disclosed in the embodiment of the present invention, the shunt unit 500 may adopt any one of the following three topology types, which is specifically described as follows:
1) The first topology type of the shunt unit 500 includes a diode D1 and a first capacitance C1; the cathode of the diode D1 is connected with the negative output terminal of the rectifier bridge 100, and the anode of the diode D1 is connected with the negative end of the bus capacitor C2; the first capacitor C1 is connected in parallel with the diode D1 as shown in fig. 2;
2) The second topology type of the shunt unit 500 includes a diode D1 and a third capacitance C3; the cathode of the diode D1 is connected with the negative output terminal of the rectifier bridge 100, and the anode of the diode D1 is connected with the negative end of the bus capacitor C2; one end of the third capacitor C3 is connected with the cathode of the diode D1, and the other end of the third capacitor C3 is connected with the high-potential end of the bus capacitor C2, as shown in FIG. 3;
3) The third topology type of the shunt unit 500 is based on the second topology type, and further includes a fourth capacitor C4; the fourth capacitor C4 is connected in parallel with the diode D1 as shown in fig. 4.
Next, taking fig. 2 as an example, the working principle of the resonant converter disclosed in the embodiment of the present invention is described in detail.
The structure of the resonant converter in the prior art is shown in fig. 5, and includes a rectifier bridge 100, a bus capacitor C2, a switch unit 200, a resonant network 300, and a control unit 400, where:
the output side of the rectifier bridge 100 is connected with a busbar capacitor C2 in parallel;
the input side of the switch unit 200 is connected with a bus capacitor C2 in parallel;
an output terminal of the switching unit 200 is connected to a positive input terminal of the resonant network 300;
the negative input terminal of the resonant network 300 is connected to the negative output terminal of the rectifier bridge 100;
the control unit 400 receives a sampling signal Is representing an output parameter of the resonant converter, and a signal output end of the sampling signal Is connected with a control end of a switching tube in the switching unit 200 and Is used for controlling the working frequency of the switching tube in the switching unit 200 according to the sampling signal Is so that the sampling signal Is reaches a preset reference signal.
The resonant converter shown in fig. 5 has three modes of operation, f respectively r ＜f s ＜f o 、f s ＝f o And f s >f o In the corresponding working mode of the device,f s is the resonant frequency of the resonant network 300. Hereinafter denoted by f r ＜f s ＜f o For example, the operating waveforms of the resonant converter shown in fig. 5 were analyzed.
Resonant current I in the resonant converter of FIG. 5 Lr (resonant Current I) Lr As indicated by the arrow in fig. 5) and the waveform of the current flowing through the rectifier bridge 100 are respectively referred to waveforms B1, B2 (Ts represents one switching cycle) shown in fig. 6, since there is only a forward resonant current I Lr The reverse resonant current I can flow through the rectifier bridge 100 Lr Cannot flow through the rectifier bridge 100, so that the current flowing through the rectifier bridge 100 is the resonant current I with a current value greater than zero Lr 。
Resonant current I Lr The forward resonant current flowing through the rectifier bridge 100 is also a high-frequency current, and the frequency of the high-frequency current is the same as the operating frequency of the resonant converter, however, the waveform of the input voltage and current of the converter in the power frequency period affects the PF value, specifically: resonant current I under the condition that the input voltage and the output load of the resonant converter are unchanged Lr The current flowing through the rectifier bridge 100 is unchanged, so that the input current Iin of the rectifier bridge 100 is a square wave in the power frequency period, as shown in fig. 7 (Vin in fig. 7 represents the input voltage of the rectifier bridge 100, is a sine wave; and the input voltage and current of the rectifier bridge 100 are the input voltage and current of the resonant converter).It is known that the closer the waveforms of Iin and Vin are, the higher the PF value of the resonant converter, while Vin is a sine wave, so the closer Iin is to the sine wave, the higher the PF value of the resonant converter is. However, as can be seen from fig. 7, in the resonant converter shown in fig. 5, iin is a square wave, so that the PF value of the resonant converter shown in fig. 5 is low.
In order to increase the PF value of the resonant converter shown in fig. 5, the present embodiment connects the shunt unit 500 shown in fig. 1 to the resonant converter shown in fig. 5, and uses the shunt unit 500 to couple the forward resonant current I Lr And (5) splitting. Taking the resonant converter shown in fig. 5 as an example, the shunt unit 500 shown in fig. 2 is connected to the resonant converter, as shown in fig. 8, and the resonant current I is positive Lr One part flows through the rectifier bridge 100 (denoted as current Idc) and the other part flows through the capacitor C1 (denoted as current Id) in the shunt unit 500, I Lr =idc+id; diode D1 in the shunt unit 500 is used to cut off the forward resonant current I Lr While diode D1 is a reverse resonant current I Lr Providing access.
In fig. 8, id flows through the capacitor C1 to generate a voltage Vd, and at this time, the voltage Vd across the capacitor C1, the voltage Vbus across the bus capacitor C2, and the voltage Vdc on the output side of the rectifier bridge 100 satisfy the relation vd=vbus-Vdc. The waveform of Vd, vbus, vdc is shown in fig. 9.
The shunt unit 500 shunts a high frequency shunt, which has the same envelope shape and Vd at the power frequency period, and because idc=i Lr Id, idc, I at power frequency period L (this embodiment records the resonant current at the power frequency period as I) L And resonant current I at high frequency period Lr Distinguishing), the waveforms of Id, iin are as shown in fig. 10, and although Iin in fig. 10 is closer to a sine wave than Iin in fig. 9, the waveform of Iin is still distorted from a sine wave because of the large dc component of Id. However, as can be seen from a review of fig. 10, if the dc component of Id can be removed or reduced, the resulting Iin is closer to a sine wave.
To remove or reduce the dc component of Id in fig. 10, the present embodiment injects the compensation signal Ic into the control unit 400, resulting in a resonant converter as shown in fig. 2. Injecting the compensation signal Ic changes the resonance changeThe operating frequency of the converter, thereby changing the resonant current I Lr While changing the operating frequency of the resonant converter does not change the waveform of Id (or Vd), the present embodiment injects the compensation signal Ic into the control unit 400 such that the operating frequency of the resonant converter Is related not only to the sampling signal Is but also to the compensation signal Ic; in other words, the control unit 400 Is capable of controlling the operating frequency of the resonant converter in accordance with the sampling signal Is and the compensation signal Ic. Specifically, the injected compensation signal Ic needs to satisfy: the injected compensation signal Ic can make the working frequency of the resonant converter be highest at zero crossing point of the input voltage of the resonant converter and lowest at peak value and valley value of the input voltage of the resonant converter, so that the resonant current I Lr The zero crossing point of the input voltage of the resonant converter is lowest, and the peak value and the valley value of the input voltage of the resonant converter are highest, so that the resonant current I in the power frequency period L The zero crossing is also lowest at the resonant converter input voltage and the peak and valley values are highest at the resonant converter input voltage, as shown in fig. 11.
Referring to fig. 11, the current waveform of the shunt unit 500 is not changed by increasing the compensation signal Ic, so that the waveform of the current Id flowing through the shunt unit 500 in the power frequency period is not changed, and the resonant current I in the power frequency period after the compensation signal Ic is increased L Waveform changes, so that the waveform of the current Idc flowing through the rectifier bridge 100 changes (idc=i L Id), the input current Iin of the rectifier bridge 100 after adding the compensation signal Ic is more sinusoidal, so that the PF value of the resonant converter shown in fig. 2 is higher and THD (Total Harmonic Distortion ) is lower.
As shown in fig. 12, the control unit 400 specifically includes a frequency control module 401 and a comparison module 402; the comparison module 402 takes the sampling signal Is as an input signal, and Is used for comparing the sampling signal Is with a preset reference signal Vref to generate a feedback signal; the signal output end of the frequency control module 401 Is connected to the control end of the switching tube in the switching unit 200, and takes the compensation signal Ic and the feedback signal output by the comparison module 402 as input signals, so that the sampling signal Is equal to the reference signal according to the feedback signal on the one hand, and the operating frequency of the switching tube in the switching unit 200 (the operating frequency of the switching tube in the switching unit 200 Is the operating frequency of the resonant converter) Is controlled according to the compensation signal Ic on the other hand, so as to improve the PF value and THD of the resonant converter.
The output result of the frequency control module 401 may be positive correlation between the magnitude of the operating frequency of the resonant converter and the magnitude of the compensation signal Ic, or may be negative correlation between the magnitude of the operating frequency of the resonant converter and the magnitude of the compensation signal Ic.
When the output result of the frequency control module 401 is a positive correlation between the magnitude of the operating frequency of the resonant converter and the magnitude of the compensation signal Ic, the magnitude of the compensation signal Ic is highest at the zero crossing point of the resonant converter input voltage and lowest at the peak and valley of the resonant converter input voltage, the frequency of the compensation signal Ic being the same as the resonant converter input voltage frequency. For example, the waveform of the compensation signal Ic can be the same as or proportional to Id (or Vd), then the resonant current I at power frequency L The waveform of Idc becomes as shown in fig. 11, and the dc component of Idc is reduced, so that Iin after adding the compensation signal Ic is more similar to a sine wave, thereby increasing the PF value and decreasing THD. In this case, in fig. 2 to 4, the compensation signal Ic can be obtained from the cathode of the diode D1.
When the output result of the frequency control module 401 is that the magnitude of the operating frequency of the resonant converter and the magnitude of the compensation signal Ic are inversely related, the magnitude of the compensation signal Ic is lowest at the zero crossing point of the resonant converter input voltage and highest at the peak and valley of the resonant converter input voltage, and the frequency of the compensation signal Ic is the same as the resonant converter input voltage frequency.
In summary, the present embodiment splits the forward resonant current and provides a path for the backward resonant current by introducing the splitting unit 500 into the resonant converter, so that the resonant converter input current is changed from a square wave to a sine wave with a certain distortion, and reduces or even eliminates the distortion by introducing the compensation signal Ic, so that the current resonant converter input current is more similar to the sine wave, and the resonant converter PF value and THD are improved.
Finally, it should be noted that, the switching of the working mode of the resonant network 300 and the changing of the topology types of the resonant network 300 and the shunt unit 500 will not change the implementation of the above technical effects, and the analysis principles thereof are the same and will not be described in detail herein.
In the present specification, each embodiment is described in a progressive manner, and each embodiment is mainly described in a different point from other embodiments, and identical and similar parts between the embodiments are all enough to refer to each other.
The previous description of the disclosed embodiments is provided to enable any person skilled in the art to make or use the present invention. Various modifications to these embodiments will be readily apparent to those skilled in the art, and the generic principles defined herein may be applied to other embodiments without departing from the spirit or scope of the embodiments of the invention. Thus, the present embodiments are not intended to be limited to the embodiments shown herein but is to be accorded the widest scope consistent with the principles and novel features disclosed herein.
Claims (9)
1. The utility model provides a resonant converter which characterized in that includes rectifier bridge, bus-bar capacitance, switch element, resonant network, control unit and reposition of redundant personnel unit, wherein:
the positive output terminal of the rectifier bridge is connected with one end of the bus capacitor;
the input side of the switch unit is connected with the bus capacitor in parallel;
the output terminal of the switch unit is connected with the positive input terminal of the resonant network;
the negative input terminal of the resonant network is connected with the negative output terminal of the rectifier bridge;
the shunt unit is connected between the negative output terminal of the resonant network and the bus capacitor and is used for shunting forward resonant current and providing a passage for reverse resonant current; the current-dividing unit comprises a diode and a capacitor, one part of forward resonance current flows through the rectifier bridge, and the other part of forward resonance current flows through the capacitor in the current-dividing unit;
the control unit receives a compensation signal and a sampling signal representing an output parameter of the resonant converter, and generates a driving control signal according to the compensation signal and the sampling signal, wherein the driving control signal is output to a control end of a switching tube in the switching unit; wherein the compensation signal is a signal indicating the control unit to raise the operating frequency of the resonant converter at the zero crossing point of the input voltage of the rectifier bridge and to lower the operating frequency of the resonant converter at the peak value and the valley value of the input voltage of the rectifier bridge;
the control unit comprises a frequency control module and a comparison module, wherein:
the comparison module receives the sampling signal and is used for comparing the sampling signal with a preset reference signal to generate a feedback signal;
the frequency control module receives the feedback signal and the compensation signal, and is used for generating a driving control signal according to the feedback signal and the compensation signal, wherein the compensation signal is obtained from the cathode of the diode.
2. The resonant converter of claim 1, wherein the switching unit comprises a first switching tube and a second switching tube in series, wherein:
the first end of the first switching tube and the second end of the second switching tube are input sides of the switching unit; the second end of the first switching tube is connected with the first end of the second switching tube, and the third ends of the first switching tube and the second switching tube are control ends of the first switching tube and the second switching tube as output terminals of the switching unit.
3. The resonant converter of claim 2, wherein the resonant converter is an LLC resonant converter;
the LLC resonant converter comprises a resonant inductor, a resonant capacitor and an excitation inductor; one end of the resonant inductor is connected with the output terminal of the switch unit, and the other end of the resonant inductor is connected with one end of the excitation inductor; the other end of the excitation inductance is connected with one end of the resonance capacitor, and the other end of the resonance capacitor is connected with the negative output terminal of the rectifier bridge.
4. A resonant converter according to claim 3, wherein the shunt unit comprises a diode and a first capacitance, wherein:
the cathode of the diode is connected with the negative output terminal of the rectifier bridge, and the anode of the diode is connected with the negative terminal of the bus capacitor; the first capacitor is connected in parallel with the diode.
5. A resonant converter according to claim 3, wherein the shunt unit comprises a third capacitance of a diode, wherein:
the cathode of the diode is connected with the negative output terminal of the rectifier bridge, and the anode of the diode is connected with the negative terminal of the bus capacitor;
one end of the third capacitor is connected with the cathode of the diode, and the other end of the third capacitor is connected with the high-potential end of the bus capacitor.
6. The resonant converter of claim 5, wherein the shunt unit further comprises a fourth capacitance, the fourth capacitance being in parallel with the diode.
7. The resonant converter of any of claims 1-6, wherein the output of the frequency control module is a negative correlation of the magnitude of the operating frequency of the resonant converter and the magnitude of the compensation signal;
correspondingly, the amplitude of the compensation signal is lowest at the zero crossing point of the input voltage of the rectifier bridge and highest at the peak value and the valley value of the input voltage of the rectifier bridge; the frequency of the compensation signal is the same as the frequency of the resonant converter input voltage.
8. The resonant converter of any of claims 1-6, wherein the output of the frequency control module is a positive correlation of the magnitude of the operating frequency of the resonant converter and the magnitude of the compensation signal;
correspondingly, the amplitude of the compensation signal is highest at the zero crossing point of the input voltage of the rectifier bridge and lowest at the peak value and the valley value of the input voltage of the rectifier bridge; the frequency of the compensation signal is the same as the frequency of the resonant converter input voltage.
9. The resonant converter of any of claims 4-6, wherein the output of the frequency control module is a positive correlation of the magnitude of the operating frequency of the resonant converter and the magnitude of the compensation signal.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201710703224.2A CN107257194B (en) | 2017-08-16 | 2017-08-16 | Resonant converter |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201710703224.2A CN107257194B (en) | 2017-08-16 | 2017-08-16 | Resonant converter |
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| Publication Number | Publication Date |
|---|---|
| CN107257194A CN107257194A (en) | 2017-10-17 |
| CN107257194B true CN107257194B (en) | 2024-04-02 |
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| CN201710703224.2A Active CN107257194B (en) | 2017-08-16 | 2017-08-16 | Resonant converter |
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| CN111629496B (en) * | 2020-06-12 | 2022-01-25 | 英飞特电子（杭州）股份有限公司 | Charge pump control circuit and driving power supply |
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| US5559688A (en) * | 1993-05-19 | 1996-09-24 | 1,005,539 Ontario Inc. | Resonant power factor converter |
| US5598326A (en) * | 1994-02-10 | 1997-01-28 | Philips Electronics North America | High frequency AC/AC converter with PF correction |
| EP1164689A2 (en) * | 2000-06-16 | 2001-12-19 | FORFAS, (trading as PEI Technologies) | A single stage ac/dc converter |
| US6359395B1 (en) * | 2000-12-06 | 2002-03-19 | Fazle S. Quazi | Control circuit for power factor corrected electronic ballasts and power supplies |
| CN106787675A (en) * | 2016-12-28 | 2017-05-31 | 成都芯源系统有限公司 | Resonant converter with power factor correction function and controller thereof |
| CN207304371U (en) * | 2017-08-16 | 2018-05-01 | 英飞特电子（杭州）股份有限公司 | A kind of controlled resonant converter |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| KR20050048692A (en) * | 2002-10-21 | 2005-05-24 | 어드밴스드 파워 테크놀로지 인코포레이티드 | Ac-dc power converter having high input power factor and low harmonic distortion |
| NZ563188A (en) * | 2007-11-05 | 2010-03-26 | Auckland Uniservices Ltd | Power control |
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Patent Citations (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5559688A (en) * | 1993-05-19 | 1996-09-24 | 1,005,539 Ontario Inc. | Resonant power factor converter |
| US5598326A (en) * | 1994-02-10 | 1997-01-28 | Philips Electronics North America | High frequency AC/AC converter with PF correction |
| EP1164689A2 (en) * | 2000-06-16 | 2001-12-19 | FORFAS, (trading as PEI Technologies) | A single stage ac/dc converter |
| US6359395B1 (en) * | 2000-12-06 | 2002-03-19 | Fazle S. Quazi | Control circuit for power factor corrected electronic ballasts and power supplies |
| CN106787675A (en) * | 2016-12-28 | 2017-05-31 | 成都芯源系统有限公司 | Resonant converter with power factor correction function and controller thereof |
| CN207304371U (en) * | 2017-08-16 | 2018-05-01 | 英飞特电子（杭州）股份有限公司 | A kind of controlled resonant converter |
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| CN107257194A (en) | 2017-10-17 |
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