WO2018040799A1 - Online uninterruptible power supply - Google Patents

Online uninterruptible power supply Download PDF

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Publication number
WO2018040799A1
WO2018040799A1 PCT/CN2017/094226 CN2017094226W WO2018040799A1 WO 2018040799 A1 WO2018040799 A1 WO 2018040799A1 CN 2017094226 W CN2017094226 W CN 2017094226W WO 2018040799 A1 WO2018040799 A1 WO 2018040799A1
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WO
WIPO (PCT)
Prior art keywords
bus
voltage
negative
positive
power supply
Prior art date
Application number
PCT/CN2017/094226
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French (fr)
Chinese (zh)
Inventor
蔡火圆
张起校
胡双平
张怀超
高鹏
Original Assignee
伊顿制造（格拉斯哥）有限合伙莫尔日分支机构
蔡火圆
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Application filed by 伊顿制造（格拉斯哥）有限合伙莫尔日分支机构, 蔡火圆 filed Critical 伊顿制造（格拉斯哥）有限合伙莫尔日分支机构
Publication of WO2018040799A1 publication Critical patent/WO2018040799A1/en

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J9/00—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting
    • H02J9/04—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source
    • H02J9/06—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems
    • H02J9/062—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems for AC powered loads
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J9/00—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting
    • H02J9/04—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source
    • H02J9/06—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4216—Arrangements for improving power factor of AC input operating from a three-phase input voltage
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • This invention relates to uninterruptible power supplies, and more particularly to an online uninterruptible power supply.
  • the online uninterruptible power supply continuously supplies power to the load and has been widely used in various fields.
  • the online uninterruptible power supply 1 includes a safety switch 12, a power factor correction circuit (PFC) 13, a half bridge inverter 14 and a bypass switch 17 which are sequentially connected between the AC input terminal 10 and the AC output terminal 11, wherein the PFC 13 The output is connected to the input of the half-bridge inverter 14 and serves as a DC bus.
  • the bypass switch 17 is used to connect the output of the half-bridge inverter 14 and one of the inputs of the PFC 13 to the AC output 11 .
  • the online uninterruptible power supply 1 further includes a charger 15 and a push-pull circuit 16 connected in series, wherein the input of the charger 15 is connected to the AC input terminal 10, and the output of the charger 15 is connected to the input terminal of the push-pull circuit 16. To both ends of the rechargeable battery 18, the output of the push-pull circuit 16 is connected to the DC bus.
  • the online uninterruptible power supply 1 of Fig. 1 has the following four modes of operation.
  • the control safety switch 12 is in an on state, and the bypass switch 17 is controlled such that the output of the half bridge inverter 14 is connected to the AC output terminal 11, and the control PFC 13, the half bridge inverter 14 and the charger 15 are in operation.
  • the mains (alternating current) of the AC input terminal 10 supplies power to the load (not shown in FIG. 1) connected to the AC output terminal 11 through the safety switch 12, the PFC 13 and the half-bridge inverter 14, while the charger 15 pairs The rechargeable battery 18 at its output is charged.
  • the control safety switch 12 is in an off state, and the bypass switch 17 is controlled such that the output of the half bridge inverter 14 is connected to the AC output terminal 11, and the control push-pull circuit 16 and the half-bridge inverter 14 are in operation.
  • the rechargeable battery 18 supplies power to the load through the push-pull circuit 16 and the half-bridge inverter 14.
  • ECO Economic Operation Mode
  • Bypass mode The control safety switch 12 is in an on state, and the bypass switch 17 is controlled such that the input of the PFC 13 is connected to the AC output terminal 11 and the control charger 15 is in an active state.
  • the PFC 13, the half-bridge inverter 14, the charger 15, and the push-pull circuit 16 in the online uninterruptible power supply 1 shown in FIG. 1 operate as independent circuit modules in respective operating modes, so the online uninterruptible power supply
  • the utilization rate of the electronic device in 1 is low, resulting in a large number of electronic devices and a high cost.
  • an embodiment of the present invention provides an online uninterruptible power supply, including:
  • a power factor correction circuit and an inverter, an output of the power factor correction circuit being coupled to an input of the inverter to form a positive DC bus and a negative DC bus;
  • Push-pull circuit which includes:
  • a transformer comprising a primary winding and a secondary winding
  • a rectifier circuit an input end of the rectifier circuit is connected to the secondary winding, and an output terminal is connected to the positive DC bus and the negative DC bus;
  • a unidirectional controllable charging line connected between the negative input terminal of the push-pull circuit and the other end of the charging winding
  • the unidirectional controllable charging line comprises a first diode and a switching device connected in series.
  • the unidirectionally controllable charging line further includes a first inductance in series with the first diode and the switching device.
  • the online uninterruptible power supply further includes a second inductor and a third inductor respectively connected to the output end of the rectifier circuit.
  • the in-line uninterruptible power supply further includes a second diode in series with the first switching transistor and a third diode in series with the second switching transistor.
  • the rectifier circuit is a full bridge rectifier circuit.
  • the online uninterruptible power supply further includes control means for controlling the power factor correction circuit, the inverter, the push-pull circuit, the first switch tube, the second switch tube, and the one-way Control the working state of the charging line.
  • control device is configured to control the power factor correction circuit and the inverter to operate, and control the one-way controllable charging line to be turned on, and
  • the first switch is controlled to be turned off, and the second switch is controlled to operate in a pulse width modulation manner.
  • control device is configured to control the power factor correction circuit and the inverter to operate, and
  • a switch tube operates in a pulse width modulation mode, and controls the second switch tube to be turned off;
  • a switch tube is turned off, and the second switch tube is controlled to operate in a pulse width modulation mode.
  • control device is configured to control the operation of the inverter, and control the disconnection of the one-way controllable charging line, and
  • the push-pull circuit operates, and controls the first switch tube and the second switch tube to be turned off;
  • a switch tube operates in a pulse width modulation mode, and controls the second switch tube and the switch tube in the push-pull circuit to be turned off;
  • the push-pull circuit operates, and controls the first switch tube and the second switch tube to be turned off;
  • the online uninterruptible power supply of the present invention significantly reduces the cost, improves the input total harmonic current distortion rate (THDI) during charging, and improves the half-wave load capability.
  • TDDI total harmonic current distortion rate
  • FIG. 1 is a circuit diagram of an in-circuit uninterruptible power supply in the prior art.
  • FIG. 2 is a circuit diagram of an in-line uninterruptible power supply in accordance with a first embodiment of the present invention.
  • FIG. 3 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in an online mode.
  • FIG. 4 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in a battery mode.
  • Figure 5 is a circuit diagram of an in-line uninterruptible power supply in accordance with a second embodiment of the present invention.
  • Figure 6 is a circuit diagram of an in-line uninterruptible power supply in accordance with a third embodiment of the present invention.
  • the online uninterruptible power supply 2 is basically the same as the online uninterruptible power supply 1 shown in FIG. 1, so that the same or similar components have the same reference numerals, except that the online uninterruptible power supply 2 does not have an expensive charger. 15.
  • the online uninterruptible power supply 2 further includes a charging winding W1 on the primary side of the transformer TX wound in the push-pull circuit 26, connected to the negative pole of the rechargeable battery 28 (i.e., the negative input terminal of the push-pull circuit 26) and the charging winding W1.
  • a one-way controllable charging line 29 a switching tube Q4 connected between the positive DC bus B1 and one end of the secondary winding of the transformer TX, and the other end of the secondary winding connected to the transformer TX and the negative DC bus B2 Switch tube Q5.
  • the online uninterruptible power supply 2 further includes a control device 200 for controlling the power factor correction circuit 23, the half bridge inverter 24, the push-pull circuit 26, the switching transistor Q4, the switching transistor Q5, and the one-way controllable charging line 29.
  • a control device 200 for controlling the power factor correction circuit 23, the half bridge inverter 24, the push-pull circuit 26, the switching transistor Q4, the switching transistor Q5, and the one-way controllable charging line 29.
  • FIG. 3 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in an online mode.
  • the full switch 22 is in an on state, the output of the half bridge inverter 24 is connected to the AC output terminal 21 via the bypass switch 27, and the control device 200 controls the PFC 23 and the half bridge inverter 24 to be in operation, thus the AC input
  • the mains (i.e., alternating current) of the terminal 20 supplies power to a load (not shown in Fig. 3) connected to the alternating current output terminal 21 via the safety switch 22, the PFC 23, and the half bridge inverter 24.
  • the primary winding of the transformer TX has a tap T5 connected to the anode of the rechargeable battery 28 (ie, the positive input terminal of the push-pull circuit 26), and the secondary winding has terminals T1, T3 and is connected to the neutral line. N tap T2.
  • the input end of the full bridge rectifier circuit 261 is connected to both ends of the secondary winding of the transformer TX, and its positive output terminal 2611 (connected to the positive DC bus B1) is connected to the terminal T1 of the transformer TX through the switch Q4, and the terminal T3 of the transformer TX It is connected to its negative output terminal 2612 (connected to the negative DC bus B2) through the switching transistor Q5.
  • the negative electrode of the rechargeable battery 28 (i.e., the negative input terminal of the push-pull circuit 26) is connected to the charging winding W1 through a one-way controllable charging line 29.
  • the switching transistor Q4, the switching transistor Q5, the charging winding W1, the unidirectional controllable charging line 29, a portion of the transformer TX, and the full bridge rectifier circuit 261 constitute a charger 25 for charging the rechargeable battery 28.
  • the mode of operation of the charger 25 is described in detail below.
  • the control device 200 controls the one-way controllable charging line 29 to be turned on, the switch tube Q5 to be turned off, and the switch tube Q4 to operate in a pulse width modulation mode (ie, to the switch tube Q4)
  • a pulse width modulated signal is provided to cause its high frequency to be turned on and off).
  • the switch tube Q4 is turned on, the winding between the terminal T1 of the transformer TX and the tap T2 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the positive DC bus B1, the switch Q4, the terminal T1 of the transformer TX, and the tap T2 to neutral Line N.
  • the battery charging circuit formed at this time is as follows: the tap T5 of the transformer TX, the positive and negative electrodes of the rechargeable battery 28, the diode D6, the switching device RY3, the charging winding W1, the terminal T6 of the transformer TX, and the tap T5 of the transformer TX. Thereby, the capacitor C1 connected between the positive DC bus B1 and the neutral line N is discharged and the rechargeable battery 28 is charged.
  • the winding between the tap T2 of the transformer TX and the terminal T3 acts as a demagnetization inductance, and the demagnetization loop formed is as follows: neutral line N, tap of the transformer TX T2, terminal T3, diode D5 to positive DC bus B1.
  • the demagnetization circuit is formed as follows: a negative DC bus B2, a diode D8, a transformer Terminal T1 of TX, tap T2 to neutral line N.
  • the control device 200 controls the one-way controllable charging line 29 to be turned on, the switch tube Q4 to be turned off, and the switch tube Q5 to be controlled in a pulse width modulation manner.
  • the switch tube Q5 When the switch tube Q5 is turned on, the winding between the tap T2 of the transformer TX and the terminal T3 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, the switch tube Q5 to the negative direct current Bus B2.
  • the same battery charging circuit is formed, so that the capacitor C5 connected between the neutral line N and the negative DC bus B2 is discharged and the rechargeable battery 28 is charged.
  • the demagnetization circuit is formed as follows: a negative DC bus B2, a diode D8, a transformer Terminal T1 of TX, tap T2 to neutral line N.
  • the winding between the tap T2 of the transformer TX and the terminal T3 acts as a demagnetization inductance, and the demagnetization loop formed is as follows: neutral line N, tap of the transformer TX T2, terminal T3, diode D5 to positive DC bus B1.
  • the half-bridge architecture has the following problems.
  • the output is positive half-cycle
  • the excess energy in the inductance of the half-bridge inverter 24 is fed back to the capacitor C5
  • the output is negative half cycle
  • the excess energy in the inductance in the half bridge inverter 24 is fed back to the capacitor C1.
  • the online uninterruptible power supply 2 has a half-wave load
  • the energy fed back by the inductance of the half-bridge inverter 24 will cause the voltage on the positive DC bus B1 or the negative DC bus B2 to rise all the time, resulting in overvoltage protection of the machine bus.
  • the half-wave load capacity is very low.
  • the half-wave load capacity can also be improved by the following control method.
  • the difference between the voltage on the capacitor C1 and the voltage on the capacitor C5 is greater than a predetermined first threshold or the voltage on the capacitor C1 is greater than the bus voltage over-high protection threshold.
  • the control device 200 controls the switching transistor Q5 to be turned off, and controls the switching transistor Q4 to operate in a pulse width modulation mode.
  • the control switch Q4 When the control switch Q4 is turned on, the winding between the terminal T1 of the transformer TX and the tap T2 acts as the exciting inductance, and the excitation circuit is formed as follows: the positive DC bus B1, the switch Q4, the terminal T1 of the transformer TX, and the tap T2 to the middle Sex line N.
  • the negative DC bus charging circuit formed at this time is as follows: negative DC bus B2, diode D7, terminal T3 of the transformer TX, tap T2 to the neutral line N; if the switching device RY3 is in the on state at this time, the same battery charging will be formed. Loop.
  • the demagnetization circuit formed by it is as follows: a negative DC bus B2, a diode D8, a terminal T1 of the transformer TX, and a tap T2 to the neutral line N.
  • control device 200 The control switch Q4 is turned off, and the switch tube Q5 is controlled to operate in a pulse width modulation mode.
  • the control switch tube Q5 When the control switch tube Q5 is turned on, the winding between the tap T2 of the transformer TX and the terminal T3 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the switch tube Q5 to the negative DC bus B2.
  • the positive DC bus charging circuit formed at this time is as follows: neutral line N, tap T2 of the transformer TX, terminal T1, diode D4 to the positive DC bus B1; if the switching device RY3 is in the on state at this time, the same battery charging will be formed. Loop.
  • the demagnetization circuit formed by it is as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the diode D5 to the positive DC bus B1.
  • first threshold second threshold
  • bus voltage over-protection threshold Those skilled in the art can set appropriate first threshold, second threshold, and bus voltage over-protection threshold according to the type and specification of the online uninterruptible power supply and the specifications of the capacitors C1 and C5 therein.
  • the invention is therefore not limited to a predetermined first threshold, a predetermined second threshold, and a specific range of bus voltage over-high protection thresholds.
  • the charger 25 repeatedly utilizes the full bridge rectifier circuit 261 and the transformer TX in the push-pull circuit 26 to charge the rechargeable battery 28, and since the charging process of the rechargeable battery 28 is controllable, the charging process can Improve total harmonic current distortion rate and improve power factor.
  • the online uninterruptible power supply 2 of the present invention can also maintain a substantially balanced voltage across the positive and negative DC busses B1, B2, improving the half-wave load capability.
  • FIG. 4 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in a battery mode.
  • the safety switch 22 and the switching device RY3 are in an off state, the output of the half bridge inverter 24 is connected to the AC output terminal 21 through the bypass switch 27, and the control device 200 controls the switching transistors Q4 and Q5 to be turned off, and controls the push-pull circuit 26
  • the half-bridge inverter 24 is in operation and the rechargeable battery 28 supplies power to the load via the push-pull circuit 26 and the half-bridge inverter 24.
  • the online uninterruptible power supply 2 has the same problem as the half-wave load capability in the battery mode as in the mains mode.
  • the online uninterruptible power supply 2 of the present embodiment can be improved in its half-wave load capability by the following control method.
  • the difference between the voltage on the capacitor C1 and the voltage on the capacitor C5 is greater than a predetermined first threshold or the voltage on the capacitor C1 is greater than the bus voltage over-high protection threshold.
  • the control device 200 controls the switching transistors in the switching transistor Q5 and the push-pull circuit 26 to be turned off, and controls the switching transistor Q4 to operate in a pulse width modulation manner.
  • the control switch Q4 is turned on, the terminal T1 and the tap of the transformer TX
  • the winding between T2 acts as a magnetizing inductance, and the resulting excitation circuit is as follows: positive DC bus B1, switching transistor Q4, terminal T1 of transformer TX, tap T2 to neutral line N.
  • the negative DC bus charging circuit formed at this time is as follows: negative DC bus B2, diode D7, terminal T3 of transformer TX, and tap T2 to neutral line N.
  • the demagnetization circuit formed by it is as follows: a negative DC bus B2, a diode D8, a terminal T1 of the transformer TX, and a tap T2 to the neutral line N.
  • the control device 200 controls the switch Q4, Q5 is turned off and the push-pull circuit 26 is controlled to operate so that the rechargeable battery 28 supplies power to the load again through the push-pull circuit 26 and the half-bridge inverter 24.
  • the difference between the voltage on the capacitor C5 and the voltage on the capacitor C1 is greater than a predetermined second threshold or the voltage on the capacitor C5 is greater than the bus voltage over-high protection threshold.
  • the control device 200 controls the switching transistors in the switching transistor Q4 and the push-pull circuit 26 to be turned off, and controls the switching transistor Q5 to operate in a pulse width modulation manner.
  • the control switch tube Q5 When the control switch tube Q5 is turned on, the winding between the tap T2 of the transformer TX and the terminal T3 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the switch tube Q5 to the negative DC bus B2.
  • the positive DC bus charging circuit formed at this time is as follows: neutral line N, tap T2 of the transformer TX, terminal T1, diode D4 to the positive DC bus B1.
  • the demagnetization circuit formed by it is as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the diode D5 to the positive DC bus B1.
  • the control device 200 controls the switch Q4, Q5 is turned off and the push-pull circuit 26 is controlled to operate so that the rechargeable battery 28 supplies power to the load again through the push-pull circuit 26 and the half-bridge inverter 24.
  • the on-line uninterruptible power supply 2 of the present invention can maintain the basic balance of the voltages on the positive and negative DC buses B1 and B2 in the battery mode, and improve the half-wave load capability without additional components, which significantly reduces the cost.
  • the safety switch 22 and the switching device RY3 are in an on state, and the bypass switch 27 is controlled such that the input end of the PFC 23 is connected to the AC output terminal 21, and the PFC 23 and the charger 25 are controlled to operate.
  • the rechargeable battery 28 is charged.
  • bypass mode of the online uninterruptible power supply 2 the safety switch 22 and the switching device RY3 are in an on state, and the bypass switch 27 is controlled such that the input end of the PFC 23 is connected to the AC output terminal 21, and the charger 25 is controlled to operate to be rechargeable.
  • the battery 28 is charged.
  • FIG. 5 is a circuit diagram of an in-line uninterruptible power supply 3 in accordance with a second embodiment of the present invention. It is substantially the same as FIG. 2, and the components denoted by reference numerals 30, 31, 32, 33, 34, 36, 37, 38, and 300 in FIG. 5 are the same as the components indicated by the corresponding reference numerals in FIG.
  • the unidirectionally controllable charging line 39 also includes an inductance L5 in series with the diode D36. During charging of the rechargeable battery 38, the inductor L5 acts to limit the charging current while reducing the charging ripple current to avoid damage to the rechargeable battery 38.
  • FIG. 6 is a circuit diagram of an in-line uninterruptible power supply 4 in accordance with a third embodiment of the present invention. It is substantially the same as FIG. 5, and the components denoted by reference numerals 40, 41, 42, 33, 44, 46, 47, 48, 49, and 400 in FIG. 6 are the same as those shown by the corresponding reference numerals in FIG. 5. The difference is that the online uninterruptible power supply 4 further includes a diode D3 connected in series with the switching transistor Q44, a diode D9 connected in series with the switching transistor Q45, an inductance L4 connected to the positive output terminal 4611 of the full bridge rectifier circuit, and a connection at the full bridge.
  • diodes D3 and D9 prevent current in the secondary winding of the transformer from flowing through switches Q44 and Q45, allowing inductors L4 and L6 to filter the current in the secondary winding of the transformer, reducing the ripple of the output current. wave.
  • a series of unidirectional controllable conduction devices may be used in place of the series connected diode D6 and switching device RY3 in the above embodiments.
  • any power factor correction circuit of the prior art may be employed instead of the power factor correction circuits 23, 33, 43 of the above embodiment.
  • any of the prior art inverters may be employed in place of the half bridge inverters 24, 34, 44 of the above embodiments.

Abstract

An online uninterruptible power supply comprises: a positive DC bus (B1) and a negative DC bus (B2); a push-pull circuit (26), comprising a positive input terminal, a negative input terminal, a transformer (TX) having a primary winding and a secondary winding, and a rectification circuit (261) having an input end thereof connected to the secondary winding and an output end thereof connected to the positive DC bus (B1) and the negative DC bus (B2); a charging winding (W1), wound at the primary side of the transformer (TX), having one end thereof connected to one end of the primary winding; a unidirectional controllable charging circuit (29), connected between the negative input terminal of the push-pull circuit (26) and the other end of the charging winding (W1); and a first switch transistor (Q4) and a second switch transistor (Q5), wherein the positive DC bus (B1) is connected via the first switch transistor (Q4) to one end of the secondary winding, and the other end of the secondary winding is connected via the second switch transistor (Q5) to the negative DC bus (B2). The online uninterruptible power supply reduces costs and enhances half-wave load capability.

Description

在线式不间断电源Online uninterruptible power supply 技术领域Technical field
本发明涉及不间断电源，特别涉及在线式不间断电源。This invention relates to uninterruptible power supplies, and more particularly to an online uninterruptible power supply.
背景技术Background technique
在线式不间断电源能够持续不断地给负载进行供电，已经被广泛地用于各个领域。The online uninterruptible power supply continuously supplies power to the load and has been widely used in various fields.
图1是现有技术中的一种在线式不间断电源的电路图。在线式不间断电源1包括在交流输入端10和交流输出端11之间依次连接的安全开关12、功率因数校正电路(PFC)13、半桥逆变器14和旁路开关17，其中PFC 13的输出端与半桥逆变器14的输入端相连接并作为直流母线，旁路开关17用于将半桥逆变器14的输出端和PFC 13的输入端之一连接至交流输出端11。在线式不间断电源1还包括依次连接的充电器15和推挽电路16，其中充电器15的输入端连接至交流输入端10，充电器15的输出端和推挽电路16的输入端都连接至可充电电池18的两端，推挽电路16的输出端连接至直流母线。1 is a circuit diagram of an in-circuit uninterruptible power supply in the prior art. The online uninterruptible power supply 1 includes a safety switch 12, a power factor correction circuit (PFC) 13, a half bridge inverter 14 and a bypass switch 17 which are sequentially connected between the AC input terminal 10 and the AC output terminal 11, wherein the PFC 13 The output is connected to the input of the half-bridge inverter 14 and serves as a DC bus. The bypass switch 17 is used to connect the output of the half-bridge inverter 14 and one of the inputs of the PFC 13 to the AC output 11 . The online uninterruptible power supply 1 further includes a charger 15 and a push-pull circuit 16 connected in series, wherein the input of the charger 15 is connected to the AC input terminal 10, and the output of the charger 15 is connected to the input terminal of the push-pull circuit 16. To both ends of the rechargeable battery 18, the output of the push-pull circuit 16 is connected to the DC bus.
图1的在线式不间断电源1有如下四种工作模式。The online uninterruptible power supply 1 of Fig. 1 has the following four modes of operation.
在线模式：控制安全开关12处于导通状态，控制旁路开关17使得半桥逆变器14的输出端连接至交流输出端11，控制PFC 13、半桥逆变器14和充电器15处于工作状态，交流输入端10的市电(交流电)通过安全开关12、PFC 13和半桥逆变器14对连接在交流输出端11的负载(图1未示出)进行供电，同时充电器15对其输出端的可充电电池18进行充电。Online mode: The control safety switch 12 is in an on state, and the bypass switch 17 is controlled such that the output of the half bridge inverter 14 is connected to the AC output terminal 11, and the control PFC 13, the half bridge inverter 14 and the charger 15 are in operation. State, the mains (alternating current) of the AC input terminal 10 supplies power to the load (not shown in FIG. 1) connected to the AC output terminal 11 through the safety switch 12, the PFC 13 and the half-bridge inverter 14, while the charger 15 pairs The rechargeable battery 18 at its output is charged.
电池模式：控制安全开关12处于断开状态，控制旁路开关17使得半桥逆变器14的输出端连接至交流输出端11，控制推挽电路16和半桥逆变器14处于工作状态，可充电电池18通过推挽电路16和半桥逆变器14对负载进行供电。Battery mode: The control safety switch 12 is in an off state, and the bypass switch 17 is controlled such that the output of the half bridge inverter 14 is connected to the AC output terminal 11, and the control push-pull circuit 16 and the half-bridge inverter 14 are in operation. The rechargeable battery 18 supplies power to the load through the push-pull circuit 16 and the half-bridge inverter 14.
经济运行模式(ECO)：控制安全开关12处于导通状态，控制旁路开关17使得PFC 13的输入端连接至交流输出端11，且控制PFC 13和充电器15处于工作状态。Economic Operation Mode (ECO): The control safety switch 12 is in an on state, and the bypass switch 17 is controlled such that the input of the PFC 13 is connected to the AC output terminal 11, and the PFC 13 and the charger 15 are controlled to be in an active state.
旁路模式：控制安全开关12处于导通状态，控制旁路开关17使得PFC13的输入端连接至交流输出端11，且控制充电器15处于工作状态。 Bypass mode: The control safety switch 12 is in an on state, and the bypass switch 17 is controlled such that the input of the PFC 13 is connected to the AC output terminal 11 and the control charger 15 is in an active state.
图1所示的在线式不间断电源1中的PFC 13、半桥逆变器14、充电器15和推挽电路16作为独立的电路模块在相应的工作模式下工作，因此在线式不间断电源1中的电子器件的利用率低，导致电子器件的数目较多、成本较高。The PFC 13, the half-bridge inverter 14, the charger 15, and the push-pull circuit 16 in the online uninterruptible power supply 1 shown in FIG. 1 operate as independent circuit modules in respective operating modes, so the online uninterruptible power supply The utilization rate of the electronic device in 1 is low, resulting in a large number of electronic devices and a high cost.
发明内容Summary of the invention
针对现有技术存在的上述技术问题，本发明的实施例提供了一种在线式不间断电源，包括：In an embodiment of the present invention, an embodiment of the present invention provides an online uninterruptible power supply, including:
功率因数校正电路和逆变器，所述功率因数校正电路的输出端与所述逆变器的输入端连接以形成正直流母线和负直流母线；a power factor correction circuit and an inverter, an output of the power factor correction circuit being coupled to an input of the inverter to form a positive DC bus and a negative DC bus;
推挽电路，其包括：Push-pull circuit, which includes:
正极输入端子和负极输入端子；a positive input terminal and a negative input terminal;
变压器，其包括初级绕组和次级绕组；以及a transformer comprising a primary winding and a secondary winding;
整流电路，所述整流电路的输入端连接至所述次级绕组，且输出端连接至所述正直流母线和负直流母线；a rectifier circuit, an input end of the rectifier circuit is connected to the secondary winding, and an output terminal is connected to the positive DC bus and the negative DC bus;
缠绕在所述变压器的初级侧的充电绕组，所述充电绕组的一端连接至所述初级绕组的一端；a charging winding wound on a primary side of the transformer, one end of the charging winding being connected to one end of the primary winding;
连接在所述推挽电路的负极输入端子和所述充电绕组的另一端之间的单向可控充电线路；以及a unidirectional controllable charging line connected between the negative input terminal of the push-pull circuit and the other end of the charging winding;
第一开关管和第二开关管，所述正直流母线通过所述第一开关管连接至所述次级绕组的一端，所述次级绕组的另一端通过第二开关管连接至所述负直流母线。a first switching transistor and a second switching transistor, wherein the positive DC bus is connected to one end of the secondary winding through the first switching transistor, and the other end of the secondary winding is connected to the negative through a second switching transistor DC bus.
优选的，所述单向可控充电线路包括串联的第一二极管和开关装置。Preferably, the unidirectional controllable charging line comprises a first diode and a switching device connected in series.
优选的，所述单向可控充电线路还包括与所述第一二极管和开关装置串联的第一电感。Advantageously, the unidirectionally controllable charging line further includes a first inductance in series with the first diode and the switching device.
优选的，所述在线式不间断电源还包括分别连接在所述整流电路的输出端的第二电感和第三电感。Preferably, the online uninterruptible power supply further includes a second inductor and a third inductor respectively connected to the output end of the rectifier circuit.
优选的，所述在线式不间断电源还包括与所述第一开关管串联的第二二极管，以及与所述第二开关管串联的第三二极管。Advantageously, the in-line uninterruptible power supply further includes a second diode in series with the first switching transistor and a third diode in series with the second switching transistor.
优选的，所述整流电路为全桥整流电路。Preferably, the rectifier circuit is a full bridge rectifier circuit.
优选的，所述在线式不间断电源还包括控制装置，其用于控制所述功率因数校正电路、逆变器、推挽电路、第一开关管、第二开关管和单向可 控充电线路的工作状态。Preferably, the online uninterruptible power supply further includes control means for controlling the power factor correction circuit, the inverter, the push-pull circuit, the first switch tube, the second switch tube, and the one-way Control the working state of the charging line.
优选的，在在线模式下，所述控制装置用于控制所述功率因数校正电路和逆变器工作，且控制所述单向可控充电线路导通，以及Preferably, in the online mode, the control device is configured to control the power factor correction circuit and the inverter to operate, and control the one-way controllable charging line to be turned on, and
在市电的正半周期内，控制所述第一开关管以脉宽调制方式工作、且控制所述第二开关管截止；Controlling the first switch tube to operate in a pulse width modulation mode and controlling the second switch tube to be turned off during a positive half cycle of the mains;
在市电的负半周期内，控制所述第一开关管截止、且控制所述第二开关管以脉宽调制方式工作。During the negative half cycle of the mains, the first switch is controlled to be turned off, and the second switch is controlled to operate in a pulse width modulation manner.
优选的，在在线模式下，所述控制装置用于控制所述功率因数校正电路和逆变器工作，以及Preferably, in the online mode, the control device is configured to control the power factor correction circuit and the inverter to operate, and
当所述正直流母线上的电压与所述负直流母线上的电压的差值大于预定的第一阈值或所述正直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管以脉宽调制方式工作、且控制所述第二开关管截止；Controlling the difference when the difference between the voltage on the positive DC bus and the voltage on the negative DC bus is greater than a predetermined first threshold or the voltage on the positive DC bus is greater than a bus voltage protection threshold a switch tube operates in a pulse width modulation mode, and controls the second switch tube to be turned off;
当所述负直流母线上的电压与所述正直流母线上的电压的差值大于预定的第二阈值或所述负直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管截止、且控制所述第二开关管以脉宽调制方式工作。Controlling the difference when the difference between the voltage on the negative DC bus and the voltage on the positive DC bus is greater than a predetermined second threshold or the voltage on the negative DC bus is greater than the bus voltage protection threshold A switch tube is turned off, and the second switch tube is controlled to operate in a pulse width modulation mode.
优选的，在电池模式下，所述控制装置用于控制所述逆变器工作，且控制所述单向可控充电线路断开，以及Preferably, in the battery mode, the control device is configured to control the operation of the inverter, and control the disconnection of the one-way controllable charging line, and
当所述正直流母线上的电压与所述负直流母线上的电压的差值不大于预定的第一阈值、且所述正直流母线上的电压不大于母线电压过高保护阀值时，控制所述推挽电路工作、且控制所述第一开关管和第二开关管截止；Controlling when a difference between a voltage on the positive DC bus and a voltage on the negative DC bus is not greater than a predetermined first threshold, and a voltage on the positive DC bus is not greater than a protection threshold of a bus voltage The push-pull circuit operates, and controls the first switch tube and the second switch tube to be turned off;
当所述正直流母线上的电压与所述负直流母线上的电压的差值大于预定的第一阈值或所述正直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管以脉宽调制方式工作、且控制所述第二开关管及所述推挽电路中的开关管截止；Controlling the difference when the difference between the voltage on the positive DC bus and the voltage on the negative DC bus is greater than a predetermined first threshold or the voltage on the positive DC bus is greater than a bus voltage protection threshold a switch tube operates in a pulse width modulation mode, and controls the second switch tube and the switch tube in the push-pull circuit to be turned off;
当所述负直流母线上的电压与所述正直流母线上的电压的差值不大于预定的第二阈值、且所述负直流母线上的电压不大于母线电压过高保护阀值时，控制所述推挽电路工作、且控制所述第一开关管和第二开关管截止；Controlling when a difference between a voltage on the negative DC bus and a voltage on the positive DC bus is not greater than a predetermined second threshold, and a voltage on the negative DC bus is not greater than a protection threshold of a bus voltage The push-pull circuit operates, and controls the first switch tube and the second switch tube to be turned off;
当所述负直流母线上的电压与所述正直流母线上的电压的差值大于 预定的第二阈值或所述负直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管及所述推挽电路中的开关管截止、且控制所述第二开关管以脉宽调制方式工作。When the difference between the voltage on the negative DC bus and the voltage on the positive DC bus is greater than Controlling the first switch tube and the switch tube in the push-pull circuit to be turned off and controlling the second switch when the predetermined second threshold or the voltage on the negative DC bus is greater than the bus voltage over-high protection threshold The tube works in pulse width modulation mode.
本发明的在线式不间断电源显著地降低了成本，改善了充电时的输入总谐波电流畸变率(THDI)，并提高了带半波负载能力。The online uninterruptible power supply of the present invention significantly reduces the cost, improves the input total harmonic current distortion rate (THDI) during charging, and improves the half-wave load capability.
附图说明DRAWINGS
以下参照附图对本发明实施例作进一步说明，其中：The embodiments of the present invention are further described below with reference to the accompanying drawings, wherein:
图1是现有技术中的一种在线式不间断电源的电路图。1 is a circuit diagram of an in-circuit uninterruptible power supply in the prior art.
图2是根据本发明第一个实施例的在线式不间断电源的电路图。2 is a circuit diagram of an in-line uninterruptible power supply in accordance with a first embodiment of the present invention.
图3是图2所示的在线式不间断电源在在线模式下的等效电路图。3 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in an online mode.
图4是图2所示的在线式不间断电源在电池模式下的等效电路图。4 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in a battery mode.
图5是根据本发明第二个实施例的在线式不间断电源的电路图。Figure 5 is a circuit diagram of an in-line uninterruptible power supply in accordance with a second embodiment of the present invention.
图6是根据本发明第三个实施例的在线式不间断电源的电路图。Figure 6 is a circuit diagram of an in-line uninterruptible power supply in accordance with a third embodiment of the present invention.
具体实施方式detailed description
为了使本发明的目的、技术方案及优点更加清楚明白，以下结合附图通过具体实施例对本发明进一步详细说明。The present invention will be further described in detail below with reference to the accompanying drawings.
图2是根据本发明第一个实施例的在线式不间断电源的电路图。在线式不间断电源2与图1所示的在线式不间断电源1基本相同，因此其相同或者类似的部件其标号也相互对应，区别在于，在线式不间断电源2不具有价格昂贵的充电器15。在线式不间断电源2还包括缠绕在推挽电路26中的变压器TX的初级侧的充电绕组W1，连接在可充电电池28的负极(即推挽电路26的负极输入端子)和充电绕组W1之间的单向可控充电线路29，连接在正直流母线B1和变压器TX的次级绕组的一端之间的开关管Q4，以及连接在变压器TX的次级绕组的另一端和负直流母线B2之间的开关管Q5。2 is a circuit diagram of an in-line uninterruptible power supply in accordance with a first embodiment of the present invention. The online uninterruptible power supply 2 is basically the same as the online uninterruptible power supply 1 shown in FIG. 1, so that the same or similar components have the same reference numerals, except that the online uninterruptible power supply 2 does not have an expensive charger. 15. The online uninterruptible power supply 2 further includes a charging winding W1 on the primary side of the transformer TX wound in the push-pull circuit 26, connected to the negative pole of the rechargeable battery 28 (i.e., the negative input terminal of the push-pull circuit 26) and the charging winding W1. a one-way controllable charging line 29, a switching tube Q4 connected between the positive DC bus B1 and one end of the secondary winding of the transformer TX, and the other end of the secondary winding connected to the transformer TX and the negative DC bus B2 Switch tube Q5.
在线式不间断电源2还包括控制装置200，其用于控制功率因数校正电路23、半桥逆变器24、推挽电路26、开关管Q4、开关管Q5和单向可控充电线路29的工作状态。The online uninterruptible power supply 2 further includes a control device 200 for controlling the power factor correction circuit 23, the half bridge inverter 24, the push-pull circuit 26, the switching transistor Q4, the switching transistor Q5, and the one-way controllable charging line 29. Working status.
以下将结合在线式不间断电源2的工作模式来说明其优点。The advantages of the online uninterruptible power supply 2 will be described below in connection with the operation mode of the online uninterruptible power supply 2.
图3是图2所示的在线式不间断电源在在线模式下的等效电路图。安 全开关22处于导通状态、半桥逆变器24的输出端通过旁路开关27连接至交流输出端21，且控制装置200控制PFC 23和半桥逆变器24处于工作状态，因此交流输入端20的市电(即交流电)通过安全开关22、PFC 23和半桥逆变器24对连接在交流输出端21的负载(图3未示出)进行供电。3 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in an online mode. Ann The full switch 22 is in an on state, the output of the half bridge inverter 24 is connected to the AC output terminal 21 via the bypass switch 27, and the control device 200 controls the PFC 23 and the half bridge inverter 24 to be in operation, thus the AC input The mains (i.e., alternating current) of the terminal 20 supplies power to a load (not shown in Fig. 3) connected to the alternating current output terminal 21 via the safety switch 22, the PFC 23, and the half bridge inverter 24.
如图3所示，变压器TX的初级绕组具有与可充电电池28的正极(即推挽电路26的正极输入端子)连接的抽头T5，且次级绕组具有端子T1、T3和连接至中性线N的抽头T2。全桥整流电路261的输入端连接至变压器TX的次级绕组两端，其正极输出端子2611(连接至正直流母线B1)通过开关管Q4连接至变压器TX的端子T1，且变压器TX的端子T3通过开关管Q5连接至其负极输出端子2612(连接至负直流母线B2)。可充电电池28的负极(即推挽电路26的负极输入端子)通过单向可控充电线路29连接至充电绕组W1。在在线模式下，开关管Q4、开关管Q5、充电绕组W1、单向可控充电线路29、变压器TX的一部分和全桥整流电路261构成了对可充电电池28进行充电的充电器25。下面详细描述充电器25的工作方式。As shown in FIG. 3, the primary winding of the transformer TX has a tap T5 connected to the anode of the rechargeable battery 28 (ie, the positive input terminal of the push-pull circuit 26), and the secondary winding has terminals T1, T3 and is connected to the neutral line. N tap T2. The input end of the full bridge rectifier circuit 261 is connected to both ends of the secondary winding of the transformer TX, and its positive output terminal 2611 (connected to the positive DC bus B1) is connected to the terminal T1 of the transformer TX through the switch Q4, and the terminal T3 of the transformer TX It is connected to its negative output terminal 2612 (connected to the negative DC bus B2) through the switching transistor Q5. The negative electrode of the rechargeable battery 28 (i.e., the negative input terminal of the push-pull circuit 26) is connected to the charging winding W1 through a one-way controllable charging line 29. In the online mode, the switching transistor Q4, the switching transistor Q5, the charging winding W1, the unidirectional controllable charging line 29, a portion of the transformer TX, and the full bridge rectifier circuit 261 constitute a charger 25 for charging the rechargeable battery 28. The mode of operation of the charger 25 is described in detail below.
在交流输入端20的市电的正半周期内，控制装置200控制单向可控充电线路29导通、开关管Q5截止，并控制开关管Q4以脉宽调制方式工作(即给开关管Q4提供脉宽调制信号使其高频导通和截止)。当开关管Q4导通时，变压器TX的端子T1和抽头T2之间的绕组作为励磁电感，形成的励磁回路如下：正直流母线B1、开关管Q4、变压器TX的端子T1、抽头T2到中性线N。此时形成的电池充电回路如下：变压器TX的抽头T5、可充电电池28的正极和负极、二极管D6、开关装置RY3、充电绕组W1、变压器TX的端子T6到变压器TX的抽头T5。从而使得连接在正直流母线B1和中性线N之间的电容C1放电并对可充电电池28进行充电。当开关管Q4截止、且电容C1的电压低于电容C5的电压时，变压器TX的抽头T2和端子T3之间的绕组作为退磁电感，形成的退磁回路如下：中性线N、变压器TX的抽头T2、端子T3、二极管D5到正直流母线B1。当开关管Q4截止、且电容C1的电压高于电容C5的电压时，变压器TX的端子T1和抽头T2之间的绕组作为退磁电感，形成的退磁回路如下：负直流母线B2、二极管D8、变压器TX的端子T1、抽头T2到中性线N。During the positive half cycle of the mains supply of the AC input terminal 20, the control device 200 controls the one-way controllable charging line 29 to be turned on, the switch tube Q5 to be turned off, and the switch tube Q4 to operate in a pulse width modulation mode (ie, to the switch tube Q4) A pulse width modulated signal is provided to cause its high frequency to be turned on and off). When the switch tube Q4 is turned on, the winding between the terminal T1 of the transformer TX and the tap T2 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the positive DC bus B1, the switch Q4, the terminal T1 of the transformer TX, and the tap T2 to neutral Line N. The battery charging circuit formed at this time is as follows: the tap T5 of the transformer TX, the positive and negative electrodes of the rechargeable battery 28, the diode D6, the switching device RY3, the charging winding W1, the terminal T6 of the transformer TX, and the tap T5 of the transformer TX. Thereby, the capacitor C1 connected between the positive DC bus B1 and the neutral line N is discharged and the rechargeable battery 28 is charged. When the switch Q4 is turned off and the voltage of the capacitor C1 is lower than the voltage of the capacitor C5, the winding between the tap T2 of the transformer TX and the terminal T3 acts as a demagnetization inductance, and the demagnetization loop formed is as follows: neutral line N, tap of the transformer TX T2, terminal T3, diode D5 to positive DC bus B1. When the switch Q4 is turned off and the voltage of the capacitor C1 is higher than the voltage of the capacitor C5, the winding between the terminal T1 of the transformer TX and the tap T2 acts as a demagnetization inductance, and the demagnetization circuit is formed as follows: a negative DC bus B2, a diode D8, a transformer Terminal T1 of TX, tap T2 to neutral line N.
在交流输入端20的市电的负半周期内，控制装置200控制单向可控充电线路29导通、开关管Q4截止，并控制开关管Q5以脉宽调制方式工 作。当开关管Q5导通时，变压器TX的抽头T2和端子T3之间的绕组作为励磁电感，形成的励磁回路如下：中性线N、变压器TX的抽头T2、端子T3、开关管Q5到负直流母线B2。此时形成相同的电池充电回路，从而使得连接在中性线N和负直流母线B2之间的电容C5放电并对可充电电池28进行充电。当开关管Q5截止、且电容C1的电压高于电容C5的电压时，变压器TX的端子T1和抽头T2之间的绕组作为退磁电感，形成的退磁回路如下：负直流母线B2、二极管D8、变压器TX的端子T1、抽头T2到中性线N。当开关管Q5截止、且电容C1的电压低于电容C5的电压时，变压器TX的抽头T2和端子T3之间的绕组作为退磁电感，形成的退磁回路如下：中性线N、变压器TX的抽头T2、端子T3、二极管D5到正直流母线B1。During the negative half cycle of the mains supply of the AC input terminal 20, the control device 200 controls the one-way controllable charging line 29 to be turned on, the switch tube Q4 to be turned off, and the switch tube Q5 to be controlled in a pulse width modulation manner. Work. When the switch tube Q5 is turned on, the winding between the tap T2 of the transformer TX and the terminal T3 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, the switch tube Q5 to the negative direct current Bus B2. At this time, the same battery charging circuit is formed, so that the capacitor C5 connected between the neutral line N and the negative DC bus B2 is discharged and the rechargeable battery 28 is charged. When the switch Q5 is turned off and the voltage of the capacitor C1 is higher than the voltage of the capacitor C5, the winding between the terminal T1 of the transformer TX and the tap T2 acts as a demagnetization inductance, and the demagnetization circuit is formed as follows: a negative DC bus B2, a diode D8, a transformer Terminal T1 of TX, tap T2 to neutral line N. When the switch tube Q5 is turned off and the voltage of the capacitor C1 is lower than the voltage of the capacitor C5, the winding between the tap T2 of the transformer TX and the terminal T3 acts as a demagnetization inductance, and the demagnetization loop formed is as follows: neutral line N, tap of the transformer TX T2, terminal T3, diode D5 to positive DC bus B1.
在半桥逆变器正负半周交替工作的过程中，半桥架构存在如下问题，当输出为正半周时，半桥逆变器24中的电感中多余的能量会回馈到电容C5上；当输出为负半周时，半桥逆变器24中的电感中多余的能量会回馈到电容C1上。如果在线式不间断电源2带半波负载，半桥逆变器24的电感回馈的能量将导致正直流母线B1或负直流母线B2上的电压一直升高，导致机器母线过压保护，其带半波负载能力很低。在本实施例的在线式不间断电源2中，还可以通过如下控制方式提高其带半波负载能力。In the process of alternating half-cycle operation of the half-bridge inverter, the half-bridge architecture has the following problems. When the output is positive half-cycle, the excess energy in the inductance of the half-bridge inverter 24 is fed back to the capacitor C5; When the output is negative half cycle, the excess energy in the inductance in the half bridge inverter 24 is fed back to the capacitor C1. If the online uninterruptible power supply 2 has a half-wave load, the energy fed back by the inductance of the half-bridge inverter 24 will cause the voltage on the positive DC bus B1 or the negative DC bus B2 to rise all the time, resulting in overvoltage protection of the machine bus. The half-wave load capacity is very low. In the online uninterruptible power supply 2 of the present embodiment, the half-wave load capacity can also be improved by the following control method.
第一种情况：电容C1上的电压与电容C5上的电压的差值大于预定的第一阈值或电容C1上的电压大于母线电压过高保护阀值。控制装置200控制开关管Q5截止，并控制开关管Q4以脉宽调制方式工作。当控制开关管Q4导通时，变压器TX的端子T1和抽头T2之间的绕组作为励磁电感，形成的励磁回路如下：正直流母线B1、开关管Q4、变压器TX的端子T1、抽头T2到中性线N。此时形成的负直流母线充电回路如下：负直流母线B2、二极管D7、变压器TX的端子T3、抽头T2到中性线N；如果开关装置RY3此时处于导通状态，将形成相同的电池充电回路。当控制开关管Q4截止时，其形成的退磁回路如下：负直流母线B2、二极管D8、变压器TX的端子T1、抽头T2到中性线N。通过上述分析可知，在电容C1放电过程中，实现了对可充电电池28和电容C5进行充电，因此减小电容C1和电容C5上的电压差值，提高带半波负载能力。In the first case, the difference between the voltage on the capacitor C1 and the voltage on the capacitor C5 is greater than a predetermined first threshold or the voltage on the capacitor C1 is greater than the bus voltage over-high protection threshold. The control device 200 controls the switching transistor Q5 to be turned off, and controls the switching transistor Q4 to operate in a pulse width modulation mode. When the control switch Q4 is turned on, the winding between the terminal T1 of the transformer TX and the tap T2 acts as the exciting inductance, and the excitation circuit is formed as follows: the positive DC bus B1, the switch Q4, the terminal T1 of the transformer TX, and the tap T2 to the middle Sex line N. The negative DC bus charging circuit formed at this time is as follows: negative DC bus B2, diode D7, terminal T3 of the transformer TX, tap T2 to the neutral line N; if the switching device RY3 is in the on state at this time, the same battery charging will be formed. Loop. When the control switch Q4 is turned off, the demagnetization circuit formed by it is as follows: a negative DC bus B2, a diode D8, a terminal T1 of the transformer TX, and a tap T2 to the neutral line N. It can be seen from the above analysis that during the discharge of the capacitor C1, the rechargeable battery 28 and the capacitor C5 are charged, thereby reducing the voltage difference between the capacitor C1 and the capacitor C5, and improving the half-wave load capability.
第二种情况：电容C5上的电压与电容C1上的电压的差值大于预定的第二阈值或电容C5上的电压大于母线电压过高保护阀值。控制装置200 控制开关管Q4截止，并控制开关管Q5以脉宽调制方式工作。当控制开关管Q5导通时，变压器TX的抽头T2和端子T3之间的绕组作为励磁电感，形成的励磁回路如下：中性线N、变压器TX的抽头T2、端子T3、开关管Q5到负直流母线B2。此时形成的正直流母线充电回路如下：中性线N、变压器TX的抽头T2、端子T1、二极管D4到正直流母线B1；如果开关装置RY3此时处于导通状态，将形成相同的电池充电回路。当控制开关管Q5截止时，其形成的退磁回路如下：中性线N、变压器TX的抽头T2、端子T3、二极管D5到正直流母线B1。通过上述分析可知，在电容C5放电过程中，实现了对可充电电池28和电容C1进行充电，因此减小电容C1和电容C5上的电压差值，提高带半波负载能力。In the second case, the difference between the voltage on the capacitor C5 and the voltage on the capacitor C1 is greater than a predetermined second threshold or the voltage on the capacitor C5 is greater than the bus voltage over-high protection threshold. Control device 200 The control switch Q4 is turned off, and the switch tube Q5 is controlled to operate in a pulse width modulation mode. When the control switch tube Q5 is turned on, the winding between the tap T2 of the transformer TX and the terminal T3 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the switch tube Q5 to the negative DC bus B2. The positive DC bus charging circuit formed at this time is as follows: neutral line N, tap T2 of the transformer TX, terminal T1, diode D4 to the positive DC bus B1; if the switching device RY3 is in the on state at this time, the same battery charging will be formed. Loop. When the control switch Q5 is turned off, the demagnetization circuit formed by it is as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the diode D5 to the positive DC bus B1. Through the above analysis, it is known that during the discharge of the capacitor C5, the rechargeable battery 28 and the capacitor C1 are charged, thereby reducing the voltage difference between the capacitor C1 and the capacitor C5, and improving the half-wave load capability.
本领域的技术人员可以根据在线式不间断电源的型号、规格及其中的电容C1、C5的规格，来设定合适的第一阈值、第二阈值以及母线电压过高保护阀值。因此本发明并不限于预定的第一阈值、预定的第二阈值以及母线电压过高保护阀值的具体范围。Those skilled in the art can set appropriate first threshold, second threshold, and bus voltage over-protection threshold according to the type and specification of the online uninterruptible power supply and the specifications of the capacitors C1 and C5 therein. The invention is therefore not limited to a predetermined first threshold, a predetermined second threshold, and a specific range of bus voltage over-high protection thresholds.
在在线模式下，充电器25重复利用了推挽电路26中的全桥整流电路261和变压器TX对可充电电池28进行充电，由于对可充电电池28的充电过程可控，因此充电过程中能够改善总谐波电流畸变率和提高功率因数。与图1所示的在线式不间断电源1相比，无需额外使用价格昂贵的变压器，显著地降低了成本。另外，本发明的在线式不间断电源2还能够使得正负直流母线B1、B2上的电压保持基本平衡，提高带半波负载能力。In the online mode, the charger 25 repeatedly utilizes the full bridge rectifier circuit 261 and the transformer TX in the push-pull circuit 26 to charge the rechargeable battery 28, and since the charging process of the rechargeable battery 28 is controllable, the charging process can Improve total harmonic current distortion rate and improve power factor. Compared with the online uninterruptible power supply 1 shown in Fig. 1, there is no need to additionally use an expensive transformer, which significantly reduces the cost. In addition, the online uninterruptible power supply 2 of the present invention can also maintain a substantially balanced voltage across the positive and negative DC busses B1, B2, improving the half-wave load capability.
图4是图2所示的在线式不间断电源在电池模式下的等效电路图。安全开关22和开关装置RY3处于断开状态，半桥逆变器24的输出端通过旁路开关27连接至交流输出端21，控制装置200控制开关管Q4和Q5截止，且控制推挽电路26和半桥逆变器24处于工作状态，可充电电池28通过推挽电路26和半桥逆变器24对负载进行供电。4 is an equivalent circuit diagram of the online uninterruptible power supply shown in FIG. 2 in a battery mode. The safety switch 22 and the switching device RY3 are in an off state, the output of the half bridge inverter 24 is connected to the AC output terminal 21 through the bypass switch 27, and the control device 200 controls the switching transistors Q4 and Q5 to be turned off, and controls the push-pull circuit 26 The half-bridge inverter 24 is in operation and the rechargeable battery 28 supplies power to the load via the push-pull circuit 26 and the half-bridge inverter 24.
在线式不间断电源2在电池模式与市电模式一样，也存在带半波负载能力很低的问题。本实施例的在线式不间断电源2可以通过如下控制方式提高其带半波负载能力。The online uninterruptible power supply 2 has the same problem as the half-wave load capability in the battery mode as in the mains mode. The online uninterruptible power supply 2 of the present embodiment can be improved in its half-wave load capability by the following control method.
第一种情况：电容C1上的电压与电容C5上的电压的差值大于预定的第一阈值或电容C1上的电压大于母线电压过高保护阀值。控制装置200控制开关管Q5及推挽电路26中的开关管截止，并控制开关管Q4以脉宽调制方式工作。当控制开关管Q4导通时，变压器TX的端子T1和抽头 T2之间的绕组作为励磁电感，形成的励磁回路如下：正直流母线B1、开关管Q4、变压器TX的端子T1、抽头T2到中性线N。此时形成的负直流母线充电回路如下：负直流母线B2、二极管D7、变压器TX的端子T3、抽头T2到中性线N。当控制开关管Q4截止时，其形成的退磁回路如下：负直流母线B2、二极管D8、变压器TX的端子T1、抽头T2到中性线N。通过上述分析可知，通过控制电容C1放电并对电容C5进行充电，因此减小电容C1和电容C5上的电压差值，提高带半波负载能力。In the first case, the difference between the voltage on the capacitor C1 and the voltage on the capacitor C5 is greater than a predetermined first threshold or the voltage on the capacitor C1 is greater than the bus voltage over-high protection threshold. The control device 200 controls the switching transistors in the switching transistor Q5 and the push-pull circuit 26 to be turned off, and controls the switching transistor Q4 to operate in a pulse width modulation manner. When the control switch Q4 is turned on, the terminal T1 and the tap of the transformer TX The winding between T2 acts as a magnetizing inductance, and the resulting excitation circuit is as follows: positive DC bus B1, switching transistor Q4, terminal T1 of transformer TX, tap T2 to neutral line N. The negative DC bus charging circuit formed at this time is as follows: negative DC bus B2, diode D7, terminal T3 of transformer TX, and tap T2 to neutral line N. When the control switch Q4 is turned off, the demagnetization circuit formed by it is as follows: a negative DC bus B2, a diode D8, a terminal T1 of the transformer TX, and a tap T2 to the neutral line N. It can be seen from the above analysis that the capacitor C5 is discharged by the control capacitor C1, thereby reducing the voltage difference between the capacitor C1 and the capacitor C5, and improving the half-wave load capability.
其中，当电容C1上的电压与电容C5上的电压的差值不大于预定的第一阈值、且电容C1上的电压不大于母线电压过高保护阀值时，控制装置200控制开关管Q4、Q5截止，且控制推挽电路26工作，从而使得可充电电池28再次通过推挽电路26和半桥逆变器24对负载进行供电。Wherein, when the difference between the voltage on the capacitor C1 and the voltage on the capacitor C5 is not greater than a predetermined first threshold, and the voltage on the capacitor C1 is not greater than the bus voltage over-high protection threshold, the control device 200 controls the switch Q4, Q5 is turned off and the push-pull circuit 26 is controlled to operate so that the rechargeable battery 28 supplies power to the load again through the push-pull circuit 26 and the half-bridge inverter 24.
第二种情况：电容C5上的电压与电容C1上的电压的差值大于预定的第二阈值或电容C5上的电压大于母线电压过高保护阀值。控制装置200控制开关管Q4及推挽电路26中的开关管截止，并控制开关管Q5以脉宽调制方式工作。当控制开关管Q5导通时，变压器TX的抽头T2和端子T3之间的绕组作为励磁电感，形成的励磁回路如下：中性线N、变压器TX的抽头T2、端子T3、开关管Q5到负直流母线B2。此时形成的正直流母线充电回路如下：中性线N、变压器TX的抽头T2、端子T1、二极管D4到正直流母线B1。当控制开关管Q5截止时，其形成的退磁回路如下：中性线N、变压器TX的抽头T2、端子T3、二极管D5到正直流母线B1。通过上述分析可知，通过控制电容C5放电并对电容C1进行充电，因此减小电容C1和电容C5上的电压差值，提高带半波负载能力。In the second case, the difference between the voltage on the capacitor C5 and the voltage on the capacitor C1 is greater than a predetermined second threshold or the voltage on the capacitor C5 is greater than the bus voltage over-high protection threshold. The control device 200 controls the switching transistors in the switching transistor Q4 and the push-pull circuit 26 to be turned off, and controls the switching transistor Q5 to operate in a pulse width modulation manner. When the control switch tube Q5 is turned on, the winding between the tap T2 of the transformer TX and the terminal T3 acts as the magnetizing inductance, and the excitation circuit is formed as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the switch tube Q5 to the negative DC bus B2. The positive DC bus charging circuit formed at this time is as follows: neutral line N, tap T2 of the transformer TX, terminal T1, diode D4 to the positive DC bus B1. When the control switch Q5 is turned off, the demagnetization circuit formed by it is as follows: the neutral line N, the tap T2 of the transformer TX, the terminal T3, and the diode D5 to the positive DC bus B1. It can be seen from the above analysis that the capacitor C1 is discharged by the control capacitor C5, thereby reducing the voltage difference between the capacitor C1 and the capacitor C5, and improving the half-wave load capability.
其中，当电容C5上的电压与电容C1上的电压的差值不大于预定的第二阈值、且电容C5上的电压不大于母线电压过高保护阀值时，控制装置200控制开关管Q4、Q5截止，且控制推挽电路26工作，从而使得可充电电池28再次通过推挽电路26和半桥逆变器24对负载进行供电。Wherein, when the difference between the voltage on the capacitor C5 and the voltage on the capacitor C1 is not greater than a predetermined second threshold, and the voltage on the capacitor C5 is not greater than the bus voltage over-high protection threshold, the control device 200 controls the switch Q4, Q5 is turned off and the push-pull circuit 26 is controlled to operate so that the rechargeable battery 28 supplies power to the load again through the push-pull circuit 26 and the half-bridge inverter 24.
本发明的在线式不间断电源2在电池模式下能够使得正负直流母线B1、B2上的电压保持基本平衡，提高带半波负载能力，无需额外增加元器件，显著地降低了成本。The on-line uninterruptible power supply 2 of the present invention can maintain the basic balance of the voltages on the positive and negative DC buses B1 and B2 in the battery mode, and improve the half-wave load capability without additional components, which significantly reduces the cost.
在线式不间断电源2的经济运行模式：安全开关22和开关装置RY3处于导通状态，控制旁路开关27使得PFC 23的输入端连接至交流输出端21，控制PFC 23和充电器25工作以对可充电电池28进行充电。 Economic operation mode of the online uninterruptible power supply 2: the safety switch 22 and the switching device RY3 are in an on state, and the bypass switch 27 is controlled such that the input end of the PFC 23 is connected to the AC output terminal 21, and the PFC 23 and the charger 25 are controlled to operate. The rechargeable battery 28 is charged.
在线式不间断电源2的旁路模式：安全开关22和开关装置RY3处于导通状态，控制旁路开关27使得PFC 23的输入端连接至交流输出端21，控制充电器25工作以对可充电电池28进行充电。Bypass mode of the online uninterruptible power supply 2: the safety switch 22 and the switching device RY3 are in an on state, and the bypass switch 27 is controlled such that the input end of the PFC 23 is connected to the AC output terminal 21, and the charger 25 is controlled to operate to be rechargeable. The battery 28 is charged.
图5是根据本发明第二个实施例的在线式不间断电源3的电路图。其与图2基本相同，图5中的附图标记30、31、32、33、34、36、37、38和300表示的部件与图2中相对应的附图标记表示的部件相同，区别在于，单向可控充电线路39还包括与二极管D36串联的电感L5。在对可充电电池38进行充电过程中，电感L5对充电电流起到限流作用，同时降低充电纹波电流，避免对可充电电池38造成损坏。Figure 5 is a circuit diagram of an in-line uninterruptible power supply 3 in accordance with a second embodiment of the present invention. It is substantially the same as FIG. 2, and the components denoted by reference numerals 30, 31, 32, 33, 34, 36, 37, 38, and 300 in FIG. 5 are the same as the components indicated by the corresponding reference numerals in FIG. The unidirectionally controllable charging line 39 also includes an inductance L5 in series with the diode D36. During charging of the rechargeable battery 38, the inductor L5 acts to limit the charging current while reducing the charging ripple current to avoid damage to the rechargeable battery 38.
图6是根据本发明第三个实施例的在线式不间断电源4的电路图。其与图5基本相同，图6中的附图标记40、41、42、33、44、46、47、48、49和400表示的部件与图5中相对应的附图标记表示的部件相同，区别在于，在线式不间断电源4还包括与开关管Q44串联的二极管D3、与开关管Q45串联的二极管D9、连接在全桥整流电路的正极输出端子4611的电感L4、以及连接在全桥整流电路的负极输出端子4612的电感L6。在电池模式下，二极管D3、D9可以阻止变压器次级绕组中的电流流经开关管Q44、Q45，使得电感L4、L6能够对变压器的次级绕组中的电流进行滤波，减小输出电流的纹波。Figure 6 is a circuit diagram of an in-line uninterruptible power supply 4 in accordance with a third embodiment of the present invention. It is substantially the same as FIG. 5, and the components denoted by reference numerals 40, 41, 42, 33, 44, 46, 47, 48, 49, and 400 in FIG. 6 are the same as those shown by the corresponding reference numerals in FIG. 5. The difference is that the online uninterruptible power supply 4 further includes a diode D3 connected in series with the switching transistor Q44, a diode D9 connected in series with the switching transistor Q45, an inductance L4 connected to the positive output terminal 4611 of the full bridge rectifier circuit, and a connection at the full bridge. The inductance L6 of the negative output terminal 4612 of the rectifier circuit. In battery mode, diodes D3 and D9 prevent current in the secondary winding of the transformer from flowing through switches Q44 and Q45, allowing inductors L4 and L6 to filter the current in the secondary winding of the transformer, reducing the ripple of the output current. wave.
在本发明的其他实施例中，可以采用单颗单向可控导通器件(例如单向开关管)替换上述实施例中的串联的二极管D6和开关装置RY3。In other embodiments of the present invention, a series of unidirectional controllable conduction devices (e.g., unidirectional switching transistors) may be used in place of the series connected diode D6 and switching device RY3 in the above embodiments.
在本发明的其他实施例中，可采用现有技术中的任一功率因数校正电路代替上述实施例中的功率因数校正电路23、33、43。In other embodiments of the present invention, any power factor correction circuit of the prior art may be employed instead of the power factor correction circuits 23, 33, 43 of the above embodiment.
在本发明的其他实施例中，可采用现有技术中的任一逆变器(例如全桥逆变器)代替上述实施例中的半桥逆变器24、34、44。In other embodiments of the present invention, any of the prior art inverters (e.g., full bridge inverters) may be employed in place of the half bridge inverters 24, 34, 44 of the above embodiments.
虽然本发明已经通过优选实施例进行了描述，然而本发明并非局限于这里所描述的实施例，在不脱离本发明范围的情况下还包括所作出的各种改变以及变化。 While the present invention has been described in its preferred embodiments, the invention is not limited to the embodiments described herein, and various changes and modifications may be made without departing from the scope of the invention.

Claims (10)

  1. 一种在线式不间断电源，其特征在于，包括：An online uninterruptible power supply, comprising:
    功率因数校正电路和逆变器，所述功率因数校正电路的输出端与所述逆变器的输入端连接以形成正直流母线和负直流母线；a power factor correction circuit and an inverter, an output of the power factor correction circuit being coupled to an input of the inverter to form a positive DC bus and a negative DC bus;
    推挽电路，其包括：Push-pull circuit, which includes:
    正极输入端子和负极输入端子；a positive input terminal and a negative input terminal;
    变压器，其包括初级绕组和次级绕组；以及a transformer comprising a primary winding and a secondary winding;
    整流电路，所述整流电路的输入端连接至所述次级绕组，且输出端连接至所述正直流母线和负直流母线；a rectifier circuit, an input end of the rectifier circuit is connected to the secondary winding, and an output terminal is connected to the positive DC bus and the negative DC bus;
    缠绕在所述变压器的初级侧的充电绕组，所述充电绕组的一端连接至所述初级绕组的一端；a charging winding wound on a primary side of the transformer, one end of the charging winding being connected to one end of the primary winding;
    连接在所述推挽电路的负极输入端子和所述充电绕组的另一端之间的单向可控充电线路；以及a unidirectional controllable charging line connected between the negative input terminal of the push-pull circuit and the other end of the charging winding;
    第一开关管和第二开关管，所述正直流母线通过所述第一开关管连接至所述次级绕组的一端，所述次级绕组的另一端通过第二开关管连接至所述负直流母线。a first switching transistor and a second switching transistor, wherein the positive DC bus is connected to one end of the secondary winding through the first switching transistor, and the other end of the secondary winding is connected to the negative through a second switching transistor DC bus.
  2. 根据权利要求1所述的在线式不间断电源，其特征在于，所述单向可控充电线路包括串联的第一二极管和开关装置。The online uninterruptible power supply of claim 1 wherein said unidirectionally controllable charging line comprises a first diode and a switching device in series.
  3. 根据权利要求2所述的在线不间断电源，其特征在于，所述单向可控充电线路还包括与所述第一二极管和开关装置串联的第一电感。The online uninterruptible power supply of claim 2 wherein said unidirectionally controllable charging line further comprises a first inductance in series with said first diode and said switching device.
  4. 根据权利要求1所述的在线式不间断电源，其特征在于，所述在线式不间断电源还包括分别连接在所述整流电路的输出端的第二电感和第三电感。The online uninterruptible power supply according to claim 1, wherein said online uninterruptible power supply further comprises a second inductance and a third inductance respectively connected to the output of said rectifier circuit.
  5. 根据权利要求4所述的在线式不间断电源，其特征在于，所述在线式不间断电源还包括与所述第一开关管串联的第二二极管，以及与所述第二开关管串联的第三二极管。The online uninterruptible power supply according to claim 4, wherein said online uninterruptible power supply further comprises a second diode in series with said first switching transistor, and in series with said second switching transistor The third diode.
  6. 根据权利要求1所述的在线式不间断电源，其特征在于，所述整流电路为全桥整流电路。The online uninterruptible power supply according to claim 1, wherein said rectifier circuit is a full bridge rectifier circuit.
  7. 根据权利要求1至6中任一项所述的在线式不间断电源，其特征在于，所述在线式不间断电源还包括控制装置，其用于控制所述功率因数校正电路、逆变器、推挽电路、第一开关管、第二开关管和单向可控充电 线路的工作状态。The online uninterruptible power supply according to any one of claims 1 to 6, wherein the online uninterruptible power supply further comprises control means for controlling the power factor correction circuit, the inverter, Push-pull circuit, first switch tube, second switch tube and one-way controllable charging The working state of the line.
  8. 根据权利要求7所述的在线式不间断电源，其特征在于，在在线模式下，所述控制装置用于控制所述功率因数校正电路和逆变器工作，且控制所述单向可控充电线路导通，以及The online uninterruptible power supply according to claim 7, wherein in the online mode, the control device is configured to control the power factor correction circuit and the inverter to operate, and control the one-way controllable charging Line conduction, and
    在市电的正半周期内，控制所述第一开关管以脉宽调制方式工作、且控制所述第二开关管截止；Controlling the first switch tube to operate in a pulse width modulation mode and controlling the second switch tube to be turned off during a positive half cycle of the mains;
    在市电的负半周期内，控制所述第一开关管截止、且控制所述第二开关管以脉宽调制方式工作。During the negative half cycle of the mains, the first switch is controlled to be turned off, and the second switch is controlled to operate in a pulse width modulation manner.
  9. 根据权利要求7所述的在线式不间断电源，其特征在于，在在线模式下，所述控制装置用于控制所述功率因数校正电路和逆变器工作，以及The online uninterruptible power supply according to claim 7, wherein in the online mode, said control means is for controlling said power factor correction circuit and said inverter to operate, and
    当所述正直流母线上的电压与所述负直流母线上的电压的差值大于预定的第一阈值或所述正直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管以脉宽调制方式工作、且控制所述第二开关管截止；Controlling the difference when the difference between the voltage on the positive DC bus and the voltage on the negative DC bus is greater than a predetermined first threshold or the voltage on the positive DC bus is greater than a bus voltage protection threshold a switch tube operates in a pulse width modulation mode, and controls the second switch tube to be turned off;
    当所述负直流母线上的电压与所述正直流母线上的电压的差值大于预定的第二阈值或所述负直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管截止、且控制所述第二开关管以脉宽调制方式工作。Controlling the difference when the difference between the voltage on the negative DC bus and the voltage on the positive DC bus is greater than a predetermined second threshold or the voltage on the negative DC bus is greater than the bus voltage protection threshold A switch tube is turned off, and the second switch tube is controlled to operate in a pulse width modulation mode.
  10. 根据权利要求7所述的在线式不间断电源，其特征在于，在电池模式下，所述控制装置用于控制所述逆变器工作，且控制所述单向可控充电线路断开，以及The online uninterruptible power supply according to claim 7, wherein in the battery mode, the control device is configured to control the operation of the inverter, and control the disconnection of the one-way controllable charging line, and
    当所述正直流母线上的电压与所述负直流母线上的电压的差值不大于预定的第一阈值、且所述正直流母线上的电压不大于母线电压过高保护阀值时，控制所述推挽电路工作、且控制所述第一开关管和第二开关管截止；Controlling when a difference between a voltage on the positive DC bus and a voltage on the negative DC bus is not greater than a predetermined first threshold, and a voltage on the positive DC bus is not greater than a protection threshold of a bus voltage The push-pull circuit operates, and controls the first switch tube and the second switch tube to be turned off;
    当所述正直流母线上的电压与所述负直流母线上的电压的差值大于预定的第一阈值或所述正直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管以脉宽调制方式工作、且控制所述第二开关管及所述推挽电路中的开关管截止；Controlling the difference when the difference between the voltage on the positive DC bus and the voltage on the negative DC bus is greater than a predetermined first threshold or the voltage on the positive DC bus is greater than a bus voltage protection threshold a switch tube operates in a pulse width modulation mode, and controls the second switch tube and the switch tube in the push-pull circuit to be turned off;
    当所述负直流母线上的电压与所述正直流母线上的电压的差值不大于预定的第二阈值、且所述负直流母线上的电压不大于母线电压过高保护 阀值时，控制所述推挽电路工作、且控制所述第一开关管和第二开关管截止；When the difference between the voltage on the negative DC bus and the voltage on the positive DC bus is not greater than a predetermined second threshold, and the voltage on the negative DC bus is not greater than the protection of the bus voltage is too high Controlling the push-pull circuit to operate, and controlling the first switch tube and the second switch tube to be turned off;
    当所述负直流母线上的电压与所述正直流母线上的电压的差值大于预定的第二阈值或所述负直流母线上的电压大于母线电压过高保护阀值时，控制所述第一开关管及所述推挽电路中的开关管截止、且控制所述第二开关管以脉宽调制方式工作。 Controlling the difference when the difference between the voltage on the negative DC bus and the voltage on the positive DC bus is greater than a predetermined second threshold or the voltage on the negative DC bus is greater than the bus voltage protection threshold A switch tube and a switch tube in the push-pull circuit are turned off, and the second switch tube is controlled to operate in a pulse width modulation manner.
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CN110401256A (en) * 2019-08-27 2019-11-01 珠海格力电器股份有限公司 For promoting charging circuit, control method and the PV air-conditioner equipment of reliability

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