US6496396B2 - Reverse recovery circuit, method of operation thereof and asymmetrical half-bridge power converter - Google Patents
Reverse recovery circuit, method of operation thereof and asymmetrical half-bridge power converter Download PDFInfo
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- US6496396B2 US6496396B2 US09/780,187 US78018701A US6496396B2 US 6496396 B2 US6496396 B2 US 6496396B2 US 78018701 A US78018701 A US 78018701A US 6496396 B2 US6496396 B2 US 6496396B2
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33571—Half-bridge at primary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
Definitions
- the present invention is directed, in general, to power conversion and, more specifically, to a circuit for reducing losses associated with a power converter, a method of operating the circuit and a power converter employing the circuit or the method.
- a switched-mode power converter is a frequently employed component of a power supply that converts an input voltage waveform into a specified output voltage waveform.
- switched-mode power converters including an asymmetrical half-bridge power converter.
- a conventional asymmetrical half-bridge power converter includes two power switches coupled to a controller, at least one isolation transformer, a voltage balancing capacitor, a rectifier and a filter.
- the asymmetrical half-bridge power converter generally operates as follows.
- the first and second power switches conduct current in a complimentary manner, with generally unequal duty cycles, to convert an input DC voltage into an AC voltage to be applied across the isolation transformer. Any DC component of the voltage applied to a primary winding of the isolation transformer is blocked by the voltage balancing capacitor coupled in series with the primary winding of the isolation transformer.
- the rectifier then rectifies a secondary voltage from the isolation transformer and the filter smooths and filters the rectified voltage to develop an output voltage for delivery to a load.
- the controller monitors the output voltage of the asymmetrical half-bridge power converter and adjusts the duty cycle of the power switches to ultimately control the output voltage.
- the output voltage may be maintained at a relatively constant level despite relative fluctuations in the input voltage and the load.
- the asymmetrical half-bridge power converter is a well known power circuit topology that may be capable of zero voltage switching (ZVS) operation.
- ZVS zero voltage switching
- a high magnetizing current usually exceeding twice the load current, however, may be required to attain ZVS operation.
- Wittenbreder suggests placing an inductor in series with the primary winding of the isolation transformer.
- One of the ZVS transitions is driven by a combination of the magnetic energy stored in the transformer and the magnetizing energy stored in the inductor.
- the other ZVS transition is driven by energy stored in the inductor. While the series inductance may allow for ZVS operation with lower magnetizing currents, the inductor may cause spurious voltage spikes across the rectifier during reverse recovery.
- one or more of the power switches may be subject to current spikes induced therein by the reverse recovery of the rectifier.
- Saturable reactors may be used in the secondary circuit to reduce current spiking.
- saturable reactors tend to be larger in size than desired and contribute an appreciable cost factor to the power converter.
- the present invention provides, for use with an asymmetrical half-bridge power converter having a primary switching circuit coupled to a primary winding of a transformer and a rectifier coupled to a secondary winding of the transformer, a reverse recovery circuit a method of operation thereof.
- the reverse recovery circuit includes an inductor that reduces current spikes in the primary switching circuit caused by a reverse recovery phenomenon associated with the rectifier.
- the reverse recovery circuit also includes a diode, coupled to the inductor, that clamps a voltage across the rectifier.
- the present invention introduces, in one aspect, a circuit capable of reducing current spikes in the primary switching circuit of a power converter. Additionally, voltage spiking across the rectifier associated with a reverse recovery phenomenon is positively affected. Advantageously, recovering transient energy associated with the reverse recovery phenomenon enhances an energy transfer to a load of the power converter and therefore improves the overall efficiency of the power converter.
- the reverse recovery circuit includes an auxiliary winding, coupled to the inductor, that transfers a portion of energy in the inductor to the secondary winding.
- the inductor and the auxiliary winding are series-coupled to the primary winding. These arrangements allow an effective recovery of a portion of the energy in the power converter.
- the diode of the reverse recovery circuit is coupled to a node between the auxiliary winding and the primary winding.
- the reverse recovery circuit further includes a second diode coupled to the node.
- other circuit configurations may be possible and are well within the scope of the present invention.
- the power converter further includes a controller that controls conduction intervals of a power switch of the power switching circuit.
- the controller monitors an output voltage of the power converter and to operate the power switch in response thereto.
- the output voltage of the power converter may thus be regulated despite variations in the input voltage or the load.
- the controller may monitor other characteristics associated with the power converter as desired and control the power switch as a function thereof.
- FIG. 1 illustrates a schematic diagram of an embodiment of an asymmetrical half-bridge power converter constructed in accordance with the principles of the present invention
- FIG. 2 illustrates a schematic diagram of another embodiment of an asymmetrical half-bridge power converter constructed in accordance with the principles of the present invention.
- FIG. 3 illustrates a schematic diagram of yet another embodiment of an asymmetrical half-bridge power converter constructed in accordance with the principles of the present invention.
- FIG. 1 illustrated is a schematic diagram of an asymmetrical half-bridge power converter 100 constructed in accordance with the principles of the present invention.
- the power converter 100 has an input couplable to a source of electrical power supplying an input voltage Vin.
- the power converter 100 provides an output voltage Vout to a load employing a load resistor R L .
- the power converter 100 includes a primary switching circuit 105 and a secondary rectifying circuit (or rectifier) 110 , which are coupled through an isolation transformer T 1 having a primary winding T 1 p and a secondary winding T 1 s.
- the power converter 100 further includes a controller 115 .
- the primary switching circuit 105 employs a half-bridge topology, which includes first and second power switches Q 1 , Q 2 that are series-coupled across the input of the power converter 100 .
- the primary switching circuit 105 further includes first and second capacitors C 1 , C 2 and a reverse recovery circuit 106 .
- the reverse recovery circuit 106 includes an inductor L 1 and first and second diodes D 1 , D 2 that are coupled to the inductor L 1 and series-coupled across the first and second power switches Q 1 , Q 2 .
- the inductor L 1 is configured to reduce current spikes in the primary switching circuit 105 caused by a reverse recovery phenomenon associated with the secondary rectifying circuit 110 .
- the first and second diodes D 1 , D 2 are configured to clamp a voltage across first and second rectifiers CR 1 , CR 2 included in the secondary rectifying circuit 110 .
- the secondary rectifying circuit 110 further includes first and second filter inductors L 2 , L 3 and a filter capacitor C 3 coupled to the load resistor R L .
- the primary winding T 1 p is coupled between a first node A intermediate the first and second capacitors C 1 , C 2 and a second node B intermediate the first and second diodes D 1 , D 2 . Additionally, the inductor L 1 is coupled between the second node B and a third node C intermediate the first and second power switches Q 1 , Q 2 .
- the controller 115 monitors the output voltage Vout and adjusts relative duty cycles of the first and second power switches Q 1 , Q 2 to regulate the output voltage Vout despite fluctuations in the input voltage Vin or the load resistor R L .
- the controller 115 may monitor other characteristics associated with the power converter 100 as desired.
- the first and second power switches Q 1 , Q 2 are metal oxide semiconductor field-effect transistors (MOSFETs).
- MOSFETs metal oxide semiconductor field-effect transistors
- BJTs bipolar junction transistors
- the power converter 100 may be capable of zero voltage switching (ZVS) operation, a high load current may be required. Further, the first and second power switches Q 1 , Q 2 may be subject to current spikes induced therein by the reverse recovery of the first and second rectifiers CR 1 , CR 2 . The power converter 100 , therefore, uses the inductor L 1 to reduce such current spiking and to allow for ZVS operation with lower load currents.
- ZVS zero voltage switching
- the power converter 100 operates as follows.
- the first and second power switches Q 1 , Q 2 conduct current in a complimentary manner, with generally unequal duty cycles, to convert the input voltage Vin into an AC voltage to be applied across the primary winding Tip of the isolation transformer T 1 .
- the first and second rectifiers CR 1 , CR 2 then rectify a secondary voltage from the secondary winding T 1 s wherein the rectified voltage is smoothed and filtered by the first and second filter inductors L 2 , L 3 and the filter capacitor C 3 to develop the output voltage Vout.
- the first power switch Q 1 has been conducting and current in the primary switching circuit 105 circulates through the first power switch Q 1 , the inductor L 1 , the primary winding T 1 p and the second capacitor C 2 .
- the first filter inductor L 2 is freewheeling and the second filter inductor L 3 is being energized.
- the first power switch Q 1 is then turned OFF (becomes non-conducting), and the second power switch Q 2 becomes conducting (after the ZVS transition) causing the voltage polarity across the secondary winding T 1 s to reverse.
- This condition thereby places a temporarily shorted condition across the secondary winding T 1 s, which is reflected into the primary winding T 1 p.
- the primary winding T 1 p becomes a constant current source and the extra current freewheels and slowly dissipates in the conducting power switch (e.g., the second power switch Q 2 ).
- the conducting power switch thereby performs like a resistive/inductive snubber dissipating energy in the ON-resistance of the conducting power switch and a forward voltage drop of the conducting diode (e.g., the second diode D 2 ).
- the larger the value of inductance of the inductor L 1 the less energy is absorbed thereby requiring more time for reverse recovery of the first and second rectifiers CR 1 , CR 2 . This action is symmetrical when the first and second power switches Q 1 , Q 2 reverse their conducting and non-conducting modes.
- FIG. 2 illustrated is a schematic diagram of another embodiment of an asymmetrical half-bridge power converter 200 constructed in accordance with the principles of the present invention.
- the power converter 200 has an input couplable to a source of electrical power supplying an input voltage Vin.
- the power converter 200 provides an output voltage Vout to a load employing a load resistor R L .
- the power converter 200 includes a primary switching circuit 205 and a secondary rectifying circuit (or rectifier) 210 , which are coupled through an isolation transformer T 1 having a primary winding Tip and a secondary winding T 1 s.
- the power converter 200 further includes a controller 215 .
- the primary switching circuit 205 employs a half-bridge topology, which includes first and second power switches Q 1 , Q 2 that are series-coupled across the input of the power converter 200 .
- the primary switching circuit 205 further includes first and second capacitors C 1 , C 2 and a reverse recovery circuit 206 .
- the reverse recovery circuit 206 includes an inductor L 1 and first and second diodes D 1 , D 2 that are coupled to the inductor L 1 and series-coupled across the first and second power switches Q 1 , Q 2 .
- the inductor L 1 is configured to reduce current spikes in the primary switching circuit 205 caused by a reverse recovery phenomenon associated with the secondary rectifying circuit 210 .
- the first and second diodes D 1 , D 2 are configured to clamp a voltage across first and second rectifiers CR 1 , CR 2 included in the secondary rectifying circuit 210 .
- the secondary rectifying circuit 210 further includes first and second filter inductors L 2 , L 3 and a filter capacitor C 3 coupled to the load resistor R L .
- the primary winding T 1 p is coupled between a first node A intermediate the first and second power switches Q 1 , Q 2 and a second node B intermediate the first and second diodes D 1 , D 2 .
- the inductor L 1 is coupled between the second node B and a third node C intermediate first and second capacitors C 1 , C 2 . This arrangement couples the inductor L 1 to the other side of the primary winding T 1 p as compared to the power converter illustrated and described with respect to FIG. 1 .
- the controller 215 monitors the output voltage Vout and adjusts relative duty cycles of the first and second power switches Q 1 , Q 2 to regulate the output voltage Vout despite fluctuations in the input voltage Vin or the load resistor R L .
- the controller 215 may monitor other characteristics associated with the power converter 200 as desired.
- the first and second power switches Q 1 , Q 2 are metal oxide semiconductor field-effect transistors (MOSFETs), as before.
- MOSFETs metal oxide semiconductor field-effect transistors
- BJTs bipolar junction transistors
- the inductor L 1 is still used to store energy during switching transients that occur when the first and second power switches Q 1 , Q 2 are toggled between their respective conducting states.
- the operation of the power converter 200 is analogous to the operation of the power converter 100 of FIG. 1 .
- the transients modulated by the reverse recovery circuit 206 may be recovered within the power converter 200 .
- the first and second rectifiers CR 1 , CR 2 should be able to accommodate the transients (e.g., a large transient voltage appearing across the isolation transformer T 1 , which produces a large voltage spike on secondary winding T 1 s) without experiencing component damage. Therefore, recovering the switching energy suggests that the first and second rectifiers CR 1 , CR 2 associated with the power converter 200 have about twice the reverse breakdown voltage capability in comparison to the first and second rectifiers CR 1 , CR 2 associated with power converter 100 of FIG. 1 . The overall efficiency of the power converter 200 may be improved by recovering the energy.
- FIG. 3 illustrated is a schematic diagram of another embodiment of an asymmetrical half-bridge power converter 300 employing an auxiliary winding T 1 aux associated with an isolation transformer T 1 .
- the power converter 300 also has an input couplable to a source of electrical power supplying an input voltage Vin.
- the power converter 300 provides an output voltage Vout to a load employing a load resistor R L .
- the power converter 300 includes a primary switching circuit 305 and a secondary rectifying circuit (or rectifier) 310 , which are coupled through the isolation transformer T 1 .
- the isolation transformer T 1 includes a primary winding T 1 p, a secondary winding T 1 s and the auxiliary winding T 1 aux coupled to the primary winding T 1 p.
- the power converter 300 further includes a controller 315 .
- the primary switching circuit 305 also employs a half-bridge topology, which includes first and second power switches Q 1 , Q 2 that are series-coupled across the input of the power converter 300 .
- the primary switching circuit 305 further includes first and second capacitors C 1 , C 2 and a reverse recovery circuit 306 .
- the reverse recovery circuit 306 includes an inductor L 1 coupled to the auxiliary winding T 1 aux and first and second diodes D 1 , D 2 that are coupled to the inductor L 1 and series-coupled across the first and second power switches Q 1 , Q 2 .
- the inductor L 1 and the auxiliary winding T 1 aux cooperate to reduce current spikes in the primary switching circuit 305 and transfer a portion of the energy in the inductor L 1 to the secondary winding T 1 s and, ultimately, an output of the power converter 300 .
- the secondary rectifying circuit 310 includes first and second rectifiers CR 1 , CR 2 coupled to the secondary winding T 1 s.
- the secondary rectifying circuit 310 further includes first and second filter inductors L 2 , L 3 and a filter capacitor C 3 coupled to the load resistor R L .
- the first and second diodes D 1 , D 2 are configured to clamp a voltage across the first and second rectifiers CR 1 , CR 2 .
- the controller 315 monitors the output voltage Vout and adjusts relative duty cycles of the first and second power switches Q 1 , Q 2 to regulate the output voltage Vout despite fluctuations in the input voltage Vin or the load resistor R L .
- the controller 315 may monitor other characteristics associated with the power converter 200 as desired.
- the primary winding T 1 p is coupled between a first node A intermediate the first and second capacitors C 1 , C 2 and a second node B intermediate the first and second diodes D 1 , D 2 .
- the series-coupled auxiliary winding T 1 aux and the inductor L 1 are coupled between the second node B and a third node C intermediate the first and second power switches Q 1 , Q 2 .
- This series-coupled arrangement of the auxiliary winding T 1 aux and the inductor L 1 in the power converter 300 allows improved transient energy management. Part of the transient energy is dissipated in the conducting first or second power switch Q 1 , Q 2 just subsequent to a transition time. However, another portion of the energy is transferred to the secondary winding T 1 s through the auxiliary winding T 1 aux. In this manner, a portion of the transient energy may be recycled for transfer to the load resistor R L .
- the inductor L 1 stores energy while the isolation transformer T 1 is experiencing a shorted condition, as before. As this shorted condition terminates, that is, the reverse recovery mode of the first or second rectifier CR 1 , CR 2 terminates, the voltage across the isolation transformer T 1 increases and is actually larger than usual.
- the input voltage Vin is 400 DC volts.
- 200 volts is applied across the now series-coupled primary winding T 1 p and the auxiliary winding T 1 aux.
- auxiliary winding T 1 aux has one turn and the primary winding T 1 p has nine turns, 20 volts appears across the auxiliary winding T 1 aux and 180 volts appears across the primary winding T 1 p, respectively.
- 200 volts appears across the secondary winding T 1 s. If a current in the secondary winding T 1 s is 10 amperes, this dictates a current of 10 amperes in the primary winding T 1 p as well.
- the current through the inductor L 1 will be greater than 10 amperes since it has been accumulating energy.
- a current of 15 amperes through the inductor L 1 allows a current balance to be made for the isolation transformer T 1 .
- the auxiliary winding T 1 aux has one turn with 15 amperes through it giving 15 ampere-turns.
- the secondary winding T 1 s has 10 turns with 10 amperes, which is 100 ampere-turns. So, 85 ampere-turns is supplied by the primary winding T 1 p, which has 9 turns. This gives a current of about 9.44 amperes to meet the needs of the secondary rectifying circuit 310 .
- the primary winding T 1 p has 200 volts impressed across its nine turns yielding about 22 volts per turn. So the series-coupled auxiliary and primary windings T 1 aux, T 1 p are producing 222 volts instead of 200 volts. Therefore, more energy in the form of a higher secondary voltage is being delivered to the secondary rectifying circuit 310 due to the presence of the auxiliary winding T 1 aux. This action allows the stored energy in the inductor L 1 to dissipate more quickly, and the energy dissipated in the first or second power switches Q 1 , Q 2 to be reduced.
- the present invention introduces, in one aspect, embodiments of a circuit capable of reducing current spikes in the primary switching circuit of a power converter. Additionally, voltage spiking across the secondary rectifier circuits associated with a reverse recovery phenomenon is positively affected.
- recovering transient energy associated with the reverse recovery phenomenon enhances an energy transfer to a load of the power converter and therefore improves an efficiency of the power converter.
- exemplary embodiments of the present invention have been illustrated with reference to specific electronic components. Those skilled in the art are aware, however, that components may be substituted (not necessarily with components of the same type) to create desired conditions or accomplish desired results. For instance, multiple components may be substituted for a single component and vice-versa. Further, while the principles of the present invention have been illustrated in the environment of an asymmetrical half-bridge power converter, other power converter topologies may advantageously employ the principles of the present invention and remain well within the scope of the present invention.
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Priority Applications (1)
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US09/780,187 US6496396B2 (en) | 2001-02-09 | 2001-02-09 | Reverse recovery circuit, method of operation thereof and asymmetrical half-bridge power converter |
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US09/780,187 US6496396B2 (en) | 2001-02-09 | 2001-02-09 | Reverse recovery circuit, method of operation thereof and asymmetrical half-bridge power converter |
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US20020110010A1 US20020110010A1 (en) | 2002-08-15 |
US6496396B2 true US6496396B2 (en) | 2002-12-17 |
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Cited By (7)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
EP1701384A1 (en) | 2005-03-08 | 2006-09-13 | Sun Microsystems France S.A. | Network chip design for grid communication |
US20070025125A1 (en) * | 2005-07-29 | 2007-02-01 | Tdk Corporation | Switching power supply unit |
US20070139020A1 (en) * | 2005-12-20 | 2007-06-21 | Dell Products L.P. | Coupled inductor output regulation |
US20090185398A1 (en) * | 2007-06-30 | 2009-07-23 | Cuks, Llc | Integrated magnetics switching converter with zero inductor and output ripple currents and lossless switching |
US20090196072A1 (en) * | 2007-12-03 | 2009-08-06 | Zhong Ye | Phase-shifted dual-bridge DC/DC converter with wide-range ZVS and zero circulating current |
CN1929279B (en) * | 2006-08-16 | 2010-05-12 | 南京航空航天大学 | Magnetism-integrated double decompression semi-bridge converter |
US20120087161A1 (en) * | 2009-06-16 | 2012-04-12 | Siemens Aktiengesellschaft | Power supply connected in parallel with a power switch for the control circuit thereof |
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US7869226B2 (en) * | 2009-03-31 | 2011-01-11 | Tdk-Lambda Americas Inc. | Achieving ZVS in a two quadrant converter using a simplified auxiliary circuit |
CN103684032B (en) * | 2013-12-30 | 2017-01-11 | 西安理工大学 | Composite pulse generation circuit |
CN106329973A (en) * | 2016-10-31 | 2017-01-11 | 福州大学 | Non-circulation and magnetic integration dual buck half bridge inverter and control method thereof |
CN106452154A (en) * | 2016-12-06 | 2017-02-22 | 福州大学 | Magnetic integration three-level dual-buck type half-bridge inverter and working mode thereof |
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Cited By (11)
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---|---|---|---|---|
EP1701384A1 (en) | 2005-03-08 | 2006-09-13 | Sun Microsystems France S.A. | Network chip design for grid communication |
US20070025125A1 (en) * | 2005-07-29 | 2007-02-01 | Tdk Corporation | Switching power supply unit |
US7313003B2 (en) | 2005-07-29 | 2007-12-25 | Tdk Corporation | Switching power supply unit |
US20070139020A1 (en) * | 2005-12-20 | 2007-06-21 | Dell Products L.P. | Coupled inductor output regulation |
US7602163B2 (en) | 2005-12-20 | 2009-10-13 | Dell Products L.P. | Coupled inductor output regulation |
CN1929279B (en) * | 2006-08-16 | 2010-05-12 | 南京航空航天大学 | Magnetism-integrated double decompression semi-bridge converter |
US20090185398A1 (en) * | 2007-06-30 | 2009-07-23 | Cuks, Llc | Integrated magnetics switching converter with zero inductor and output ripple currents and lossless switching |
US8040704B2 (en) * | 2007-06-30 | 2011-10-18 | Cuks, Llc | Integrated magnetics switching converter with zero inductor and output ripple currents and lossless switching |
US20090196072A1 (en) * | 2007-12-03 | 2009-08-06 | Zhong Ye | Phase-shifted dual-bridge DC/DC converter with wide-range ZVS and zero circulating current |
US9118259B2 (en) | 2007-12-03 | 2015-08-25 | Texas Instruments Incorporated | Phase-shifted dual-bridge DC/DC converter with wide-range ZVS and zero circulating current |
US20120087161A1 (en) * | 2009-06-16 | 2012-04-12 | Siemens Aktiengesellschaft | Power supply connected in parallel with a power switch for the control circuit thereof |
Also Published As
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US20020110010A1 (en) | 2002-08-15 |
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