US20180219473A1 - Power supply apparatus converting input voltage to predetermined output voltage and controlling output voltage based on feedback signal corresponding to output voltage - Google Patents
Power supply apparatus converting input voltage to predetermined output voltage and controlling output voltage based on feedback signal corresponding to output voltage Download PDFInfo
- Publication number
- US20180219473A1 US20180219473A1 US15/420,125 US201715420125A US2018219473A1 US 20180219473 A1 US20180219473 A1 US 20180219473A1 US 201715420125 A US201715420125 A US 201715420125A US 2018219473 A1 US2018219473 A1 US 2018219473A1
- Authority
- US
- United States
- Prior art keywords
- power supply
- voltage
- supply apparatus
- output
- current
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
-
- G—PHYSICS
- G05—CONTROLLING; REGULATING
- G05F—SYSTEMS FOR REGULATING ELECTRIC OR MAGNETIC VARIABLES
- G05F1/00—Automatic systems in which deviations of an electric quantity from one or more predetermined values are detected at the output of the system and fed back to a device within the system to restore the detected quantity to its predetermined value or values, i.e. retroactive systems
- G05F1/10—Regulating voltage or current
- G05F1/46—Regulating voltage or current wherein the variable actually regulated by the final control device is dc
- G05F1/56—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices
- G05F1/575—Regulating voltage or current wherein the variable actually regulated by the final control device is dc using semiconductor devices in series with the load as final control devices characterised by the feedback circuit
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/06—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes without control electrode or semiconductor devices without control electrode
-
- H05B33/0809—
-
- H02M2001/0009—
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/1566—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators with means for compensating against rapid load changes, e.g. with auxiliary current source, with dual mode control or with inductance variation
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
- H05B45/30—Driver circuits
- H05B45/37—Converter circuits
- H05B45/3725—Switched mode power supply [SMPS]
- H05B45/375—Switched mode power supply [SMPS] using buck topology
-
- H—ELECTRICITY
- H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
- H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
- H05B45/00—Circuit arrangements for operating light-emitting diodes [LED]
- H05B45/30—Driver circuits
- H05B45/37—Converter circuits
- H05B45/3725—Switched mode power supply [SMPS]
- H05B45/385—Switched mode power supply [SMPS] using flyback topology
Definitions
- the second power supply circuit having a response higher than that of the first power supply circuit compensates for an excess or a deficiency relative to a desired direct-current current or voltage of a load via the capacitor, so that the load-transient response characteristics of the first power supply circuit can be improved so as to have a higher speed as compared to the prior art.
- FIG. 5A is a timing chart of currents, which shows operations of the power supply apparatus 103 in FIG. 4 ;
- FIG. 8 is a circuit diagram showing detailed configurations of a power factor correction circuit 12 A and a direct-current voltage source 5 in FIG. 7 ;
- FIG. 5A is a timing chart of currents, which shows operations of the power supply apparatus 103 in FIG. 4 .
- FIG. 5B is a timing chart of voltages, which shows operations of the power supply apparatus 103 in FIG. 4 .
- FIG. 6 is a circuit diagram showing a configuration of a power supply apparatus 104 according to a fourth preferred embodiment of the present invention.
- the power supply apparatus 104 is different from the power supply apparatus 103 according to the third preferred embodiment in that a load 8 is replaced with a series circuit in which an LED light emitting element 15 formed of series connection of, for example, two LEDs D 1 and D 2 , and a current sensing resistor 16 are connected in series, and that the series circuit serves as a voltage dividing circuit 17 .
- FIG. 8 is a circuit diagram showing detailed configurations of the power factor correction circuit 12 A and direct-current voltage source 5 in FIG. 7 .
- a voltage V 4 is applied to the main winding 23 .
- a voltage (V 4 /N) generates in the auxiliary winding 26 , and the smoothing capacitor 28 is charged via the rectification element 27 . Accordingly, the voltage V 5 is equal to the voltage (V 4 /N).
- N By adjusting N in accordance with the voltage V 4 , it is possible to set the voltage V 5 .
- the power supply apparatus 100 C includes, instead of the voltage dividing resistor 7 , a current sensing resistor 16 .
Abstract
Description
- The present invention relates to a power supply apparatus such as an ACDC converter or a DCDC converter, for example, electronic equipment including the power supply apparatus, and a power supply circuit for the power supply apparatus.
- A time constant and responsiveness of a passive component included in a typical switching power supply decrease in accordance with a level of a withstand voltage. Accordingly, responsiveness to sharp load transient particularly in a high power application-specific power supply apparatus tends to be lower than that in a small power application-specific power supply apparatus. In addition, a power factor correction circuit is essential for regulating an input harmonic, particularly for high power applications, and power factor correction circuits using various control systems have been developed. It is known that such a power factor correction circuit changes an input current in accordance with a pulsating voltage rectified by a diode bridge, so that pulsation occurs at an output current or an output voltage.
- For example, FIG. 6 of Patent Document 1 (Japanese Patent No. JP5110197B) shows such an example that an output including pulsation, which is provided from a power factor correction circuit, is stepped down and is smoothed by a smoothing switching converter. Such a technique shown in FIG. 6 is typically called a two-converter system. While a switching converter is efficient on one hand, there are problems of an increased circuit scale and an increased noise due to a large number of components in a switching circuit. Regarding those problems, according to
Patent Document 1, a constant-current feedback control circuit that variably controls impedance is connected in series to a light emitting diode (LED) serving as a load, in an effort to miniaturize a power supply apparatus. - In addition, according to Patent Document 2 (Japanese Patent Laid-open Publication No. JP2013-038882A), when an input voltage including pulsation is higher than a predetermined voltage in a power supply apparatus that adopts a two-converter system, a power factor correction circuit is caused to stop and only a smoothing switching converter is allowed to operate. This allows a reduction in loss of a power factor correction circuit, a reduction in size, and an increase in efficiency.
- A problem associated with a high power application-specific power supply apparatus is an unsatisfactory capability of following an excess or a deficiency of a temporary output voltage or current relative to a predetermined output direct-current voltage or current of a load.
- According to one aspect of the present invention, there is provided a power supply apparatus having an input terminal and an output terminal, where the power supply apparatus converts an input voltage at the input terminal into a predetermined output voltage at the output terminal. The power supply apparatus includes first and second power supply circuits and a smoothing capacitor. The first power supply circuit is coupled between the input terminal and the output terminal, and converts the input voltage into a predetermined voltage to output the predetermined voltage. The smoothing capacitor is coupled to the output terminal. The second power supply circuit outputs a predetermined voltage or current to the output terminal via the smoothing capacitor, based on a feedback signal corresponding to the predetermined output voltage.
- With the power supply apparatus according to the present invention, the second power supply circuit having a response higher than that of the first power supply circuit compensates for an excess or a deficiency relative to a desired direct-current current or voltage of a load via the capacitor, so that the load-transient response characteristics of the first power supply circuit can be improved so as to have a higher speed as compared to the prior art.
-
FIG. 1 is a circuit diagram showing a configuration of a power supply apparatus 101 according to a first preferred embodiment of the present invention; -
FIG. 2A is a timing chart of voltages, which shows operations of the power supply apparatus 101 inFIG. 1 ; -
FIG. 2B is a timing chart of currents, which shows operations of the power supply apparatus 101 inFIG. 1 ; -
FIG. 3 is a circuit diagram showing a configuration of a power supply apparatus 102 according to a second preferred embodiment of the present invention; -
FIG. 4 is a circuit diagram showing a configuration of a power supply apparatus 103 according to a third preferred embodiment of the present invention; -
FIG. 5A is a timing chart of currents, which shows operations of the power supply apparatus 103 inFIG. 4 ; -
FIG. 5B is a timing chart of voltages, which shows operations of the power supply apparatus 103 inFIG. 4 ; -
FIG. 6 is a circuit diagram showing a configuration of a power supply apparatus 104 according to a fourth preferred embodiment of the present invention; -
FIG. 7 is a circuit diagram showing a configuration of a power supply apparatus 105 according to a fifth preferred embodiment of the present invention; -
FIG. 8 is a circuit diagram showing detailed configurations of a powerfactor correction circuit 12A and a direct-current voltage source 5 inFIG. 7 ; -
FIG. 9 is a circuit diagram showing detailed configurations of abidirectional converter 4A and a controlsignal generator circuit 12 a inFIG. 7 ; -
FIG. 10 is a circuit diagram showing a configuration of a power supply apparatus 105A according to a first modified embodiment of the fifth preferred embodiment of the present invention; -
FIG. 11 is a circuit diagram showing a configuration of a power supply apparatus 105B according to a second modified embodiment of the fifth preferred embodiment of the present invention; -
FIG. 12 is a circuit diagram showing a configuration of a power supply apparatus 105C according to a third modified embodiment of the fifth preferred embodiment of the present invention; -
FIG. 13 is a circuit diagram showing a configuration of apower supply apparatus 100 according to a sixth preferred embodiment of the present invention; -
FIG. 14 is a circuit diagram showing a configuration of apower supply apparatus 100A according to a seventh preferred embodiment of the present invention; -
FIG. 15 is a circuit diagram showing a configuration of apower supply apparatus 100B according to an eighth preferred embodiment of the present invention; -
FIG. 16 is a circuit diagram showing a configuration of apower supply apparatus 100C according to a ninth preferred embodiment of the present invention; and -
FIG. 17 is a block diagram showing a configuration ofelectronic equipment 200 according to a tenth preferred embodiment of the present invention. - Preferred embodiments according to the present invention will be described below with reference to the drawings. Note that like components are denoted by the same characters in each of the following preferred embodiments.
-
FIG. 1 is a circuit diagram showing a configuration of a power supply apparatus 101 according to a first preferred embodiment of the present invention. InFIG. 1 , the power supply apparatus 101 is a DCDC converter, and includes a direct-current voltage source 1, a DCDC converter 2, and asmoothing capacitor 3. The power supply apparatus 101 further includes a bidirectional DCDC converter (which will be referred to as a bidirectional converter hereinafter) 4, a direct-current voltage source 5,voltage dividing resistors load 8. - In
FIG. 1 , a direct-current voltage from the direct-current voltage source 1 is input to the DCDC converter 2. A voltage input to the DCDC converter 2 is represented by V1 and its corresponding current is represented by I1. The DCDC converter 2 converts electric power inputted from the direct-current voltage source 1 to provide an output. An output terminal of the DCDC converter 2 is coupled to the bidirectional converter 4 via thesmoothing capacitor 3 and is also coupled to one end of theload 8. Thesmoothing capacitor 3 constitutes a smoothing circuit that smooths a voltage or current to be inputted thereto. In this case, a current outputted from the DCDC converter 2 is represented by I2. A voltage V4 applied to theload 8 is divided by a voltage dividingcircuit 9 including the two voltage dividingresistors feedback signal 10 generates and is input to the DCDC converter 2 and the bidirectional converter 4. - The bidirectional converter 4 steps up or down a direct-current voltage V5 from the direct-
current voltage source 5, to a predetermined direct-current voltage V3, based on thefeedback signal 10 corresponding to the output voltage V4, and thereafter outputs the direct-current voltage V3 to theload 8 via thesmoothing capacitor 3. Otherwise, the bidirectional converter 4 steps up or down the voltage V3 input via thesmoothing capacitor 3, to a predetermined voltage V5, based on thefeedback signal 10, and thereafter outputs the voltage V5 to the direct-current voltage source 5. That is, the bidirectional converter 4 bidirectionally converts a direct-current voltage so as to step up or down the direct-current voltage, based on thefeedback signal 10. In this case, a voltage across thesmoothing capacitor 3 is represented by V3 and a current flowing through thesmoothing capacitor 3 is represented by I3. In addition, a current flowing through theload 8 is represented by I4. In other words, a direct-current current I3 can be supplied from the bidirectional converter 4 to the smoothingcapacitor 3 in a direction of an arrow inFIG. 1 or can be extracted from the smoothingcapacitor 3 in a direction opposite to the direction of the arrow inFIG. 1 . The above-described operations do not depend on levels of withstand voltages of the DCDC converter 2 and bidirectional converter 4. That is, as shown inFIGS. 2A and 2B to be described later, even in a case where a withstand voltage of the DCDC converter 2 is set to be higher than a withstand voltage of the bidirectional converter 4, the bidirectional converter 4 can operate in a similar manner. Further, the lower a withstand voltage of the bidirectional converter 4 becomes, the higher responsiveness the bidirectional converter 4 can have as compared to the prior art. - In the power supply apparatus configured as described above, the DCDC converter 2 can be constituted of a step-up converter in a case where the voltage V4 is higher than the voltage V1. In addition, the DCDC converter 2 is required to be constituted of a step-down converter in a case where the voltage V4 is lower than the voltage V1.
-
FIG. 2A is a timing chart of voltages, which shows operations of the power supply apparatus 101 inFIG. 1 .FIG. 2B is a timing chart of currents, which shows operations of the power supply apparatus 101 inFIG. 1 . - During a time interval t1 in each of
FIGS. 2A and 2B , the load current I4 is constant. In addition, the DCDC converter 2 outputs the current I2 that corresponds to the load current I4 and the voltage V4 that corresponds to thefeedback signal 10 generated by the voltage V4 and thevoltage dividing circuit 9 and, using electric power inputted from the direct-current voltage source 1. The bidirectional converter 4 outputs the current I3 that corresponds to a change in thefeedback signal 10. During the time interval t1, thefeedback signal 10 is constant since the voltage V4 is constant, the current I3 outputted from the bidirectional converter 4 is 0, and the voltage V3 is constant. - During a time interval t2, when the load current I4 increases and the voltage V4 decreases so that the
feedback signal 10 decreases, the current I2 outputted from the DCDC converter 2 gradually increases up to a current corresponding to the load current I4, in accordance with a time constant of the DCDC converter 2. Also regarding the bidirectional converter 4, in response to a decrease in thefeedback signal 10, the current I3 outputted from the bidirectional converter 4 is caused to increase in accordance with a time constant of the bidirectional converter 4. At that time, the responsiveness of the bidirectional converter 4 is higher than the responsiveness of the DCDC converter 2 since a time constant of a typical switching power supply decreases depending on a level of a withstand voltage. Accordingly, in the time interval t2 where there is a deficiency of the current I2 outputted from the DCDC converter 2 relative to the load current I4 which has increased, the current I3 outputted from the bidirectional converter 4 compensates for a deficiency of the load current I4. Thus, the power supply apparatus 101 can be improved so as to have higher responsiveness to the load current I4, as a consequence. - During a time interval t3, operations similar to those in the time interval t1 are performed. During a time interval t4, the load current I4 decreases, the voltage V4 increases, and the
feedback signal 10 increases. At that time, operations reverse to those in the time interval t2 are performed in such a manner that the bidirectional converter 4 extracts, as the current I3, an excess of the current I2, which is outputted from the DCDC converter 2 and becomes temporarily too large with respect to a decrement of the load current I4, via the smoothingcapacitor 3 in a direction opposite to the direction of the arrow inFIG. 1 . This can improve the responsiveness of the power supply apparatus 101 to the load current I4. In addition, at that time, excess electric power extracted as the current I3 by the bidirectional converter 4 can be regenerated in the direct-current voltage source 5, so that a reduction in efficiency of the power supply apparatus 101 can be minimized as a consequence. - In this case, a withstand voltage of the bidirectional converter 4 is determined by the voltage V3 or the voltage V5, whichever is higher. If the bidirectional converter 4 is a step-down converter, the voltage V5 should be set at a value higher than a maximum value of the voltage V3.
- (1) If the bidirectional converter 4 is a step-up converter, the voltage V5 should be set at a value lower than a minimum value of the voltage V3.
- (2) If the bidirectional converter 4 is a step-up and step-down converter, the voltage V5 can have an arbitrary value.
-
FIG. 3 is a circuit diagram showing a configuration of a power supply apparatus 102 according to a second preferred embodiment of the present invention. The power supply apparatus 102 is different from the power supply apparatus 101 according to the first preferred embodiment in that the bidirectional converter 4 is replaced with alinear regulator 11. - The
linear regulator 11, like the bidirectional converter 4, outputs a current I3 corresponding to a change in afeedback signal 10, in accordance with a time constant of thelinear regulator 11. At that time, it is typically known that the time constant of thelinear regulator 11 is smaller than a time constant of a DCDC converter 2 having a higher withstand voltage, so that functions and effects similar to those in the first preferred embodiment are provided as a consequence. - The use of a liner regulator, which can be typically constituted of a circuit simpler than that of a bidirectional converter, allows a reduction in size as compared to the power supply apparatus 101 according to the first preferred embodiment. On the other hand, a difference from the first preferred embodiment lies in that, at a time of load transient such as the time interval t4 in
FIGS. 2A and 2B , excess electric power is not regenerated in a direct-current voltage source 5 so that the bidirectional converter 4 operates, but is calculated as loss. -
FIG. 4 is a circuit diagram showing a configuration of a power supply apparatus 103 according to a third preferred embodiment of the present invention. The power supply apparatus 103 is different from the power supply apparatus 101 according to the first preferred embodiment in the following respects. - (1) The DCDC converter 2 is replaced with a power
factor correction circuit 12 that corrects a power factor of the power supply apparatus 103. - (2) The direct-
current voltage source 1 is replaced with an alternating-current power supply 13, and the alternating-current power supply 13 serves as a power supply that inputs power to the powerfactor correction circuit 12 via a rectifyingcircuit 14 including a diode bridge circuit. - It is typically known that a power factor correction circuit changes an input current in accordance with a pulsating voltage rectified by a diode bridge circuit or the like, so that a ripple occurs at an output current or voltage. The power supply apparatus 103 according to the third preferred embodiment of the present invention has a function of smoothing such a ripple.
- In the power supply apparatus 103, by constituting the power
factor correction circuit 12 of a step-up and step-down converter, it is possible to achieve a function of smoothing the ripple at a voltage V4 of an arbitrary value even in a case where the voltage V4 does not depend on a level of a voltage V1 and is lower than a maximum value of the voltage V1. In a case where the voltage V4 is higher than a maximum value of the voltage V1, the powerfactor correction circuit 12 can be constituted of a step-up converter. Examples of a step-up and step-down converter may include a flyback converter, a polarity reversal converter, an H-bridge step-up and step-down converter, and the like. -
FIG. 5A is a timing chart of currents, which shows operations of the power supply apparatus 103 inFIG. 4 .FIG. 5B is a timing chart of voltages, which shows operations of the power supply apparatus 103 inFIG. 4 . - As is made clear from
FIGS. 5A and 5B , the powerfactor correction circuit 12 allows the voltage V1 and a current I1 to have waveforms similar to each other. Assuming that the powerfactor correction circuit 12 is a switching converter, for example, and loss can be disregarded, input electric power (V1×I1) and output electric power (V4×I2) are approximately equal to each other. Accordingly, a current I2 is expressed by the following equation. -
I2=V1×I1/V4 - Thus, also the current I2 is a pulsating current like the current I1. Since the bidirectional converter 4 operates so as to make a signal level of a feedback signal constant, the voltage V4 is constant. The bidirectional converter 4 controls a voltage V3 in order to make the voltage V4 constant, so that a voltage (V2+V3) is constant. In addition, this matter is equivalent to operations of cancelling the pulsating current I2 and converting the pulsating current I2 into a current I4 via the smoothing
capacitor 3 in the bidirectional converter 4, so that the current I3 and a ripple current of the current I2 are symmetrical and an average value of the current I3 is 0. From operation waveforms shown inFIGS. 5A and 5B , it is made clear that the bidirectional converter 4 can smooth a ripple current and a ripple voltage of the powerfactor correction circuit 12 with the configuration inFIG. 4 . - In this case, a withstand voltage of the bidirectional converter 4 is determined by the voltage V3 or a voltage V5, whichever is higher. If the bidirectional converter 4 is a step-down converter, the voltage V5 should be set at a value higher than a maximum value of the voltage V3.
- (1) If the bidirectional converter 4 is a step-up converter, the voltage V5 should be set at a value lower than a minimum value of the voltage V3.
- (2) If the bidirectional converter 4 is a step-up and step-down converter, the voltage V5 can have an arbitrary value. Since the direct-
current voltage source 5 supplies to the bidirectional converter 4 a current having an average value of approximately 0, the direct-current voltage source 5 need not achieve high performance as a power supply. - Accordingly, while the direct-
current voltage source 5 can be constituted of a power supply using an auxiliary winding extending from the powerfactor correction circuit 12, for example, an amplitude range of V3 should be determined taking into account variation in withstand voltage of the direct-current voltage source 5 if the bidirectional converter 4 is a step-down converter or a step-up converter. In addition, a withstand voltage of the bidirectional converter 4 should include an adequate margin for variation. On the other hand, if the bidirectional converter 4 is a step-up and step-down converter, the direct-current voltage source 5 can have an arbitrary value. Accordingly, if an average value of V3 is set at, for example, a median value in variation of the direct-current voltage source 5, a withstand voltage of the bidirectional converter 4 is determined substantially by a ripple voltage of the voltage V3 unless variation in voltage of the direct-current voltage source 5 exceeds V3. -
FIG. 6 is a circuit diagram showing a configuration of a power supply apparatus 104 according to a fourth preferred embodiment of the present invention. The power supply apparatus 104 is different from the power supply apparatus 103 according to the third preferred embodiment in that aload 8 is replaced with a series circuit in which an LEDlight emitting element 15 formed of series connection of, for example, two LEDs D1 and D2, and acurrent sensing resistor 16 are connected in series, and that the series circuit serves as avoltage dividing circuit 17. - In this case, the
voltage dividing circuit 17 including the LEDlight emitting element 15 and thecurrent sensing resistor 16 divides an output voltage V4, and generates a feedback signal corresponding to the output voltage V4. A signal voltage of the feedback signal is determined by a product of a current I4 flowing through thecurrent sensing resistor 16 and a resistance of thecurrent sensing resistor 16. Since a bidirectional converter 4 operates so as to make the feedback signal constant, the current I4 is constant on the assumption that the resistance of thecurrent sensing resistor 16 is constant. Accordingly, operation waveforms similar to those inFIGS. 5A and 5B are provided. - The power supply apparatus configured as described above has functions and effects similar to those in the first preferred embodiment.
-
FIG. 7 is a circuit diagram showing a configuration of a power supply apparatus 105 according to a fifth preferred embodiment of the present invention. The power supply apparatus 105 is different from the power supply apparatus 103 according to the third preferred embodiment in the following respects. - (1) The
feedback signal 10 input to the bidirectional converter 4 is replaced with acontrol signal 18 outputted from a powerfactor correction circuit 12, and the bidirectional converter 4 is replaced with abidirectional converter 4A. - (2) The power
factor correction circuit 12 is replaced with a powerfactor correction circuit 12A, and the powerfactor correction circuit 12A further includes a controlsignal generator circuit 12 a that generates acontrol signal 18, based on afeedback signal 10. - The
control signal 18 outputted from the powerfactor correction circuit 12A uses an output signal of a differential amplifier 45 (FIG. 9 ) included in the powerfactor correction circuit 12A, for example. As a result of this, a function equivalent to using the above-describedfeedback signal 10 as a signal input to thebidirectional converter 4A can be obtained. -
FIG. 8 is a circuit diagram showing detailed configurations of the powerfactor correction circuit 12A and direct-current voltage source 5 inFIG. 7 . -
FIG. 8 shows the powerfactor correction circuit 12A which has a configuration including a polarity reversal converter, as an example of a case where a step-up and step-down converter is used for the powerfactor correction circuit 12A. InFIG. 8 , VIN+ and VIN− represent a positive voltage and a negative voltage of an input, respectively, and VOUT+ and VOUT− represent a positive voltage and a negative voltage of an output, respectively. V1, V4, and V5 are the same as the voltages shown inFIG. 1, 3, 4, 6 , or 7, respectively. - In
FIG. 8 , the polarity reversal converter in the powerfactor correction circuit 12A is configured to include aconversion control circuit 19, adrive element 20, arectification element 21, a main winding 23 of atransformer 22, aninput bypass capacitor 24, and anoutput capacitor 25. In this case, thedrive element 20 is a MOS transistor, for example, and therectification element 21 is a diode, for example. An input voltage V1 is applied to theinput bypass capacitor 24, theinput bypass capacitor 24 and theoutput capacitor 25 are connected in series to each other, and a junction point of those capacitors is connected so that feedback is provided to an input-voltage side via the main winding 23 and thedrive element 20. One end of theoutput capacitor 25 is coupled to a cathode of therectification element 21 and thedrive element 20 via the main winding 23, and the other end of theoutput capacitor 25 is coupled to an anode of therectification element 21. In this case, thedrive element 20 is controlled to be turned on/off by acontrol signal 19S from theconversion control circuit 19. - The direct-
current voltage source 5 has a configuration using an auxiliary winding 26 of thetransformer 22 in the power supply apparatus 101, 102, 103, 104, or 105 shown inFIG. 1, 3, 4, 6 , or 7, and VAUX represents an output voltage from an output terminal of the direct-current voltage source 5. An output voltage from the auxiliary winding 26 serves as an output voltage V5, passing through arectification element 27, which is a diode, for example, and a smoothingcapacitor 28. - Next, operations of the direct-
current voltage source 5 using the auxiliary winding 26 will be described below, with reference toFIG. 8 . In this case, assume that the main winding 23 and the auxiliary winding 26 of thetransformer 22 have a turn ratio of N to 1. - First of all, when the
drive element 20 is turned off and therectification element 21 is rectifying, a voltage V4 is applied to the main winding 23. A voltage (V4/N) generates in the auxiliary winding 26, and the smoothingcapacitor 28 is charged via therectification element 27. Accordingly, the voltage V5 is equal to the voltage (V4/N). By adjusting N in accordance with the voltage V4, it is possible to set the voltage V5. - Subsequently, when the
drive element 20 is turned on, a voltage V1 is applied to the main winding 23. A voltage (−V1/N) generates in the auxiliary winding 26, a reverse bias voltage is applied to therectification element 27, and charging of the smoothingcapacitor 28 is stopped. Thus, the smoothingcapacitor 28 is charged only in a period during which thedrive element 20 is turned off. - As described above, it is clear that the voltage V5 varies due to variation in the main winding 23 and the auxiliary winding 26, or variation in the voltage V4, in the configuration of the direct-
current voltage source 5 shown inFIG. 8 . However, while an output voltage includes pulsation in a typical power factor correction circuit, pulsation in the output voltage V4 is reduced in the above-described system, which eliminates a need to include a pulsating voltage in variation in the voltage V4. Thus, variation in the voltage V5 is smaller than that in the prior art. -
FIG. 9 is a circuit diagram showing detailed configurations of thebidirectional converter 4A and controlsignal generator circuit 12 a inFIG. 7 . In this case, an example in which a step-down converter is used for thebidirectional converter 4A is shown. - In
FIG. 9 , the powerfactor correction circuit 12A includes the controlsignal generator circuit 12 a, and the controlsignal generator circuit 12 a is configured to include aphase compensation capacitor 44, the differential amplifier 45, a reference voltage source 46, and theconversion control circuit 19. In this case, theconversion control circuit 19 is configured to include adifferential amplifier 47, asawtooth oscillator 48, and adriver circuit 49. In addition, thebidirectional converter 4A includes adiode 29, aninput bypass capacitor 30, adrive element 32, arectification element 33, aninductor 34, anoutput capacitor 35, andvoltage dividing resistors bidirectional converter 4A further includes afilter capacitor 38,decoupling resistors control circuit 31, areference voltage source 43, adifferential amplifier 42, and a high-frequencyresponse adjusting resistor 41. In this case, the powerfactor correction circuit 12A and thebidirectional converter 4A are coupled to each other via thephase compensation capacitor 44. - In
FIG. 9 , thediode 29 is interposed at an input terminal in order to prevent a back-flowing current of thebidirectional converter 4A from flowing into an input. Theinput bypass capacitor 30 smooths a current flowing in each of two opposite directions of thebidirectional converter 4A. A smoothed voltage is subjected to switching by thedrive element 32 and therectification element 33 each driven by a control signal from the switchingcontrol circuit 31, and thereafter, is output as an output voltage V3, via theinductor 34 and theoutput capacitor 35. The output voltage V3 is divided by thevoltage dividing resistors control circuit 31 via thedecoupling resistor 37. In addition, afeedback signal 10 generated from a pulsating current outputted from the powerfactor correction circuit 12A is input to the controlsignal generator circuit 12 a in the powerfactor correction circuit 12A. Thefeedback signal 10 is input, as acontrol signal 18, to thebidirectional converter 4A via the differential amplifier 45 and thephase compensation capacitor 44. Only a high-frequency component of thecontrol signal 18, which includes the above-stated pulsation, is amplified by thedifferential amplifier 42 and the high-frequencyresponse adjusting resistor 41 in thebidirectional converter 4A, and is input to the switchingcontrol circuit 31 via thedecoupling resistor 36. That is, the switchingcontrol circuit 31 of thebidirectional converter 4A receives both inputs of: - (1) a control signal for making an average value of the voltage V3 constant, via the
decoupling resistor 37; and - (2) a signal for controlling V3 in accordance with a pulsating current outputted from a power factor correction circuit, via the
decoupling resistor 36. - Then, the switching
control circuit 31 can control the voltage V3 so that the voltage V4 is constant, as a consequence. - It is additionally noted that the
differential amplifier 47 generates a voltage difference between a voltage signal outputted from the differential amplifier 45 and a sawtooth voltage from thesawtooth oscillator 48, and outputs the voltage difference to thedriver circuit 49, in theconversion control circuit 19. Thedriver circuit 49 drives the voltage difference input thereto, to generate acontrol signal 19S. - A voltage that generates in the
input bypass capacitor 30 is a pulsating voltage, a minimum value of which is equal to the voltage V5, so that a withstand voltage that thebidirectional converter 4A is required to have, can be made lower as capacitance of theinput bypass capacitor 30 increases. Each of thedrive element 32 and therectification element 33 is required to have a withstand voltage not lower than a voltage that generates in theinput bypass capacitor 30. In a case where the voltage V5 has amplitude of 20 V, for example, and a pulsating voltage that generates in theinput bypass capacitor 30 has amplitude of 5 V, for example, each of thedrive element 32 and therectification element 33 can be constituted of an element having a withstand voltage not lower than 25 V. Theoutput capacitor 35 is used for smoothing a ripple current of theinductor 34. An average value of the voltage V3 is determined as a result of feedback of a voltage divided by thevoltage dividing resistors filter capacitor 38, to the switchingcontrol circuit 31. In a case where a control voltage of the switchingcontrol circuit 31 is 1 V, for example, assuming that thevoltage dividing resistor 39 is 90 kΩ and thevoltage dividing resistor 40 is 10 kΩ, the voltage V3 is 10 V on average and has a waveform having amplitude of 20 V. In a case where thebidirectional converter 4A is constituted of an element having a withstand voltage of 30 V, for example, a scale of thebidirectional converter 4A can be reduced to one-tenth or smaller of a smoothing switching converter used in a two-converter system. -
FIG. 10 is a circuit diagram showing a configuration of a power supply apparatus 105A according to a first modified embodiment of the fifth preferred embodiment of the present invention. InFIG. 10 , the power supply apparatus 105A is different from the power supply apparatus 105 according to the fifth preferred embodiment in that theload 8 is replaced with a series circuit in which an LEDlight emitting element 15 formed of series connection of, for example, two LEDs D1 and D2, and acurrent sensing resistor 16 are connected in series, and that the series circuit serves as avoltage dividing circuit 17. The configuration, functions, and effects in the other respects are similar to those in the fifth preferred embodiment. -
FIG. 11 is a circuit diagram showing a configuration of a power supply apparatus 105B according to a second modified embodiment of the fifth preferred embodiment of the present invention. InFIG. 11 , the power supply apparatus 105B is different from the power supply apparatus 105 according to the fifth preferred embodiment in that the powerfactor correction circuit 12A is replaced with aDCDC converter 2A including a controlsignal generator circuit 12 a. The configuration, functions, and effects in the other respects are similar to those in the fifth preferred embodiment. It is additionally noted that an input terminal of theDCDC converter 2A is coupled to a direct-current voltage source 1. -
FIG. 12 is a circuit diagram showing a configuration of a power supply apparatus 105C according to a third modified embodiment of the fifth preferred embodiment of the present invention. InFIG. 12 , the power supply apparatus 105C is different from the power supply apparatus 105B inFIG. 11 in that theload 8 is replaced with a series circuit in which an LEDlight emitting element 15 forming of series connection of, for example, two LEDs D1 and D2, and acurrent sensing resistor 16 are connected in series, and that the series circuit serves as avoltage dividing circuit 17. The configuration, functions, and effects in the other respects are similar to those in the second modified embodiment of the fifth preferred embodiment. It is additionally noted that an input terminal of aDCDC converter 2A is coupled to a direct-current voltage source 1. - Next, sixth to ninth preferred embodiments will discuss overall configurations of the first to fifth preferred embodiments with reference to
FIGS. 13 to 16 . -
FIG. 13 is a circuit diagram showing a configuration of apower supply apparatus 100 according to a sixth preferred embodiment of the present invention. InFIG. 13 , thepower supply apparatus 100 is coupled to be interposed between a direct-current voltage source 1 and aload 8 and is configured to include: - (1) a switching power supply circuit 301 constituted of a DCDC converter 2 or a power
factor correction circuit 12; - (2) a smoothing
capacitor 3; - (3) a power supply circuit 302 constituted of a bidirectional converter 4 or a
linear regulator 11; and - (4) a
voltage dividing circuit 9 that includesvoltage dividing resistors feedback signal 10 of a divided voltage. - The
power supply apparatus 100 configured as described above is similar in functions and effects to the power supply apparatuses 101, 102, 103, 105, and 105B. -
FIG. 14 is a circuit diagram showing a configuration of apower supply apparatus 100A according to a seventh preferred embodiment of the present invention. InFIG. 14 , thepower supply apparatus 100A is coupled to be interposed between a direct-current voltage source 1 and aload 8 and is configured to include: - (1) a switching power supply circuit 301A constituted of a
DCDC converter 2A or a powerfactor correction circuit 12A that includes a controlsignal generator circuit 12 a; - (2) a smoothing
capacitor 3; - (3) a
power supply circuit 302A constituted of abidirectional converter 4A or alinear regulator 11A; and - (4) a
voltage dividing circuit 9 that includesvoltage dividing resistors feedback signal 10 of a divided voltage. - The
power supply apparatus 100A configured as described above is similar in functions and effects to the power supply apparatuses 104, 105A, and 105C. -
FIG. 15 is a circuit diagram showing a configuration of apower supply apparatus 100B according to an eighth preferred embodiment of the present invention. InFIG. 15 , thepower supply apparatus 100B is different from thepower supply apparatus 100 inFIG. 13 in the following respects. - (1) The
power supply apparatus 100B includes, instead of theload 8, aload 15A such as an LEDlight emitting element 15, for example, which is placed at a position where avoltage dividing resistor 6 is coupled. - (2) The
power supply apparatus 100B includes, instead of thevoltage dividing resistor 7, acurrent sensing resistor 16. - The
power supply apparatus 100B configured as described above is similar in functions and effects to the power supply apparatuses 105A and 105C. -
FIG. 16 is a circuit diagram showing a configuration of apower supply apparatus 100C according to a ninth preferred embodiment of the present invention. InFIG. 16 , thepower supply apparatus 100C is different from thepower supply apparatus 100A inFIG. 14 in the following respects. - (1) The
power supply apparatus 100C includes, instead of theload 8, aload 15A such as an LEDlight emitting element 15, for example, which is placed at a position where avoltage dividing resistor 6 is coupled. - (2) The
power supply apparatus 100C includes, instead of thevoltage dividing resistor 7, acurrent sensing resistor 16. - The
power supply apparatus 100C configured as described above is similar in functions and effects to the power supply apparatuses 105A and 105C. -
FIG. 17 is a block diagram showing a configuration ofelectronic equipment 200 according to a tenth preferred embodiment of the present invention. InFIG. 17 , theelectronic equipment 200 is configured to include: - (1) the
power supply apparatus - (2) an
electronic circuit 110 which is a predetermined load. - The
electronic equipment 200 is, for example, a portable telephone, a smartphone, a personal computer, or a multifunctional peripheral including a scanner and a printer, for example. A direct-current voltage from thepower supply apparatus electronic circuit 110. - (1) In a case where the
DCDC converter 2 or 2A is used as the switching power supply circuit 301 or 301A, thepower supply circuit 302 or 302A which is improved so as to have higher responsiveness than responsiveness of theDCDC converter 2 or 2A is included. Accordingly, an excess or a deficiency relative to a desired direct-current current or voltage of theload capacitor 3, so that load-transient response characteristics of the switching power supply circuit 301 or 301A can be improved. - (2) When the power
factor correction circuit power supply circuit 302 or 302A which has higher responsiveness than that of the powerfactor correction circuit power supply circuit 302 or 302A compensates for an excess or a deficiency in a pulsating current or voltage outputted from the powerfactor correction circuit load capacitor 3. This can reduce pulsating components occurring due to the powerfactor correction circuit - (3) In a case where the
bidirectional converter 4 or 4A is used as thepower supply circuit 302 or 302A, excess electric power relative to desired electric power of theload power supply apparatus - (4) In a case where the
linear regulator power supply circuit 302 or 302A, though excess electric power is not stored but calculated as loss, thepower supply circuit 302 or 302A can be typically constituted of a simpler circuit than that of thebidirectional converter 4 or 4A, so that a reduction in size can be achieved. - (5) As described above, what is required of the
power supply circuit 302 or 302A is to output only an excess or a deficiency relative to a desired direct-current current or voltage of theload power supply circuit 302 or 302A can operate with a withstand voltage lower than a desired withstand voltage of thepower supply apparatus - While the smoothing
capacitor 3 is used in the above-described preferred embodiments, the present invention is not limited thereto, and a capacitor may be used.
Claims (23)
Priority Applications (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US15/420,125 US10050517B1 (en) | 2017-01-31 | 2017-01-31 | Power supply apparatus converting input voltage to predetermined output voltage and controlling output voltage based on feedback signal corresponding to output voltage |
PCT/JP2017/021952 WO2018142640A1 (en) | 2017-01-31 | 2017-06-14 | Power source device and electronic apparatus |
Applications Claiming Priority (1)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US15/420,125 US10050517B1 (en) | 2017-01-31 | 2017-01-31 | Power supply apparatus converting input voltage to predetermined output voltage and controlling output voltage based on feedback signal corresponding to output voltage |
Publications (2)
Publication Number | Publication Date |
---|---|
US20180219473A1 true US20180219473A1 (en) | 2018-08-02 |
US10050517B1 US10050517B1 (en) | 2018-08-14 |
Family
ID=62980259
Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
---|---|---|---|
US15/420,125 Active US10050517B1 (en) | 2017-01-31 | 2017-01-31 | Power supply apparatus converting input voltage to predetermined output voltage and controlling output voltage based on feedback signal corresponding to output voltage |
Country Status (2)
Country | Link |
---|---|
US (1) | US10050517B1 (en) |
WO (1) | WO2018142640A1 (en) |
Cited By (4)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20190202300A1 (en) * | 2018-01-03 | 2019-07-04 | Lear Corporation | Pre-Charging DC Link Capacitor of On-Board Charger (OBC) Using Traction Battery |
US11349386B2 (en) * | 2020-06-17 | 2022-05-31 | Hyundai Motor Company | Apparatus and method for charging battery of vehicle |
US11606849B2 (en) * | 2019-06-28 | 2023-03-14 | Texas Instruments Incorporated | Active shunt filtering |
US11815928B2 (en) | 2020-12-11 | 2023-11-14 | Skyworks Solutions, Inc. | Supply-glitch-tolerant regulator |
Families Citing this family (3)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
CN109587889B (en) * | 2018-12-25 | 2022-03-04 | 中山市卓越制品有限公司 | LED lamp tube control method, system and device |
CN112015093B (en) * | 2019-05-31 | 2022-02-11 | 广东美的制冷设备有限公司 | Drive control method, device, household appliance and computer readable storage medium |
US11314916B2 (en) | 2020-07-31 | 2022-04-26 | International Business Machines Corporation | Capacitance extraction |
Family Cites Families (20)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6700359B2 (en) * | 2001-09-12 | 2004-03-02 | Texas Instruments Incorporated | Method for simultaneous output ramp up of multiple regulators |
JP2007252113A (en) | 2006-03-16 | 2007-09-27 | Ricoh Co Ltd | Switching regulator |
JP4836624B2 (en) | 2006-03-23 | 2011-12-14 | 株式会社リコー | Switching regulator |
JP2008092635A (en) | 2006-09-29 | 2008-04-17 | Ricoh Co Ltd | Synchronous rectifying type switching regulator, control circuit of synchronous rectifying type switching regulator, and operation control method of synchronous rectifying type switching regulator |
JP5014772B2 (en) | 2006-12-26 | 2012-08-29 | 株式会社リコー | Current mode control switching regulator |
JP5386801B2 (en) | 2007-07-27 | 2014-01-15 | 株式会社リコー | Switching regulator and operation control method thereof |
JP5169170B2 (en) | 2007-11-26 | 2013-03-27 | 株式会社リコー | Step-down switching regulator |
CN101507609B (en) * | 2008-02-15 | 2013-03-06 | Ge医疗系统环球技术有限公司 | Detector panel and X-ray imaging device |
JP5063474B2 (en) | 2008-05-13 | 2012-10-31 | 株式会社リコー | Current mode control switching regulator and operation control method thereof |
JP5309683B2 (en) | 2008-05-13 | 2013-10-09 | 株式会社リコー | Step-down switching regulator |
JP5470765B2 (en) | 2008-07-17 | 2014-04-16 | 株式会社リコー | Switching power supply circuit |
JP5630895B2 (en) * | 2010-02-25 | 2014-11-26 | トレックス・セミコンダクター株式会社 | Switching power supply circuit |
JP2012019625A (en) | 2010-07-08 | 2012-01-26 | Ricoh Co Ltd | Drive circuit, semiconductor device with drive circuit, switching regulator and electronic apparatus having them |
JP5110197B2 (en) | 2011-01-18 | 2012-12-26 | サンケン電気株式会社 | LED driving device and LED lighting device |
JP5692721B2 (en) * | 2011-02-22 | 2015-04-01 | ニチコン株式会社 | Switching power supply |
JP5884026B2 (en) | 2011-08-05 | 2016-03-15 | パナソニックIpマネジメント株式会社 | Power supply |
JP2013090520A (en) | 2011-10-21 | 2013-05-13 | Nippon Soken Inc | Dc/dc converter |
JP2015126638A (en) * | 2013-12-27 | 2015-07-06 | ニチコン株式会社 | Switching power supply device |
JP6409171B2 (en) | 2014-09-11 | 2018-10-24 | リコー電子デバイス株式会社 | Switching power supply device, electronic device, and bidirectional DCDC converter |
US20160087602A1 (en) * | 2014-09-24 | 2016-03-24 | Western Digital Technologies, Inc. | Adaptive feedback for power distribution network impedance barrier suppression |
-
2017
- 2017-01-31 US US15/420,125 patent/US10050517B1/en active Active
- 2017-06-14 WO PCT/JP2017/021952 patent/WO2018142640A1/en active Application Filing
Cited By (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US20190202300A1 (en) * | 2018-01-03 | 2019-07-04 | Lear Corporation | Pre-Charging DC Link Capacitor of On-Board Charger (OBC) Using Traction Battery |
US10351004B1 (en) * | 2018-01-03 | 2019-07-16 | Lear Corporation | Pre-charging DC link capacitor of on-board charger (OBC) using traction battery |
US11606849B2 (en) * | 2019-06-28 | 2023-03-14 | Texas Instruments Incorporated | Active shunt filtering |
US11349386B2 (en) * | 2020-06-17 | 2022-05-31 | Hyundai Motor Company | Apparatus and method for charging battery of vehicle |
US11815928B2 (en) | 2020-12-11 | 2023-11-14 | Skyworks Solutions, Inc. | Supply-glitch-tolerant regulator |
Also Published As
Publication number | Publication date |
---|---|
WO2018142640A1 (en) | 2018-08-09 |
US10050517B1 (en) | 2018-08-14 |
Similar Documents
Publication | Publication Date | Title |
---|---|---|
US10050517B1 (en) | Power supply apparatus converting input voltage to predetermined output voltage and controlling output voltage based on feedback signal corresponding to output voltage | |
US10327297B2 (en) | Control circuit, control method and LED driving circuit thereof | |
US10158289B2 (en) | DC/DC converter | |
TWI479790B (en) | Switching-mode power supply with ripple mode control and associated methods | |
US9998022B2 (en) | Current limit peak regulation circuit for power converter with low standby power dissipation | |
US8866450B2 (en) | Electronic device and method for DC-DC conversion | |
EP1229634A2 (en) | Switching power supply apparatus | |
US11038423B2 (en) | Frequency control circuit, control method and switching converter | |
JP2019068675A (en) | AC-DC converter | |
TWI625923B (en) | Dc-dc converting circuit and multi-phase power controller thereof | |
US8755200B2 (en) | Single stage power conversion unit with circuit to smooth and holdup DC output voltage | |
WO2020053884A1 (en) | Ripple cancellation circuit in switching dc-dc converters and methods thereof | |
US20110210710A1 (en) | Step-up dc-dc converter and semiconductor integrated circuit device | |
JP2019062665A (en) | AC-DC converter | |
US7466111B2 (en) | Power supply unit and portable apparatus utilizing the same | |
JP6815495B2 (en) | Ripple injection circuit and electronic equipment equipped with it | |
JP6654548B2 (en) | Switching power supply | |
JP5212494B2 (en) | Multiple voltage output power supply | |
JP6409171B2 (en) | Switching power supply device, electronic device, and bidirectional DCDC converter | |
KR20220092510A (en) | Digital Non-Linear Conversion for Voltage Mode Control of Power Converters | |
US20140092644A1 (en) | Switching power supply device and method for circuit design of the switching power supply device | |
JP2005218252A (en) | Power factor improving circuit and power supply | |
JP2968670B2 (en) | DC-DC converter with protection circuit | |
KR20160089213A (en) | Switching mode power supply device | |
JP2016063607A (en) | Power supply unit, and control device thereof |
Legal Events
Date | Code | Title | Description |
---|---|---|---|
AS | Assignment |
Owner name: RICOH ELECTRONIC DEVICES CO., LTD., JAPAN Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:OGINO, YUUTA;SOHMA, SHOHTAROH;REEL/FRAME:041128/0397 Effective date: 20170127 |
|
STCF | Information on status: patent grant |
Free format text: PATENTED CASE |
|
MAFP | Maintenance fee payment |
Free format text: PAYMENT OF MAINTENANCE FEE, 4TH YEAR, LARGE ENTITY (ORIGINAL EVENT CODE: M1551); ENTITY STATUS OF PATENT OWNER: LARGE ENTITY Year of fee payment: 4 |
|
AS | Assignment |
Owner name: NEW JAPAN RADIO CO., LTD., JAPAN Free format text: MERGER;ASSIGNOR:RICOH ELECTRONIC DEVICES CO., LTD.;REEL/FRAME:059085/0740 Effective date: 20220101 |
|
AS | Assignment |
Owner name: NISSHINBO MICRO DEVICES INC., JAPAN Free format text: CHANGE OF NAME;ASSIGNOR:NEW JAPAN RADIO CO., LTD.;REEL/FRAME:059311/0446 Effective date: 20220101 |