TWI509975B - Modulation method for a single phase three-level converter - Google Patents
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一種轉換器之調變方法,特別是一種單相三階轉換器之調變方法。A modulation method of a converter, in particular, a modulation method of a single-phase three-step converter.
傳統單相全橋轉換器之架構如第1圖所示,係美國專利US7031176B2,該案採用傳統H型橋式結構(H Bridge),於直流電壓轉交流電壓(DC to AC)的電壓轉換時,其調變策略如第2圖所示,此方法主要是由載波與正弦波進行比較而取得脈衝寬度(PWM)方波調變。由第2圖可以很明顯地看出,在0°~360°區間中,開關均屬於全時且全壓切換。換言之,在每一個週期間有很高之切換次數,再以220VAC的系統換算之,每次開關的電壓差310V,因此高頻率切換下損失極高,效率不佳。The structure of the traditional single-phase full-bridge converter is shown in Figure 1, which is US patent US7031176B2. The case uses the traditional H-bridge structure (H Bridge) for voltage conversion from DC voltage to AC voltage. As shown in Fig. 2, the modulation strategy is mainly to obtain a pulse width (PWM) square wave modulation by comparing a carrier with a sine wave. It can be clearly seen from Fig. 2 that in the interval of 0°~360°, the switches are all full-time and full-voltage switching. In other words, there is a high number of switching times between each cycle, and then converted to a 220 VAC system, the voltage difference of each switch is 310V, so the loss is high under high frequency switching, and the efficiency is not good.
美國專利US20090244936A1中,亦如第3圖所示該方法是NPC三階控制策略之三相轉換器架構。In US Patent No. 20090244936A1, as shown in FIG. 3, the method is a three-phase converter architecture of an NPC third-order control strategy.
長久以來太陽能電池之能量密度與轉換效率都偏低,這特性限縮其商業用途。而太陽光電轉換器,在太陽能系統中屬於末端產品。常見的併網型太陽光電轉換器,其功能是將寶貴的太陽能模組所產生之直流電能轉換為交流電能饋送回電網。因此太陽光電轉換器被要求極高效率,而在此前提之下,電力品質控制卻依然必須維持在合理的規範之內。The energy density and conversion efficiency of solar cells have long been low, which limits their commercial use. The solar photoelectric converter is an end product in the solar system. A common grid-connected solar-to-electrical converter that converts the DC power generated by valuable solar modules into AC power and feeds it back into the grid. Therefore, solar photoelectric converters are required to be extremely efficient, and under this premise, power quality control must still be maintained within reasonable specifications.
本發明著重於分散式供電系統之效率提升,根據輸出電壓極性,輸出電流極性、1/2電壓點、經由線路操作模式之分析,製作電壓中間點嵌位(neutral point clamped,NPC)開關切換表。分析電路 等效特性化逐步化簡,達到降低開關切換次數之目的,意即減少損耗,提昇效率。然而其能量轉換功能並不能因為採用新的切換技術而犧牲。The invention focuses on the efficiency improvement of the distributed power supply system, and according to the output voltage polarity, the output current polarity, the 1/2 voltage point, and the analysis through the line operation mode, the voltage intermediate point clamped (NPC) switch switching table is fabricated. . Analysis circuit Equivalent characterization is gradually reduced to achieve the purpose of reducing the number of switching times, which means reducing losses and improving efficiency. However, its energy conversion function cannot be sacrificed due to the adoption of new switching techniques.
本發明調變方式所使用的模擬平台為T型中間點嵌位(T-type NPC)架構,如第4圖所示。與傳統半橋電路相較,中間點嵌位(neutral point clamped,NPC)半橋電路最大的優勢在於具有三階架構,相較傳統半橋電路只有二階架構,本發明可以直接運用到直流/交流轉換器系統中,可輸出至被動式負載或電網(Vgrid),俱高效率、高性能且經濟實用。The simulation platform used in the modulation mode of the present invention is a T-type intermediate point clamp (T-type NPC) architecture, as shown in FIG. Compared with the traditional half-bridge circuit, the biggest advantage of the neutral point clamped (NPC) half-bridge circuit is that it has a third-order architecture. Compared with the traditional half-bridge circuit, there is only a second-order architecture. The invention can be directly applied to DC/AC. In the converter system, it can be output to a passive load or grid (Vgrid), which is efficient, high performance and economical.
進行調變策略之設計首先假設本系統為理想平衡的結構且假設輸出交流電壓為AC220V/60Hz,故其峰值電壓為310Vdc,又直流電源(B1)=直流電源(B2)=1/2電壓=155Vdc。依據電流方向,輸出電壓極性以及1/2電壓分界點建立電路分析之條件。此處1/2電壓分界點是根據直流/交流轉換器之輸出AC1交流電壓源而言,在正半週期時+155V為1/2電壓分界點,在負半週期時-155V為1/2電壓分界點。然而,若當直流電源(B1)電壓不等於直流電源(B2)時,本系統不再用155V作為1/2電壓分界點。而是隨著直流電源(B1)及直流電源(B2)之電壓與輸出AC1交流電壓源進行動態比較而變動。在三階電壓源分別表示,正極性交流低電壓輸出0<VAC<B1、正極性交流高電壓輸出B1<VAC。為方便呈現將負極性電壓取絕對值表示為abs(VAC),據此負極性交流低電壓輸出0<abs(VAC)<B2、負極性交流高電壓輸B2<abs(VAC)。再加入線路中電感(L1)電流方向條件,即正極性電流與負極性電流,這三種條件的組合將形成八種狀態。這八種電路操作狀態若再以脈衝寬度調變(PWM)責任週期劃分,則形成每一圖框中2種電路開關型態。其中上半部屬於高脈衝寬度調變(PWM)責任週期(Duty-High),下半部屬於低脈衝寬度調變(PWM)責任週期(Duty-Low),合計總共形成16種電路。The design of the modulation strategy is first assumed that the system is an ideal balanced structure and the output AC voltage is assumed to be AC220V/60Hz, so the peak voltage is 310Vdc, and the DC power supply (B1)=DC power supply (B2)=1/2 voltage= 155Vdc. According to the current direction, the output voltage polarity and the 1/2 voltage demarcation point establish the conditions for circuit analysis. Here, the 1/2 voltage demarcation point is based on the AC/AC converter's output AC1 AC voltage source. In the positive half cycle, +155V is the 1/2 voltage demarcation point, and in the negative half cycle, the -155V is 1/2. Voltage demarcation point. However, if the DC power supply (B1) voltage is not equal to the DC power supply (B2), the system no longer uses 155V as the 1/2 voltage cut-off point. Instead, the voltages of the DC power supply (B1) and the DC power supply (B2) are dynamically compared with the output AC1 AC voltage source. The third-order voltage source indicates that the positive polarity AC low voltage output 0 < VAC < B1 and the positive polarity AC high voltage output B1 < VAC. For the sake of convenience, the absolute value of the negative polarity voltage is expressed as abs (VAC), whereby the negative polarity AC low voltage output 0 < abs (VAC) < B2, the negative polarity AC high voltage input B2 < abs (VAC). Then add the inductance (L1) current direction condition in the line, that is, the positive current and the negative current, and the combination of these three conditions will form eight states. If the eight circuit operating states are further divided by the pulse width modulation (PWM) duty cycle, two circuit switching patterns are formed in each frame. The upper half belongs to the high pulse width modulation (PWM) duty cycle (Duty-High), and the lower half belongs to the low pulse width modulation (PWM) duty cycle (Duty-Low), which collectively forms a total of 16 circuits.
表1為中間點嵌位(neutral point clamped,NPC)基本開關切換表表中(I++)表示正極性電流增加、(I+)表示正極性電流減少、表中(I--) 表示負極性電流增加、(I-)表示負極性電流減少。本發明直接以第一直流電源(B1)、第二直流電源(B2)與1/2輸出電壓比較,除應用於平衡系統之外。亦可實現於第一直流電源(B1)與第二直流電源(B2)電壓不同之不平衡系統。Table 1 is the intermediate point clamped (NPC) basic switch switching table (I++) indicating positive polarity current increase, (I+) indicating positive polarity current reduction, Table (I--) It indicates that the negative polarity current is increased, and (I-) indicates that the negative polarity current is decreased. The invention directly compares the first direct current power source (B1) and the second direct current power source (B2) with the 1/2 output voltage, except for being applied to the balance system. It is also possible to realize an unbalanced system in which the voltages of the first direct current power source (B1) and the second direct current power source (B2) are different.
本發明可用軟體或硬體方式實現,如第5圖所示虛線內為具體可實現方案之一,其系一控制器31,該方案使用電力電子模擬軟體PSIM驗證之後可產生如第6圖交流電壓輸出。而本範例之負載為一電阻。本發明一實施例,假設本系統為平衡的結構,係一種單相三階轉換器之調變方法,該調變方法包含下列步驟:使用一單相三階電路,經由一電感連結一交流電壓源的一端、以及一電容;以及使用一電壓中間點嵌位(neutral point clamped,NPC)開關切換表,控制該單相三階電路;其中,經由該電壓中間點嵌位(neutral point clamped,NPC)開關切換表,選擇該單相三階電路中電流的迴路,以降低該單相三階電路的開關切換頻率,提供低能量損耗的直流轉交流(DC to AC)轉換。若系統為不平衡,例如第一直流電源(B1)之端電壓不等於第二直流電源(B2)之端電壓。此時須比較第一直流電源(B1)與相對應極性之1/2電網電壓。方能決定操作步驟。The present invention can be implemented in a software or hardware manner. As shown in the dotted line in FIG. 5, it is one of the specific implementable schemes, which is a controller 31. After the scheme is verified by using the power electronic simulation software PSIM, the communication can be generated as shown in FIG. Voltage output. The load of this example is a resistor. According to an embodiment of the present invention, the system is a balanced structure, and is a modulation method of a single-phase three-step converter. The modulation method includes the following steps: using a single-phase third-order circuit to connect an AC voltage through an inductor. One end of the source, and a capacitor; and a single-phase third-order circuit is controlled using a voltage intermediate point clamped (NPC) switch switching table; wherein, through the voltage intermediate point clamped (NPC) The switch switching table selects the current loop of the single-phase third-order circuit to reduce the switching frequency of the single-phase third-order circuit and provide a DC to AC conversion with low energy loss. If the system is unbalanced, for example, the terminal voltage of the first DC power source (B1) is not equal to the terminal voltage of the second DC power source (B2). At this point, the first DC power supply (B1) must be compared to the 1/2 grid voltage of the corresponding polarity. Only then can you decide the steps.
Q1A‧‧‧Q1A開關Q1A‧‧‧Q1A switch
Q2A‧‧‧Q2A開關Q2A‧‧‧Q2A switch
Q2‧‧‧Q2開關Q2‧‧‧Q2 switch
Q1‧‧‧Q1開關Q1‧‧‧Q1 switch
Q3‧‧‧Q3開關Q3‧‧‧Q3 switch
Q4‧‧‧Q4開關Q4‧‧‧Q4 switch
L1‧‧‧電感L1‧‧‧Inductance
AC1‧‧‧交流電壓源AC1‧‧‧ AC voltage source
C1‧‧‧電容C1‧‧‧ capacitor
B1‧‧‧第一直流電源B1‧‧‧First DC power supply
B2‧‧‧第二直流電源B2‧‧‧second DC power supply
第1圖為習知技術結構圖。Figure 1 is a diagram showing a conventional technical structure.
第2圖為習知技術載波與正弦波進行比較而取得脈衝寬度(PWM)方波調變。Fig. 2 is a pulse width (PWM) square wave modulation obtained by comparing a conventional carrier with a sine wave.
第3圖為本發明的改變結構至全橋架構式意圖。Figure 3 is an illustration of the modified structure to full bridge architecture of the present invention.
第4圖為本發明的延伸中間點嵌位(neutral point clamped,NPC)之全橋架構與三相架構式意圖。Figure 4 is a schematic diagram of the full bridge architecture and three-phase architecture of the extended intermediate point clamped (NPC) of the present invention.
第5圖為本發明的中間點嵌位(neutral point clamped,NPC)控制方案範例說明圖。Fig. 5 is a diagram showing an example of a neutral point clamped (NPC) control scheme of the present invention.
第6圖為本發明的中間點嵌位(neutral point clamped,NPC)架構模擬狀態圖。Figure 6 is a simulation state diagram of a neutral point clamped (NPC) architecture of the present invention.
第7A~7H圖為本發明的16種迴路結構式意圖。Figures 7A-7H are diagrams of the 16 types of loop structures of the present invention.
本發明提供一實施例,假設本系統為平衡的結構,產生交流電壓源(AC1)輸出。如第7A圖~第7H圖所示,係一種單相三階轉換器之調變方法,其中,調變方法的步驟包含有:使用一單相三階電路,經由一電感(L1)連結一交流電壓源(AC1)的一端、以及一電容(C1);以及使用一電壓中間點嵌位(neutral point clamped,NPC)開關切換表,控制該單相三階電路;其中,經由該電壓中間點嵌位(neutral point clamped,NPC)開關切換表,選擇該單相三階電路中電流的迴路,以降低該單相三階電路的開關切換頻率,提供低能量損耗的直流轉交流(DC to AC)轉換。The present invention provides an embodiment in which the system is a balanced structure that produces an AC voltage source (AC1) output. As shown in FIG. 7A to FIG. 7H, a modulation method of a single-phase three-step converter, wherein the step of the modulation method includes: using a single-phase third-order circuit, connecting one through an inductor (L1) One end of an alternating voltage source (AC1) and a capacitor (C1); and a single phase third-order circuit is controlled using a voltage intermediate point clamped (NPC) switch switching table; wherein the intermediate point of the voltage is passed A neutral point clamped (NPC) switch switching table selects a current loop in the single-phase third-order circuit to reduce the switching frequency of the single-phase third-order circuit and provide a DC-AC with low energy loss (DC to AC) ) Conversion.
該單項三階電路,如第4圖所示,係包含有:一Q1A開關(Q1A)、一Q2A開關(Q2A)、一Q2開關(Q2)、一Q1開關、一Q3開關(Q3)、以及一Q4開關(Q4)。其中,Q1A開關(Q1A)的一端連接一第一直流電源(B1)的負端、以及一第二直流電源的正端;該Q2A開關(Q2A)的一端連接該Q1A開關(Q1A)的另一端;該Q2開關(Q2)的一端連接該第二直流電源(B2)的負端;該Q1開關的一端連接該第一直流電源(B1)的正端,該Q1開關的另一端,係分別連接該Q2A開關(Q2A)的另一端、該Q2開關(Q2)的另一端、以及該交流電壓源(AC1)的另一端;該Q3開關(Q3)的一端連接該第一直流電源(B1)的正端;以及該Q4開關(Q4)的一端連接該第二直流電源(B2)的負 端,該Q4開關(Q4)的一端連接該該Q3開關(Q3)的另一端、以及該電感(L1);其中,該第一直流電源(B1)、以及該第二直流電源(B2)係提供直流電壓,經由該單相三階轉換器,提供直流電壓轉換交流電壓至該交流電壓源(AC1);其中,該Q1A開關(Q1A)、該Q2A開關(Q2A)、該Q2開關(Q2)、該Q1開關、該Q3開關(Q3)、該Q4開關(Q4)係金屬氧化半導體(MOS)。The single third-order circuit, as shown in FIG. 4, includes: a Q1A switch (Q1A), a Q2A switch (Q2A), a Q2 switch (Q2), a Q1 switch, a Q3 switch (Q3), and A Q4 switch (Q4). Wherein, one end of the Q1A switch (Q1A) is connected to a negative end of the first DC power supply (B1) and a positive end of a second DC power supply; one end of the Q2A switch (Q2A) is connected to the other of the Q1A switch (Q1A) One end of the Q2 switch (Q2) is connected to the negative end of the second DC power supply (B2); one end of the Q1 switch is connected to the positive end of the first DC power supply (B1), and the other end of the Q1 switch is Connecting the other end of the Q2A switch (Q2A), the other end of the Q2 switch (Q2), and the other end of the AC voltage source (AC1); one end of the Q3 switch (Q3) is connected to the first DC power supply ( a positive end of B1); and one end of the Q4 switch (Q4) is connected to the negative of the second DC power supply (B2) End, the other end of the Q4 switch (Q4) is connected to the other end of the Q3 switch (Q3), and the inductor (L1); wherein the first DC power source (B1) and the second DC power source (B2) Providing a DC voltage, through which the DC voltage is converted to an AC voltage source (AC1) via the single-phase third-order converter; wherein the Q1A switch (Q1A), the Q2A switch (Q2A), and the Q2 switch (Q2) The Q1 switch, the Q3 switch (Q3), and the Q4 switch (Q4) are metal oxide semiconductors (MOS).
該電壓中間點嵌位(neutral point clamped,NPC)開關切換表的實施步驟詳細如下:第一步驟,如第7A圖所示,係該交流電壓源(AC1)為正極性而其端電壓低於第一直流電源(B1)電壓,且該電流為正極性;於脈衝寬度調變(PWM)致能,該Q3開關(Q3)導通、該Q2A開關(Q2A)導通,提供迴路使正極性電流增加(I++);於脈衝寬度調變(PWM)禁能,該Q3開關(Q3)導通,提供迴路使正極性電流降低(I+)。The implementation steps of the voltage intermediate point clamped (NPC) switch switching table are as follows: The first step, as shown in FIG. 7A, is that the AC voltage source (AC1) is positive and its terminal voltage is lower than The first DC power (B1) voltage, and the current is positive; in the pulse width modulation (PWM) enable, the Q3 switch (Q3) is turned on, the Q2A switch (Q2A) is turned on, and the circuit is provided to make the positive current Increase (I++); the pulse width modulation (PWM) disables, the Q3 switch (Q3) turns on, providing a loop to reduce the positive current (I+).
第二步驟,如第7B圖所示,係該交流電壓源(AC1)為正極性而其端電壓低於第一直流電源(B1)電壓,且該電流為負極性;於脈衝寬度調變(PWM)禁能,該Q3開關(Q3)導通、該Q1開關(Q1)導通,提供迴路使負極性電流增加(I--);於脈衝寬度調變(PWM)致能,該Q3開關(Q3)導通、該Q1A開關(Q1A)導通,提供迴路使負極性電流降低(I-)。The second step, as shown in FIG. 7B, is that the AC voltage source (AC1) is positive polarity and its terminal voltage is lower than the first DC power source (B1) voltage, and the current is negative polarity; (PWM) disable, the Q3 switch (Q3) is turned on, the Q1 switch (Q1) is turned on, and the loop is provided to increase the negative current (I--); the pulse width modulation (PWM) is enabled, the Q3 switch ( Q3) Conduction, the Q1A switch (Q1A) is turned on, and the circuit is provided to reduce the negative current (I-).
第三步驟,如第7C圖所示,係該交流電壓源(AC1)為正極性而其端電壓大於第一直流電源(B1)電壓,且該電流為正極性;於脈衝寬度調變(PWM)致能,該Q3開關(Q3)導通、該Q2開關(Q2)導通,提供迴路使正極性電流增加(I++);於脈衝寬度調變(PWM)禁能,該Q3開關(Q3)導通、該Q2A開關(Q2A)導通提供迴路使正極性電流降低(I+)。The third step, as shown in FIG. 7C, is that the AC voltage source (AC1) is positive polarity and its terminal voltage is greater than the first DC power source (B1) voltage, and the current is positive polarity; PWM) enable, the Q3 switch (Q3) is turned on, the Q2 switch (Q2) is turned on, and the loop is provided to increase the positive current (I++); the pulse width modulation (PWM) is disabled, and the Q3 switch (Q3) is turned on. The Q2A switch (Q2A) is turned on to provide a loop to reduce the positive current (I+).
第四步驟,如第7D圖所示,係該交流電壓源(AC1)為正極性而其端電壓大於第一直流電源(B1)電壓,且該電流為負極性;於脈衝寬度調變(PWM)禁能,該Q3開關(Q3)導通、該Q1A開關(Q1A)導通,提供迴路使負極性電流增加(I--);於脈衝寬度調變(PWM)致能,該Q3開關(Q3)導通,提供迴路使負極性電流降低(I-)。The fourth step, as shown in FIG. 7D, is that the AC voltage source (AC1) is positive polarity and its terminal voltage is greater than the first DC power source (B1) voltage, and the current is negative polarity; PWM) disable, the Q3 switch (Q3) is turned on, the Q1A switch (Q1A) is turned on, and the loop is provided to increase the negative current (I--); the pulse width modulation (PWM) is enabled, the Q3 switch (Q3) Turn on, providing a loop to reduce the negative current (I-).
第五步驟,如第7E圖所示,係該交流電壓源(AC1)為負極性而其端電壓絕對值低於第二直流電源(B2)電壓,且該電流為正極性;於脈衝寬度調變(PWM)致能,該Q4開關(Q4)導通、該Q2開關(Q2)導通、提供迴路使正極性電流增加(I++);於脈衝寬度調變(PWM)禁能,該Q4開關(Q4)導通、該Q2A開關(Q2A)導通,提供迴路使正極性電流降低(I+)。The fifth step, as shown in FIG. 7E, is that the AC voltage source (AC1) is negative polarity and the terminal voltage absolute value is lower than the second DC power source (B2) voltage, and the current is positive polarity; Variable (PWM) enable, the Q4 switch (Q4) is turned on, the Q2 switch (Q2) is turned on, the loop is provided to increase the positive current (I++), and the pulse width modulation (PWM) is disabled, the Q4 switch (Q4) The conduction, the Q2A switch (Q2A) is turned on, and the circuit is provided to reduce the positive current (I+).
第六步驟,如第7F圖所示,係該交流電壓源(AC1)為負極性而其端電壓絕對值低於第二直流電源(B2)電壓,且該電流為負極性;於脈衝寬度調變(PWM)禁能,該Q4開關(Q4)導通、該Q1A開關(Q1A)導通、提供迴路使負極性電流增加(I--);於脈衝寬度調變(PWM)致能,該Q4開關(Q4)導通,提供迴路使負極性電流降低(I-)。The sixth step, as shown in FIG. 7F, is that the AC voltage source (AC1) is negative polarity and the terminal voltage absolute value is lower than the second DC power source (B2) voltage, and the current is negative polarity; Variable (PWM) disable, the Q4 switch (Q4) is turned on, the Q1A switch (Q1A) is turned on, the loop is provided to increase the negative current (I--); the pulse width modulation (PWM) is enabled, the Q4 switch (Q4) is turned on, providing a loop to reduce the negative current (I-).
第七步驟,如第7G圖所示,係該交流電壓源(AC1)為負極性而其端電壓絕對值高於第二直流電源(B2)電壓,且該電流為正極性;於脈衝寬度調變(PWM)致能,該Q4開關(Q4)導通、該Q2A開關(Q2A)導通,提供迴路使正極性電流增加(I++);於脈衝寬度調變(PWM)禁能,該Q4開關(Q4)導通,提供迴路使正極性電流降低(I+)。The seventh step, as shown in FIG. 7G, is that the AC voltage source (AC1) is negative polarity and the terminal voltage absolute value is higher than the second DC power source (B2) voltage, and the current is positive polarity; Variable (PWM) enable, the Q4 switch (Q4) is turned on, the Q2A switch (Q2A) is turned on, and the loop is provided to increase the positive current (I++); the pulse width modulation (PWM) is disabled, the Q4 switch (Q4) Turn on, providing a loop to reduce the positive current (I+).
第八步驟,如第7H圖所示,係該交流電壓源(AC1)為負極性而其端電壓絕對值高於第二直流電源(B2)電壓,且該電流為負極性;於脈衝寬度調變(PWM)禁能,該Q4開關(Q4)導通、該Q1開關(Q1)導通,提供迴路使負極性電流增加(I--);於脈衝寬度調變(PWM)致能,該Q4開關(Q4)導通、該Q1A開關(Q1A)導通,提供迴路使負極性電流降低(I-)。The eighth step, as shown in FIG. 7H, is that the AC voltage source (AC1) is negative polarity and the absolute value of the terminal voltage is higher than the voltage of the second DC power source (B2), and the current is negative polarity; Variable (PWM) disable, the Q4 switch (Q4) is turned on, the Q1 switch (Q1) is turned on, and the loop is provided to increase the negative current (I--); the pulse width modulation (PWM) is enabled, the Q4 switch (Q4) is turned on, the Q1A switch (Q1A) is turned on, and a loop is provided to reduce the negative current (I-).
本實施中脈衝寬度調變(PWM)禁能或致能隨著控制方式之定義不同並非固定不變,其主要功能在於區分被控制的電流增加或降低,因此可以採用正邏輯、負邏輯、正邏輯與負邏輯混合使用。而電流方向若與直流電源之電壓之方向相反,表示功率因數不等於1,此時輸出端交流電源(AC1)將被負載端電網電壓(Vgrid)逆向對直流端輸電。此負載不限定為交流電網電源(Vgrid),亦可為被動性負載如純電阻等,此情況下該交流電源(AC1)即為本系統轉換後所產生之交流輸出。In this implementation, the pulse width modulation (PWM) disable or enable is not fixed with the definition of the control mode. Its main function is to distinguish the controlled current from increasing or decreasing. Therefore, positive logic, negative logic, and positive can be used. The logic is mixed with negative logic. If the direction of the current is opposite to the direction of the voltage of the DC power supply, it indicates that the power factor is not equal to 1, and the AC power supply (AC1) at the output will be reversely transmitted to the DC terminal by the load grid voltage (Vgrid). The load is not limited to the AC grid power supply (Vgrid), and may be a passive load such as a pure resistor. In this case, the AC power source (AC1) is the AC output generated after the system is converted.
以上所述,乃僅記載本發明為呈現解決問題所採用的技術手段之較佳實施方式或實施例而已,並非用來限定本發明專利實施之範圍。即凡與本發明專利申請範圍文義相符,或依本發明專利範圍所做的均等變化與修飾,皆為本發明專利範圍所涵蓋。The above description is only intended to describe the preferred embodiments or embodiments of the present invention, which are not intended to limit the scope of the invention. That is, the equivalent changes and modifications made in accordance with the scope of the patent application of the present invention or the scope of the invention are covered by the scope of the invention.
Q1A‧‧‧Q1A開關Q1A‧‧‧Q1A switch
Q2A‧‧‧Q2A開關Q2A‧‧‧Q2A switch
Q2‧‧‧Q2開關Q2‧‧‧Q2 switch
Q1‧‧‧Q1開關Q1‧‧‧Q1 switch
Q3‧‧‧Q3開關Q3‧‧‧Q3 switch
Q4‧‧‧Q4開關Q4‧‧‧Q4 switch
L1‧‧‧電感L1‧‧‧Inductance
AC1‧‧‧交流電壓源AC1‧‧‧ AC voltage source
C1‧‧‧電容C1‧‧‧ capacitor
B1‧‧‧第一直流電源B1‧‧‧First DC power supply
B2‧‧‧第二直流電源B2‧‧‧second DC power supply
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TW200425619A (en) * | 2003-05-07 | 2004-11-16 | Uis Abler Electronics Co Ltd | Bi-directional DC/DC power converter with a neutral point |
TW201304385A (en) * | 2011-07-13 | 2013-01-16 | Delta Electronics Inc | Inverting circuit |
CN103081333A (en) * | 2010-08-23 | 2013-05-01 | 东芝三菱电机产业系统株式会社 | Electricity conversion device |
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CN103337962A (en) * | 2013-06-20 | 2013-10-02 | 南京工程学院 | Offshore wind plant DC converge used three-level converter and control method thereof |
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TW200425619A (en) * | 2003-05-07 | 2004-11-16 | Uis Abler Electronics Co Ltd | Bi-directional DC/DC power converter with a neutral point |
CN103081333A (en) * | 2010-08-23 | 2013-05-01 | 东芝三菱电机产业系统株式会社 | Electricity conversion device |
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TW201322613A (en) * | 2011-11-30 | 2013-06-01 | Ind Tech Res Inst | A method for controlling hybrid multilevel DC/AC inverter apparatus |
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