201232989 六、發明說明： 【發明所屬之技術領域】 本發明關於對二次電池進行充電的共振型充電裝 搭載其之車輛。 【先前技術】 近年來隨著地球環保意識之局漲，高效率自 動車（hybrid car)之普及被進展著。複合型自動車具有 行走馬達驅動用之二次電池。由商用交流電源對該二次電 池充電可以改善複合型自動車之燃料費。欲由商用電源對 二次電池，以更少電力安全進行充電，需要轉換效率高、 而且絕緣型之DC-DC轉換器。藉由降低整流二極體之耐 壓，達成轉換效率之提升的絕緣型DC-DC轉換器，係揭 示於專利文獻1。 另外，專利文獻2揭示，在功率因子改善轉換器之後 段連接著共振型轉換器的電源裝置，係於廣電流範圍追求 高效率動作之目標的電源裝置。 〔習知技術文獻〕 〔專利文獻〕 專利文獻1 :專利第40 1 3 995號公報 專利文獻2:特開2005-65395號公報 【發明內容】 (發明所欲解決之課題） 201232989 通常欲達成絕緣型DC-DC轉換器之高效率時，降低 變壓器二次繞線之電壓電流之整流二極體之耐壓乃有效者 。但是，專利文獻1揭示之習知DC-DC轉換器，在進行 行走馬達驅動用二次電池之充電而獲得高的輸出電壓時， 需要提高二極體之耐壓，而有礙高效率之達成。另外，專 利文獻2揭示之習知電源裝置，可於較廣負荷電流範圍實 現高效率，但是，並非於較廣輸出電壓範圍可達成高效率 者。 本發明目的在於提供共振型充電裝置及車輛，其可以 高效率由交流電源針對電壓較高、電壓範圍較廣的行走馬 達驅動用二次電池進行充電。 (用以解決課題的手段） 爲解決上述問題，本發明之共振型充電裝置，係連接 於交流電源與搭載於車輛的二次電池之間，由上述交流電 源對上述二次電池供給電力者；其特徵爲：具備：AC-DC 轉換器，其被連接於上述交流電源，輸入來自上述交流電 源之電力而輸出直流之連結電壓；DC-DC轉換器，其對上 述二次電池實施絕緣之同時，由上述連結電壓對其進行電 力之供給；及控制手段，其用於控制上述AC-DC轉換器 及DC-DC轉換器；上述DC-DC轉換器爲共振型轉換器， 具備：開關電路，於直流端子間被連接著上述連結電壓， 於交流端子間輸出矩形波電壓；整流電路，用於對由交流 端子間輸入之電流實施整流，而輸出至由上述二次電池與 -6- 201232989 平滑電容器並聯連接而成的直流端子間；1次繞線，被連 接於上述開關電路之交流端子間；2次繞線，被連接於上 述整流電路之交流端子間；變壓器，用於對上述1次繞線 與2次繞線實施磁性耦合；共振電容器及共振電感器，其 被串聯連接於上述1次繞線及/或上述2次繞線；上述控 制手段，係以變化上述矩形波電壓之頻率的方式，針對上 述開關電路具備之開關元件進行控制。 本發明之車輛，其特徵爲：具備：連接於交流電源的 連接器；動力用馬達；二次電池，其對上述動力用馬達供 給電力；及共振型充電裝置，被連接於上述連接器與上述 二次電池之間，由上述連接器所連接之上述交流電源對上 述二次電池供給電力；上述共振型充電裝置，係具備： AC_ DC轉換器，用於輸入來自.上述交流電源之電力而輸出 直流之連結電壓；DC-DC轉換器，其對上述二次電池實施 絕緣之同時，由上述連結電壓對其進行電力之供給；及控 _制手段，其用於控制上述AC-DC轉換器及DC-DC轉換器 :上述DC-DC轉換器被設爲共振型轉換器，具備：開關 電路，於直流端子間被連接著上述連結電壓，於交流端子 間輸出矩形波電壓；整流電路，用於對由交流端子間輸入 之電流實施整流，而輸出至由上述二次電池與平滑電容器 並聯連接而成的直流端子間；1次繞線，被連接於上述開 關電路之交流端子間；2次繞線，被連接於上述整流電路 之交流端子間；變壓器，用於對上述1次繞線與2次繞線 實施磁性耦合；共振電容器及共振電感器，其被串聯連接 -7- 201232989 於上述1次繞線及/或上述2次繞線；上 以變化上述矩形波電壓之頻率的方式’針 具備之開關元件進行控制。 【實施方式】 參照圖面詳細說明本發明實施形態。 (第1實施例） 圖1表示本發明第1實施例之共振型 成電路圖。該共振型充電裝置1，係連接 搭載於車輛的二次電池6之間，由交流電 6供給電力。交流電源5可使用商用電源 電源可以供給穩定之電力，改善燃料費。 商用電源，亦可使用例如太陽光發電或風 置或通常之發電機。 該共振型充電裝置1具備：AC-DC _ 交流電源5之電力而輸出直流之連結電壓 3，其對二次電池6實施絕緣之同時，由 電力之供給；及控制手段4，其控制彼等辜 AC-DC轉換器2，係藉由橋式連接之 〜D14，實施交流電源5之電壓之全波整 中，整流二極體D11與D12，整流二極體 別被串聯連接之後，分別被並聯連接而成 聯連接之整流二極體D11與D12之間的 述控制手段，係 對上述開關電路 充電裝置1之構 於交流電源5與 源5對二次電池 。藉由使用商用 但是，不限定於 力發電等發電裝 換器2，其輸入 ;DC-DC轉換器 該連結電壓進行 I換器。 整流二極體D 1 1 流。本實施形態 D13與D14分 爲橋式連接，串 連接點，以及串 -8- 201232989 聯連接之整流二極體D13與D14之間的連接點係 流端子，串聯連接之整流二極體D11與D12，以及 接之整流二極體D13與D14之兩端部的連接點係 流端子。交流電源5被連接於該交流端子。 全波整流後之電壓，係輸入至由連接於直流端 滑電感器L1、升壓開關元件Q10、升壓二極體D1C 電容器C1構成之升壓截波（chopper)電路。連結 C1之兩端間設爲連結電壓。控制手段4具備：功 改善控制，用於將交流電源5之輸入電流控制成爲 電源5之電壓槪略相似的正弦波狀；及連結電壓協 ，其伴隨二次電池6之電壓上升而使連結電壓上升 DC-DC轉換器3，係具備：共振電容器Crl與 感器Lrl串聯連接的繞線N1;和繞線N2產生磁性 變壓器T1。另外，開關元件Q1〜Q4爲由第1開關 第2開關腳部並聯連接而成的全橋式連接，該第1 部係將第1開關元件之開關元件Q1與第2開關元 關元件Q2串聯連接而成，第2開關腳部係將第3 件之開關元件Q3與第4開關元件之開關元件Q4 接而成。以第1開關腳部之兩端間作爲直流端子間 關元件Q 1、Q2之串聯連接點和開關元件Q3、Q4 連接點之間作爲交流端子間。 藉由橋式連接之開關元件Q1〜Q4，使由直流 輸入之連結電壓而產生之矩形波電壓，施加於交流 之共振電容器Crl與共振電感器Lrl與繞線N1之 成爲交 串聯連. 成爲直 子的平 、連結 電容器 率因子 和交流 調控制 〇 共振電 稱合之 腳部與 開關腳 件之開 開關元 串聯連 ，以開 之串聯 端子間 端子間 串聯連 -9- 201232989 接體，使共振電流流入繞線N1 ’使繞線N2感應之電流藉 由橋式連接之二極體D21〜D24實施整流而對平滑電容器 C2及二次電池6進行充電。二極體D21〜D24構成之整流 電路，係將第1二極體腳部與第2二極體腳部並聯連接而 成，該第1二極體腳部，係將第1二極體之二極體D2 1、 第2二極體之二極體D22串聯連接而成，第2二極體腳部 ，係將第3二極體之二極體D23、第4二極體之二極體 D24串聯連接而成。以第1二極體腳部之兩端間作爲直流 端子間，而連接於平滑電容器C2及二次電池6。另外， 以二極體D21、D22之串聯連接點，和二極體D23、D24 之串聯連接點之間爲交流端子間，而連接於繞線N2。 本實施形態中，於1次繞線N1設置共振電容器Crl 與共振電感器Lrl，但亦可考慮電路設計條件或限制等， 而設於2次繞線N2，或設於1次繞線N1與2次繞線N2 之兩者。 於開關元件Q1〜Q4分別被連接逆並聯二極體D1〜 D4。其中，使用MOSFET作爲開關元件Q1〜Q4時，可以 利用MOSFET之寄生二極體作爲逆並聯連接之二極體D1 〜D4，藉由如此地具備有逆並聯二極體D1〜D4，可形成良 好的共振型充電裝置。 藉由控制手段4對升壓開關元件Q 1 〇及開關元件Q 1 〜Q4進行控制。於控制手段4被連接：檢測輸入電壓的 電壓感測器2 1 ;檢測連結電壓的電壓感測器22 ;檢測二 次電池之電壓、亦即’輸出電壓的電壓感測器2 3 ;檢測來 -10- 201232989 自交流電源5之輸入電流的電流感測器24 ;及檢測對二次 電池之輸出電流的電流感測器25。 參照圖2說明AC-DC轉換器2之電路動作。於此說 明交流電源5之電壓爲1極性之情況。交流電源5之電壓 爲逆極性之動作可以容易。另外’圖2A、2B分別表示模 態a、模態b之電路動作。 (模態a ) 於模態a，升壓開關元件Q1 〇設爲ON狀態。交流電 源5之電壓施加於平滑電感器L1，交流電源5之能量被 儲存於平滑電感器L1。 (模態b ) 升壓開關元件Q10設爲OFF時，成爲模態b之狀態 。於模態b，儲存於平滑電感器L1的能量會介由升壓二 極體D10放出至連結電容器C1。 以下重複模態a及模態b。 以下參照圖3A〜3D說明DC-DC轉換器3之電路動作 。圖3 A〜3 D分別表示模態A〜D之電路動作。 (模態A ) 於模態A，開關元件Q1、Q4爲ON之狀態。共振電 容器Crl與共振電感器Lrl產生之共振電流係由連結電容 器C 1流向繞線N1。繞線N 2感應之電流，係介由二極體 -11 - 201232989 D21、D24流向輸出。 (模態B ) 電荷儲存於共振電容器Crl，共振電容器Crl與共振電 感器Lr 1產生之共振電流流入結束後，成爲模態B。於模 態B，變壓器T1之激發電流流入繞線N1。繞線N2之電 壓，係較輸出之平滑電容器C2之電壓低，電流未流入繞 線N2。又’於模態A ’共振電流流入結束前設定開關元 件Ql、Q4成爲OFF時，可省略模態b。 (模態C ) 設定開關元件Ql、Q4成爲OFF時，成爲模態c之狀 態。於模態C，流入開關元件Q1、Q4的電流，係流入逆 並聯二極體D2、D3，流入連結電容器C 1。此時，設定開 關元件Q2、Q3成爲ON。 (模態D ) 繞線N1之電流反轉時’成爲模態D。模態D爲模態 A之對稱動作。以下，模態B、C之對稱動作之後回至模 態A。 如上述說明，於該共振型充電裝置丨’係將DC_DC轉 換器3設爲共振型轉換器，施加於二極體D2 1〜D24之電 壓，會被輸出之平滑電容器C2之電壓箝位。因此’即使 二次電池6之電壓高時，二極體D21〜D24亦可使用耐壓 -12 - 201232989 較低、順向壓降低的二極體，可以減少損失，有利於高效 率化。 於DC-DC轉換器3之輸出端、亦即平滑電容器C2與 二次電池6之間，欲減低漣波電流時可插入由電感器與電 容器構成之LC濾波器。但是，於DC-DC轉換器3之後段 ，不插入具備截波電路（chopper )等電流控制機能的轉 換器而連接至二次電池6。因此，控制手段4，欲對電壓 會依充電狀態而變的二次電池充電時，具備對DC-DC轉 換器3之輸出進行定電壓定電流控制之機能。DC-DC轉換 器3爲共振型器轉換器可控制開關元件Q 1〜Q4之開關頻 率而控制輸出。 由商用電源對車輛之二次電池充電時，通常商用電源 能供給之電流或電力有限制。控制手段4，係具備以可於 短時間進行二次電池6之充電的方式，在二次電池6之電 壓低於充電終了之電壓時，將交流電源5輸入之電流或電 力控制成爲設定値之機能。於此情況，DC-DC轉換器3之 輸出電力係槪略被維持於一定。 圖4表示連結電壓爲一定時之開關頻率fsw與輸出電 力Pout、輸出電壓Vout、輸出電流lout之關係。連結電 壓及輸出電力被維持一定時，輸出電壓低、輸出電流大時 ，開關頻率變高，反之，輸出電壓高、輸出電流小時，開 關頻率變低。共振型轉換器，在開關頻率太高或太低時效 率降低乃多數之情況，因此較好是於效率高的中間之開關 頻率動作。 13- 201232989 圖5〜7表示二次電池6之充電中之輸出電壓Vout、 連結電壓Vlink、輸出電力Pout、輸出電流lout、開關頻 率fsw、效率7?之隨時間Time之變化。 於圖5，連結電壓Vlink被維持於較低値。隨時間經 過，輸出電壓Vout上升，開關頻率fsw變爲太低而使效 率7?降低。 於圖6，連結電壓Vlink被維持於較高値。在接近充 電開始之期間，輸出電壓Vout低，開關頻率fsw變爲太 高而使效率7?降低。 於共振型充電裝置1具備藉由二次電池6之電壓來控 制連結電壓的連結電壓協調控制。於圖7，係以效率變高 的方式保有開關頻率fsw，因此隨輸出電壓Vout之上升而 使連結電壓Vlink上升。 圖8表示由輸出電壓Vout決定連結電壓Vlink之方 法。於輸出電壓Vout之各條件，以使效率77變高的方式 決定連結電壓Vlink即可。 但是，AC-DC轉換器2之電路構成如上述說明成爲升 壓截波器，因此無法將連結電壓設爲小於交流電源5之電 壓振幅。因此，連結電壓協調控制之連結電壓之可變範圍 ，槪略爲交流電源5之電壓振幅成爲下限。另外，基於連 結電容器C 1等電路元件之耐壓或壽命觀點，亦有於連結 電壓之可變範圍設定上限。圖9表示輸出電壓Vout與連 結電壓Vlink之關係。其中VlinkC爲效率變高之連結電 壓，VlinlcH爲連結電壓之上限，VlinkL爲連結電壓之下 -14- 201232989 限。 當然，交流電源5之電壓與二次電池6之電壓同時爲 低時，藉由降低連結電壓等方法，簡單實施連結電壓協調 控制亦可獲得效率提升效果。 如上述說明，於共振型充電裝置1，DC-DC轉換器3 之電路方式係採用共振型轉換器，藉由對其實施定電壓定 電流控制而可以高效率進行二次電池6之充電。另外，爲 使共振型轉換器具有之高效率發揮最大，而具備連結電壓 協調控制。 (第2實施例） 圖10表示本發明第2實施例之共振型充電裝置11之 構成電路圖該共振型充電裝置11，係和第1實施例之共 振型充電裝置1同樣，由交流電源5對二次電池6供給電 力。 該共振型充電裝置11具備：AC-DC轉換器12，其輸 入交流電源5之電力而輸出直流之連結電壓；DC-DC轉換 器13，其對二次電池6實施絕緣之同時，由該連結電壓進 行電力之供給；及控制手段1 4，其控制彼等轉換器。 於AC-DC轉換器12，係使第1實施例之AC-DC轉換 器2中之升壓截波電路，構成爲平滑電感器L2、降壓開 關元件Q5、降壓二極體D5、升壓開關元件Q6、升壓二極 體D6、及連結電容器C1構成之Η橋接電路，此點爲不同 。另外，具備由濾波電感器L3及濾波電容器C3構成之 -15- 201232989 LC濾波器。 於橋式連接之整流二極體Dll〜D14之直流端子間被 連接濾波電感器L3及濾波電容器C3。於濾波電容器C3 之兩端間串聯連接著降壓開關元件Q5及降壓二極體D5 ’ 於降壓二極體D5之兩端間串聯連接著平滑電感器L2及升 壓開關元件Q6。於升壓開關元件Q6之兩端間串聯連接著 升壓二極體D6及連結電容器C1。 和第I實施例之DC-DC轉換器3比較’ DC-DC轉換 器13之不同點在於，將共振電容器Crl設爲共振電容器 Crll、Crl2，將具備全橋式連接之逆並聯二極體D1〜D4 的開關元件Q 1〜Q4之中，和開關元件Q3、Q4逆並聯連 接之二極體D3、D4，替換爲共振電容器Crll、Crl2而設 爲半橋接電路，以及將橋式連接之二極體D21〜D24之中 之二極體D23、D24分別替換爲平滑電容器C21、C22。 亦即，DC-DC轉換器1 3之開關電路，係將第1開關 元件之開關元件Q1與第2開關元件之開關元件Q2串聯 連接而成第1開關腳部，將第1共振電容器之共振電容器 Cr 11與第2共振電容器之共振電容器Crl2串聯連接而成 共振電容器腳部，將該第1開關腳部與共振電容器腳部予 以並聯連接。於該開關電路，係以第1開關腳部之兩端間 作爲直流端子間，以開關元件Q 1、Q2之串聯連接點和共 振電容器Crl 1、Crl2之串聯連接點之間作爲交流端子間 〇 DC-DC $專換器13之整流電路，係將第1二極體之二 -16- 201232989 極體D21與第2二極體之二極體D22串聯連接而成第1 二極體腳部，將第1分壓電容器之平滑電容器C21與第2 分壓電容器之平滑電容器C22串聯連接而成分壓電容器腳 部，將該第1二極體腳部與分壓電容器腳部予以並聯連接 。於該整流電路，係以第1二極體腳部之兩端間作爲直流 端子間，以二極體D2 1、D22之串聯連接點和平滑電容器 C2 1、C22之串聯連接點之間作爲交流端子間》 降壓開關元件Q5、升壓開關元件Q6、開關元件Q1、 Q2係藉由控制手段1 4實施控制。於控制手段1 4，係和第 1實施例之共振型充電裝置1同樣，連接著電壓感測器21 〜23、電流感測器24、25。和第1實施例之控制手段4同 樣，控制手段1 4具備功率因子改善控制或連結電壓協調 控制、定電壓定電流控制等。 於共振型充電裝置11，於AC-DC轉換器12係如上述 說明採用Η橋接電路，藉由切換降壓開關元件Q5，可將 連結電壓設爲小於交流電源5之電壓振幅。因此，相較於 第1實施例之共振型充電裝置1可以更擴大連結電壓之可 變範圍，可以更高效率進行二次電池6之充電。另外，於 DC-DC轉換器13採用半橋接電路，可以減少開關元件及 二極體之元件點數。 (第3實施例） 圖11表示採用本發明共振型充電裝置1的電氣自動 車1 1 0之電源系統槪要之構成圖。共振型充電裝置1係連 -17- 201232989 接於，連接於交流電源109的即插式充電連接器（plug-in system connector) 108，及二次電池 105，於二次電池 105連接著DC-DC轉換器102，DC-DC轉換器102則對動 力用馬達104之驅動用的變頻器（inverter ) 103供給電力 。另外，於二次電池1〇5連接著DC-DC轉換器100，DC-DC轉換器100則對連接著電裝機器101的補機電池106 供給電力；以及連接著急速充電連接器107，急速充電連 接器107則連接於急速充電器等外部直流電源，而對二次 電池105進行充電。 共振型充電裝置1，係使用連接於即插式充電連接器 108之交流電源109之電力對二次電池105進行充電。 依據第3實施例，藉由使用本發明之共振型充電裝置 1，可由商用電源對搭載於車輛的動力用二次電池進行高 效率充電。 本發明之共振型充電裝置1亦適用複合型自動車（ hybrid car)。 (發明效果） 依據本發明提供之共振型充電裝置及車輛，可以由交 流電源高效率地針對電壓較高、電壓範圍較廣的二次電池 進行充電。 【圖式簡單說.明】 圖1表示第1實施例之共振型充電裝置1之構成電路 -18- 201232989 圖。 圖2A、2B表示第1實施例之AC-DC轉換器2之電路 動作說明圖。 圖3 A〜3D表示第1實施例之DC-DC轉換器3之電路 動作說明圖。 圖4表示第1實施例之DC-DC轉換器3之特性說明 圖。 圖5表示第1實施例之共振型充電裝置1之充電動作 說明圖。 圖6表示第1實施例之共振型充電裝置1之充電動作 說明圖。 圖7表示第1實施例之共振型充電裝置1之充電動作 說明圖。 圖8表示第1實施例之共振型充電裝置1之特性說明 圖。 圖9表示第1實施例之共振型充電裝置1之連結電壓 之決定方式說明圖。 圖10表示本發明第2實施例之共振型充電裝置11之 構成電路圖。 圖11表示採用本發明共振型充電裝置的電氣自動車 之電源系統槪要之構成圖。 【主要元件符號說明】 1、11:共振型充電裝置 -19- 201232989 2、 12 : AC-DC 轉換器 3、 13、100、102 ： DC-DC 轉換器 4、 1 4 :控制手段 5、 1 0 9 :交流電源 6、 1 0 5 :二次電池 2 1〜2 3 :電壓感測器 24、25 :電流感測器 101 :電裝機器 1 03 :變頻器 1 〇 4 :動力用馬達 106 :補機電池 107:急速充電連接器 108:即插式充電連接器 Π0 :電氣自動車 LI、L2 :平滑電感器 L3 :濾波電感器 L r 1 :共振電感器 C 1 :連結電容器 C2、C21、C22:平滑電容器 C 3 :濾波電容器201232989 VI. [Technical Field] The present invention relates to a vehicle in which a resonance type charging device for charging a secondary battery is mounted. [Prior Art] In recent years, as the global environmental awareness has risen, the popularity of high-efficiency hybrid cars has progressed. The hybrid automatic vehicle has a secondary battery for driving the traveling motor. Charging the secondary battery from a commercial AC power source can improve the fuel cost of the hybrid automatic vehicle. In order to charge a secondary battery from a commercial power source with less power, it is necessary to convert a highly efficient and insulated DC-DC converter. An insulated DC-DC converter which achieves an improvement in conversion efficiency by reducing the withstand voltage of the rectifying diode is disclosed in Patent Document 1. Further, Patent Document 2 discloses that a power supply device in which a resonance type converter is connected in the subsequent stage of a power factor improving converter is a power supply device that pursues a high-efficiency operation in a wide current range. [PRIOR ART DOCUMENT] [Patent Document] Patent Document 1: Patent No. 40 1 3 995 Patent Document 2: JP-A-2005-65395 [Summary of the Invention] (Invention) When the high efficiency of the DC-DC converter is used, it is effective to reduce the withstand voltage of the rectifying diode of the voltage and current of the secondary winding of the transformer. However, in the conventional DC-DC converter disclosed in Patent Document 1, when a high output voltage is obtained by charging a secondary battery for driving a traveling motor, it is necessary to increase the withstand voltage of the diode, which hinders the achievement of high efficiency. . Further, the conventional power supply device disclosed in Patent Document 2 can achieve high efficiency over a wide range of load currents, but it is not possible to achieve high efficiency over a wide range of output voltages. An object of the present invention is to provide a resonance type charging device and a vehicle which can charge a secondary battery for traveling motor drive having a high voltage and a wide voltage range from an AC power source with high efficiency. (Means for Solving the Problem) In order to solve the above problems, the resonance type charging device of the present invention is connected between an AC power source and a secondary battery mounted on a vehicle, and the AC power source supplies power to the secondary battery; The present invention is characterized in that it includes an AC-DC converter connected to the AC power source, and inputs a power from the AC power source to output a DC connection voltage, and a DC-DC converter that insulates the secondary battery And supplying the electric power by the connection voltage; and controlling means for controlling the AC-DC converter and the DC-DC converter; wherein the DC-DC converter is a resonance type converter, and includes: a switching circuit; The connection voltage is connected between the DC terminals, and a rectangular wave voltage is output between the AC terminals; and a rectifier circuit for rectifying the current input between the AC terminals and outputting the smoothing to the secondary battery and the -6-201232989 The capacitors are connected in parallel between the DC terminals; the primary winding is connected between the AC terminals of the above switching circuit; the secondary winding is connected to the upper a transformer between the alternating current terminals; a transformer for magnetically coupling the primary winding and the secondary winding; a resonant capacitor and a resonant inductor connected in series to the primary winding and/or the second winding The control means controls the switching element included in the switching circuit so as to change the frequency of the rectangular wave voltage. A vehicle according to the present invention includes: a connector connected to an AC power source; a power motor; a secondary battery that supplies electric power to the power motor; and a resonance type charging device that is connected to the connector and the The secondary battery is supplied with electric power to the secondary battery via the AC power source connected to the connector, and the resonance type charging device includes an AC_DC converter for inputting power from the AC power source. a DC-DC converter, which supplies the power to the secondary battery while being insulated by the connection voltage; and a control means for controlling the AC-DC converter and DC-DC converter: The DC-DC converter is a resonance type converter, and includes a switching circuit that is connected to the connection voltage between the DC terminals, and outputs a rectangular wave voltage between the AC terminals; and a rectifier circuit for Rectifying the current input between the AC terminals, and outputting to the DC terminal formed by connecting the above secondary battery and the smoothing capacitor in parallel; a line connected between the alternating current terminals of the switching circuit; a secondary winding connected between the alternating current terminals of the rectifier circuit; a transformer for magnetically coupling the primary winding and the secondary winding; the resonant capacitor And a resonant inductor that is connected in series to -7-201232989 for the first winding and/or the second winding; and is controlled by a switching element provided by the needle in such a manner as to change the frequency of the rectangular wave voltage. [Embodiment] Embodiments of the present invention will be described in detail with reference to the drawings. (First Embodiment) Fig. 1 is a circuit diagram showing a resonance type of a first embodiment of the present invention. The resonance type charging device 1 is connected between the secondary batteries 6 mounted on the vehicle, and is supplied with electric power by the alternating current 6. The AC power supply 5 can use a commercial power supply to supply stable power and improve fuel costs. Commercial power sources can also use, for example, solar power or wind or conventional generators. The resonance type charging device 1 includes: AC-DC _ AC power source 5, and outputs a DC connection voltage 3, which is insulated from the secondary battery 6 and supplied by electric power; and a control means 4 that controls them The 辜AC-DC converter 2 is connected to the D14 of the bridge type by the bridge type, and the rectifying diodes D11 and D12 are connected, and the rectifying diodes are connected in series, respectively. The control means between the rectifying diodes D11 and D12 connected in parallel is connected to the alternating current source 5 and the source 5 pair of secondary batteries. However, it is not limited to the power generation converter 2 such as power generation, and its input is used; the DC-DC converter connects the voltage to the converter. Rectifier diode D 1 1 flow. In this embodiment, D13 and D14 are divided into a bridge connection, a series connection point, and a connection point system terminal between the rectifying diodes D13 and D14 of the series -8-201232989, and the rectifying diode D11 connected in series and D12, and a connection point of the connection point of the two ends of the rectifying diodes D13 and D14. The AC power source 5 is connected to the AC terminal. The full-wave rectified voltage is input to a boost chopper circuit composed of a DC-side slip inductor L1, a boost switching element Q10, and a step-up diode D1C capacitor C1. The connection voltage is set between the two ends of the connection C1. The control means 4 includes: a power improvement control for controlling the input current of the AC power source 5 to be a sinusoidal waveform in which the voltage of the power source 5 is slightly similar; and a connection voltage association which causes the voltage to be connected with the voltage rise of the secondary battery 6 The rising DC-DC converter 3 includes a winding N1 in which the resonant capacitor Cr1 and the sensor Lrl are connected in series, and a winding N2 to generate a magnetic transformer T1. Further, the switching elements Q1 to Q4 are a full-bridge connection in which the first switch second switch leg is connected in parallel, and the first portion connects the switching element Q1 of the first switching element and the second switching element Q2 in series. The second switch leg is formed by connecting the switching element Q3 of the third element and the switching element Q4 of the fourth switching element. Between the two ends of the first switch leg, the series connection point of the DC terminal inter-contact elements Q1 and Q2 and the connection point of the switching elements Q3 and Q4 are used as the AC terminal. By means of the bridge-connected switching elements Q1 to Q4, the rectangular wave voltage generated by the DC input voltage is applied to the AC resonant capacitor Cr1 and the resonant inductor Lrl and the winding N1 in series. The flat and the connection capacitor rate factor and the AC modulation control 〇 resonance electric weighing of the foot and the opening and closing of the switch foot are connected in series, and the series connection between the terminals of the series terminal is connected -9-201232989 to make the resonant current The current flowing into the winding N1' causes the current induced by the winding N2 to be rectified by the bridge-connected diodes D21 to D24 to charge the smoothing capacitor C2 and the secondary battery 6. The rectifier circuit composed of the diodes D21 to D24 is formed by connecting the first diode body portion and the second diode body portion in parallel, and the first diode body portion is the first diode body. The diode D2 1 and the second diode D22 of the second diode are connected in series, and the second diode body is a diode of the third diode D23 and the second diode. The body D24 is connected in series. The smoothing capacitor C2 and the secondary battery 6 are connected between the two ends of the first diode body as a DC terminal. Further, the series connection point of the diodes D21 and D22 and the series connection point of the diodes D23 and D24 are connected between the alternating current terminals and connected to the winding N2. In the present embodiment, the resonant capacitor Cr1 and the resonant inductor Lrl are provided in the primary winding N1, but may be provided in the secondary winding N2 or in the primary winding N1 in consideration of circuit design conditions or restrictions. Two windings N2. The anti-parallel diodes D1 to D4 are connected to the switching elements Q1 to Q4, respectively. When the MOSFET is used as the switching elements Q1 to Q4, the parasitic diode of the MOSFET can be used as the diodes D1 to D4 connected in antiparallel, and the antiparallel diodes D1 to D4 can be formed in this manner. Resonant type charging device. The boosting switching element Q 1 〇 and the switching elements Q 1 to Q4 are controlled by the control means 4. The control means 4 is connected: a voltage sensor 2 1 for detecting an input voltage; a voltage sensor 22 for detecting a connection voltage; and a voltage sensor 2 for detecting a voltage of the secondary battery, that is, an output voltage; -10- 201232989 Current sensor 24 for input current from AC power source 5; and current sensor 25 for detecting output current to secondary battery. The circuit operation of the AC-DC converter 2 will be described with reference to Fig. 2 . Here, the case where the voltage of the AC power source 5 is one polarity is described. The voltage of the AC power source 5 can be easily reversed. Further, Figs. 2A and 2B show circuit operations of mode a and mode b, respectively. (Mode a) In mode a, boost switching element Q1 〇 is set to the ON state. The voltage of the alternating current source 5 is applied to the smoothing inductor L1, and the energy of the alternating current source 5 is stored in the smoothing inductor L1. (Mode b) When the boost switching element Q10 is turned OFF, it becomes the state of the modal b. In mode b, the energy stored in the smoothing inductor L1 is discharged to the junction capacitor C1 via the boosting diode D10. The modal a and the modal b are repeated below. The circuit operation of the DC-DC converter 3 will be described below with reference to Figs. 3A to 3D. 3A to 3D show the circuit operations of the modes A to D, respectively. (Mode A) In the mode A, the switching elements Q1 and Q4 are in the ON state. The resonant current generated by the resonant capacitor Crl and the resonant inductor Lrl flows from the connecting capacitor C1 to the winding N1. The current induced by the winding N 2 is output to the output through the diode -11 - 201232989 D21, D24. (Modal B) The electric charge is stored in the resonance capacitor Crl, and the resonant current generated by the resonant capacitor Cr1 and the resonant inductor Lr1 is completed, and becomes the modal B. In mode B, the excitation current of the transformer T1 flows into the winding N1. The voltage of the winding N2 is lower than the voltage of the output smoothing capacitor C2, and the current does not flow into the winding N2. Further, when the switching elements Q1 and Q4 are turned OFF before the end of the modal A' resonance current inflow, the mode b can be omitted. (Mode C) When the switching elements Q1 and Q4 are turned OFF, they are in the state of modal c. In the modal C, the current flowing into the switching elements Q1 and Q4 flows into the anti-parallel diodes D2 and D3, and flows into the connection capacitor C1. At this time, the setting switching elements Q2 and Q3 are turned ON. (Modal D) When the current of the winding N1 is reversed, MODE becomes D. Modal D is the symmetrical action of modal A. Hereinafter, the symmetry of the modes B and C is returned to the mode A. As described above, in the resonance type charging device, the DC_DC converter 3 is a resonance type converter, and the voltage applied to the diodes D2 1 to D24 is clamped by the voltage of the output smoothing capacitor C2. Therefore, even when the voltage of the secondary battery 6 is high, the diodes D21 to D24 can use a diode having a low withstand voltage of -12 - 201232989 and a reduced forward voltage, which can reduce the loss and contribute to high efficiency. At the output of the DC-DC converter 3, that is, between the smoothing capacitor C2 and the secondary battery 6, an LC filter composed of an inductor and a capacitor can be inserted in order to reduce the chopping current. However, in the subsequent stage of the DC-DC converter 3, a converter having a current control function such as a chopper is not inserted and connected to the secondary battery 6. Therefore, the control means 4 has a function of performing constant voltage constant current control on the output of the DC-DC converter 3 when the secondary battery whose voltage is changed depending on the state of charge is charged. The DC-DC converter 3 is a resonant type converter that controls the switching frequency of the switching elements Q 1 to Q4 to control the output. When a secondary battery of a vehicle is charged by a commercial power source, there is usually a limit to the current or power that can be supplied by the commercial power source. The control means 4 is provided to be capable of charging the secondary battery 6 in a short period of time. When the voltage of the secondary battery 6 is lower than the voltage at the end of charging, the current or electric power input to the AC power source 5 is controlled to be set. function. In this case, the output power system of the DC-DC converter 3 is maintained at a constant level. Fig. 4 shows the relationship between the switching frequency fsw and the output power Pout, the output voltage Vout, and the output current lout when the connection voltage is constant. When the connection voltage and output power are maintained constant, the switching frequency becomes high when the output voltage is low and the output current is large. Conversely, the output voltage is high and the output current is small, and the switching frequency becomes low. Resonant converters, where the switching frequency is too high or too low, are mostly in the case of high efficiency, so it is better to operate at the switching frequency in the middle of high efficiency. 13-201232989 Figs. 5 to 7 show changes in the output voltage Vout, the connection voltage Vlink, the output power Pout, the output current lout, the switching frequency fsw, and the efficiency 7 in the charging of the secondary battery 6 over time. In FIG. 5, the connection voltage Vlink is maintained at a lower level. Over time, the output voltage Vout rises and the switching frequency fsw becomes too low to reduce the efficiency 7?. In FIG. 6, the connection voltage Vlink is maintained at a higher level. During the near start of charging, the output voltage Vout is low, the switching frequency fsw becomes too high, and the efficiency 7? is lowered. The resonance type charging device 1 is provided with a connection voltage coordination control for controlling the connection voltage by the voltage of the secondary battery 6. In Fig. 7, the switching frequency fsw is maintained in such a manner that the efficiency becomes higher, so that the connection voltage Vlink rises as the output voltage Vout rises. Fig. 8 shows a method of determining the connection voltage Vlink by the output voltage Vout. The connection voltage Vlink may be determined so that the efficiency 77 is increased under the conditions of the output voltage Vout. However, since the circuit configuration of the AC-DC converter 2 is a boost chopper as described above, the connection voltage cannot be made smaller than the voltage amplitude of the AC power source 5. Therefore, the variable range of the connection voltage to which the voltage coordination control is connected is assumed to be the lower limit of the voltage amplitude of the AC power supply 5. Further, based on the withstand voltage or life of the circuit element such as the junction capacitor C1, the upper limit of the variable range of the connection voltage is also set. Fig. 9 shows the relationship between the output voltage Vout and the junction voltage Vlink. Among them, VlinkC is the connecting voltage with higher efficiency, VlinlcH is the upper limit of the connecting voltage, and VlinkL is the limit of the connecting voltage below -14-201232989. Of course, when the voltage of the AC power source 5 and the voltage of the secondary battery 6 are simultaneously low, the efficiency improvement effect can be obtained by simply implementing the connection voltage coordinated control by reducing the connection voltage and the like. As described above, in the resonance type charging device 1, the circuit mode of the DC-DC converter 3 is a resonance type converter, and the secondary battery 6 can be charged with high efficiency by performing constant voltage constant current control. In addition, in order to maximize the efficiency of the resonant converter, it is possible to provide coordinated voltage control. (Second Embodiment) Fig. 10 is a circuit diagram showing a configuration of a resonance type charging device 11 according to a second embodiment of the present invention. The resonance type charging device 11 is similar to the resonance type charging device 1 of the first embodiment, and is composed of an alternating current power supply 5 The secondary battery 6 supplies electric power. The resonance type charging device 11 includes an AC-DC converter 12 that inputs electric power of the AC power source 5 to output a DC connection voltage, and a DC-DC converter 13 that insulates the secondary battery 6 from the connection. The voltage is supplied to the power; and the control means 14 controls the converters. In the AC-DC converter 12, the boosting chopper circuit in the AC-DC converter 2 of the first embodiment is configured as a smoothing inductor L2, a step-down switching element Q5, a step-down diode D5, and a riser. The point is different between the voltage switching element Q6, the step-up diode D6, and the bridge circuit formed by the connection capacitor C1. In addition, it has a -15-201232989 LC filter composed of a filter inductor L3 and a smoothing capacitor C3. A filter inductor L3 and a smoothing capacitor C3 are connected between the DC terminals of the bridge-connected rectifier diodes D11 to D14. A step-down switching element Q5 and a step-down diode D5' are connected in series between both ends of the smoothing capacitor C3. A smoothing inductor L2 and a boosting switching element Q6 are connected in series between both ends of the step-down diode D5. A step-up diode D6 and a connection capacitor C1 are connected in series between both ends of the step-up switching element Q6. Compared with the DC-DC converter 3 of the first embodiment, the DC-DC converter 13 is different in that the resonant capacitor Cr1 is set as the resonant capacitors Cr11 and Crl2, and the anti-parallel diode D1 having the full bridge connection is provided. Among the switching elements Q1 to Q4 of the D4, the diodes D3 and D4 connected in anti-parallel with the switching elements Q3 and Q4 are replaced by the resonant capacitors Cr11 and Crl2, and are set as a half bridge circuit, and the bridge type is connected. Among the polar bodies D21 to D24, the diodes D23 and D24 are replaced with smoothing capacitors C21 and C22, respectively. In other words, the switching circuit of the DC-DC converter 13 connects the switching element Q1 of the first switching element and the switching element Q2 of the second switching element in series to form a first switching leg, and resonates the first resonant capacitor. The capacitor Cr 11 and the resonant capacitor Cr12 of the second resonant capacitor are connected in series to form a resonant capacitor leg, and the first switch leg portion and the resonant capacitor leg portion are connected in parallel. In the switching circuit, the two ends of the first switch leg are used as the DC terminals, and the series connection points of the switching elements Q1 and Q2 and the series connection points of the resonant capacitors Cr1 and Cr1 are used as the AC terminals. The rectifier circuit of the DC-DC $ multiplexer 13 is a first diode body leg which is connected in series with the first diode 2-16-201232989 polar body D21 and the second diode diode D22. The smoothing capacitor C21 of the first voltage dividing capacitor and the smoothing capacitor C22 of the second voltage dividing capacitor are connected in series to form a capacitor leg, and the first diode leg and the voltage dividing capacitor leg are connected in parallel. In the rectifier circuit, the two terminals of the first diode are used as the DC terminals, and the series connection points of the diodes D2 1 and D22 and the series connection points of the smoothing capacitors C2 1 and C22 are used as the communication. Between the terminals □ The buck switching element Q5, the boost switching element Q6, and the switching elements Q1 and Q2 are controlled by the control means 14. Similarly to the resonance type charging device 1 of the first embodiment, the control means 14 is connected to the voltage sensors 21 to 23 and the current sensors 24 and 25. Similarly to the control means 4 of the first embodiment, the control means 14 includes power factor improvement control, connection voltage coordination control, constant voltage constant current control, and the like. In the resonance type charging device 11, the AC-DC converter 12 employs a Η bridge circuit as described above, and by switching the step-down switching element Q5, the connection voltage can be made smaller than the voltage amplitude of the AC power source 5. Therefore, compared with the resonance type charging device 1 of the first embodiment, the variable range of the connection voltage can be further expanded, and the charging of the secondary battery 6 can be performed with higher efficiency. Further, by using the half bridge circuit in the DC-DC converter 13, the number of components of the switching element and the diode can be reduced. (Third Embodiment) Fig. 11 is a view showing a configuration of a power supply system of an electric automatic vehicle 1 10 using the resonance type charging device 1 of the present invention. The resonance type charging device 1 is connected to a plug-in system connector 108 connected to an alternating current power source 109, and a secondary battery 105 connected to a DC battery 105 in a secondary battery 105-201232989. The DC converter 102 and the DC-DC converter 102 supply electric power to an inverter 103 for driving the power motor 104. Further, the DC-DC converter 100 is connected to the secondary battery 1〇5, and the DC-DC converter 100 supplies electric power to the backup battery 106 to which the electrical equipment 101 is connected; and the rapid charging connector 107 is connected to the rapid state. The charging connector 107 is connected to an external DC power source such as a rapid charger to charge the secondary battery 105. The resonance type charging device 1 charges the secondary battery 105 using the electric power of the AC power source 109 connected to the plug-in charging connector 108. According to the third embodiment, the power secondary battery mounted on the vehicle can be efficiently charged by the commercial power source by using the resonance type charging device 1 of the present invention. The resonance type charging device 1 of the present invention is also applicable to a hybrid type hybrid car. (Effect of the Invention) According to the resonance type charging device and the vehicle provided by the present invention, it is possible to efficiently charge a secondary battery having a high voltage and a wide voltage range by an AC power source. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a view showing a configuration circuit -18-201232989 of a resonance type charging device 1 of a first embodiment. 2A and 2B are diagrams showing the operation of the circuit of the AC-DC converter 2 of the first embodiment. 3A to 3D are diagrams showing the operation of the circuit of the DC-DC converter 3 of the first embodiment. Fig. 4 is a view showing the characteristics of the DC-DC converter 3 of the first embodiment. Fig. 5 is a view showing the charging operation of the resonance type charging device 1 of the first embodiment. Fig. 6 is a view showing the charging operation of the resonance type charging device 1 of the first embodiment. Fig. 7 is a view showing the charging operation of the resonance type charging device 1 of the first embodiment. Fig. 8 is a view showing the characteristics of the resonance type charging device 1 of the first embodiment. Fig. 9 is a view showing the manner of determining the connection voltage of the resonance type charging device 1 of the first embodiment. Fig. 10 is a circuit diagram showing the configuration of a resonance type charging device 11 according to a second embodiment of the present invention. Fig. 11 is a view showing the configuration of a power supply system of an electric automatic vehicle using the resonance type charging device of the present invention. [Description of main component symbols] 1, 11: Resonant charging device -19- 201232989 2, 12: AC-DC converter 3, 13, 100, 102: DC-DC converter 4, 1 4 : Control means 5, 1 0 9 : AC power supply 6, 1 0 5 : Secondary battery 2 1 to 2 3 : Voltage sensor 24, 25 : Current sensor 101 : Electrical equipment 1 03 : Inverter 1 〇 4 : Power motor 106 : Replacement battery 107: Rapid charging connector 108: Plug-in charging connector Π 0: Electric automatic car LI, L2: Smoothing inductor L3: Filtering inductor L r 1 : Resonant inductor C 1 : Connecting capacitors C2, C21, C22: Smoothing capacitor C 3 : Filter capacitor
Crl、Crl 1、Crl2 :共振電容器 T1 :變壓器 N 1、N 2 :繞線 Q1〜Q4:開關元件 -20- 201232989 Q5 :降壓開關元件 Q6、Q10 :升壓開關元件 D1〜D4 :逆並聯二極體 D5 :降壓二極體 D6、D10:升壓二極體 D11〜D14:整流二極體 D2 1〜D24 :二極體 -21 -Crl, Crl 1, Crl2: Resonant capacitor T1: Transformer N 1 , N 2 : Winding Q1~Q4: Switching element -20- 201232989 Q5: Step-down switching element Q6, Q10: Boost switching element D1~D4: anti-parallel Diode D5: Buck Diode D6, D10: Boost Diode D11~D14: Rectifier Dipole D2 1~D24: Diode-21 -