201230672 六、發明說明： 【發明所屬之技術領域】 本發明係與用以除去至少2條之電線上之公用模式雜 音的雜音去除濾波器相關。 【先前技術】 近年來，太陽能面板十分普及，被積極地應用於家庭 內及工廠內之消耗電力的補充及以售電爲目的之利用。此 時，因爲利用太陽能面板發電之電力爲直流，爲了將其轉 換成與商用電源相同電壓之交流電源爲目的，而設置被稱 爲電源調節器之變流器裝置。 然而，因爲變流器裝置係以斬波電路使直流形成斷續 ，創造擬正弦波來將直流變換成交流，隨著該斬波電路之 直流的斷續而發生激烈之諧波雜音。該高頻雜音，也會從 變流器裝置逆流至太陽能面板側，而以連結變流器裝置與 太陽能面板之間的電線作爲天線，將高電平之高頻雜音輻 射至空間。因此，藉由於變流器裝置之輸出入部裝設線路 濾波器來減輕高頻雜音，作爲防止不必要輻射之措施。 然而，一般而言，因爲係使用平行電線作爲電源線， 其傳輸模式係相當於高頻電路之平衡模式的正常模態（差 異模態）。此時，針對正常模態之雜音成份，藉由於平行 電線間插入電容，很容易即可壓抑雜音成份。然而，無法 壓抑相當於高頻電路之不平衡模式之公用模式的雜音成份 。此外’傳送太陽能面板所產生之直流電力的平行電線， -5- 201230672 並未考慮到高頻，也未考慮到公用模式。因此，發生公用 模式之雜音的話，即使配設線路濾波器，也在未充份衰減 下被放射至空間，而產生雜音干擾。是以，因爲公用模式 之雜音在無接地線之平行電線上傳播，亦即，以公用模式 而言，在不完全之線路上傳播，而處於容易發生不必要之 輻射的狀況。 於高頻電路進行相當於公用模式之不平衡傳輸時，利 用低通濾波器（LPF )可以減輕相對於通過頻率之諧波成 份。傳統之基本LPF電路如第16 ( a ) 、（ b )圖所示。第 16(a)圖所示之LPF電路係π型，電感L201係直列連接於 輸入端子IN與輸出端子OUT之間，電感L201之兩端與接地 線之間，分別並列連接著電容C201、C202。此外’第16 ( b)圖所示之LPF電路係T型，電感L202、L203係直列連接 於輸入端子IN與輸出端子OUT之間，電感L202、L203之連 接點與接地線之間則並列連接著電容C203。 如第16 ( a ) ( b )圖所示之LPF電路，可以當作線路 濾波器使用，利用第16 ( a )圖所示之π型之LPF電路的傳 統線路濾波器200之電路，如第17圖所示。第17圖所示之 線路濾波器200，於第1輸入端子IN 201與第1輸出端子 OUT201之間，直列連接著電感L2 10，電感L2 10之兩端與 接地線E之間，則分別並列連接著電容C2 1 0、C2 1 1。此外 ，於第2輸入端子IN202與第2輸出端子OUT202之間’則直 列連接著電感L 2 1 1 ’電感L 2 1 1之兩端與接地線E之間’分 別並列連接著電容C212、C213。 -6- 201230672 其次，利用第16 ( b )圖所示之T型之LPF電路的傳統 線路濾波器300之電路，如第18圖所示。第18圖所示之線 路濾波器300，於第1輸入端子IN 301與第1輸出端子 OUT30 1之間，直列連接著電感L3 1 0、L3 1 1，於電感L3 1 0 、L31 1之連接點與接地線E之間，則並列連接著電容C310 。此外，於第2輸入端子IN3 02與第2輸出端子OUT3 02之間 ，直列連接著電感L312、L313，而於電感L312、L313之 連接點與接地線E之間，則並列連接著電容C3 1 1。 第17圖所示之線路濾波器200或第18圖所示之線路濾 波器3 00，係連接於平行電線等，然而，平行電線時’因 爲不存在公用模式所必要之明確接地線，而存在著介由與 大地之間的雜散電容等之不明確接地線。所以，線路濾波 器2 00、3 00時，並列連接之電容的接地E爲不完全之狀態 ，而爲無法發揮本來之電氣機能的狀態。所以，針對公用 模式之雜音成份，線路濾波器200或線路濾波器300之電容 ，無法期待其諧波雜音的衰減效果。所以，即使於連接太 陽能面板與變流器裝置之平行電線，連接線路濾波器200 或線路濾波器300，也無法去除變流器裝置所發出之諧波 雜音’於接近住宅之主要係利用短波波段來進行通信之業 餘無線台、AM ·短波· FM波段之無線電廣播波等，經常 會發生電波干擾的案例。 因此，以往就有人提出：將只使用抗流線圏之第1 9圖 所示之線路濾波器400應用於用以抑制公用模式電流之線 路濾波器。第1 9圖所示之線路濾波器4 0 0 ’係連接於數據 201230672 機410，並插入傳送通信訊號之電力線。於該電力線之前 端，配設有插頭413，將插頭413插入屋內之插座。線路濾 波器400，係直列連接於第1抗流線圈4 1 1及第2抗流線圈 412之構成，配設於數據機410側之第1抗流線圈41 1之阻抗 高於第2抗流線圈4 1 2之阻抗。所以，第1抗流線圈4 1 1之捲 數多於第2抗流線圈41 2之捲數。 [專利文獻1]日本特開2006-166015號公報 【發明內容】 第1 9圖所示之傳統之只使用抗流線圈之線路濾波器 40 0時，配設於電力線側之抗流線圈41 2的阻抗較低，係爲 了降低與電力線之阻抗未匹配所導致的不良影響。然而， 即使數據機410之阻抗已有規定，但電力線之阻抗並無規 定，電力線之阻抗，因爲電力線之配線狀況而有很大的差 異。是以，因爲設置線路濾波器400之各場所，電力線之 阻抗不同係十分一般的現象，即使將線路濾波器400插入 電力線，有時仍有無法去除電力線之阻抗影響所導致之高 頻雜音的問題。 此外，因爲太陽能面板及變流器裝置之阻抗也未規定 ，即使將第19圖所示之傳統線路濾波器400配設於連接太 陽能面板及變流器裝置之平行電線或變流器裝置之輸出部 ，仍有因爲上述理由而無法有效去除高頻雜音之問題。 因此，本發明之目的，係在提供可有效去除高頻雜音 之雜音去除濾波器。 -8- 201230672 本發明之主要特徵，係於Mn-Zn系之環狀核心捲繞著 導體線之至少1個之第1抗流線圈、及於Ni-Zn系之環狀核 心捲繞著導體線之至少1個之第2抗流線圈之直列連接電路 ’連接於輸入端子及輸出端子之間，成對之前述輸入端子 及前述輸出端子至少爲2對。 依據本發明，因爲以直列連接：於Mn-Zn系之環狀核 心捲繞著導體線之第1抗流線圈、及於Ni-Zn系之環狀核心 捲繞著導體線之第2抗流線圈；來構成雜音去除濾波器， 於從低通至高通之寬頻帶，可以得到安定之較大的衰減量 【實施方式】 至實現本發明之雜音去除濾波器的經過，如第〗圖至 第7圖所示。第1圖，係未具備電容之雜音去除濾波器的構 成電路圖，第2圖，係第1圖所示之雜音去除濾波器之利用 Mn-Zn (錳•鋅）系之相對磁導率y s爲約5 000之環狀核心 時之衰減量的頻率特性圖，第3圖，係第1圖所示之雜音去 除濾波器之利用Mn-Zn系之相對磁導率β s爲約5 000之環狀 核心時之衰減量之其他的頻率特性圖’第4圖’係第1圖所 示之雜音去除濾波器之利用Mn-Zn系之相對磁導率// s爲約 2500之環狀核心時之衰減量的頻率特性圖’第5圖’係第1 圖所示之雜音去除濾波器之利用Mn_Zn系之相對磁導率# s 爲約2500之環狀核心時之衰減量之其他的頻率特性圖，第 6圖，係第1圖所示之雜音去除濾波器之利用Ni-Zn (鎳· -9- 201230672 鋅）系之相對磁導率# s爲約8 00之環狀核心時之衰減量的 頻率特性圖，第7圖，係第1圖所示之雜音去除濾波器之利 用Ni-Zn系之相對磁導率"s爲約800之環狀核心時之衰減 量之其他的頻率特性圖。 第1圖所示之構成之雜音去除濾波器1〇〇，係利用2條 平行電線及電力線等之電線時的雜音去除濾波器。雜音去 除濾波器100，係由：連接於第1輸入端子IN 1及第1輸出端 子OUT1之間的第1抗流線圈CH1 ;及連接於第2輸入端子 IN2及第2輸出端子OUT2之間的第2抗流線圈CH2 ;所構成 。第1抗流線圈CH 1及第2抗流線圈CH2 ’係藉由將電線捲 繞於環狀核心來構成。該電線可以爲單線或絞線。本說明 書之環狀核心，係指將Mn-Zn系或Ni-Zn系等之複合肥粒鐵 以高溫燒結成環狀之核心。 於以Mn-Zn系作爲該環狀核心之內徑爲約40亳米、相 對磁導率A s爲約5000之環狀核心，捲繞24圈電線來構成 第1抗流線圈CH1及第2抗流線圈CH2 »由該第1抗流線圈 CH1及第2抗流線圈CH2所構成之雜音去除濾波器1〇〇之至 1MHz爲止之衰減量的頻率特性如第2圖所示，改變尺度之 至1 0 0 Μ Η z爲止之衰減量的頻率特性則如第3圖所示。參照 第2圖的話，0.3MHz周邊約39dB之衰減量的峰値’代表至 1 Μ Η z爲止有良好之衰減特性。此外’參照第3圖的話’隨 著頻率之增高，衰減量降低’約40MHz之衰減量降低至約 14dB。而且，40MHz以上之頻率時’衰減量逐漸增加’約 90MHz時，雖然有峰値但只得到約22化之衰減量。是以’ -10- 201230672 利用Mn-Zn系之相對磁導率μ s爲約5000之環狀核心的雜音 去除濾波器100，低通之衰減特性雖然優良’高通部於 40MHz附近則只能得到約14dB之衰減量，可以得知高通之 衰減特性較差。 其次，於以Μη-Zn系作爲環狀核心之內徑爲約3 1亳米 '相對磁導率μ s爲約2500之環狀核心’捲繞22圈電線來 構成第1抗流線圈CH1及第2抗流線圈CH2。由該第1抗流線 圈CH1及第2抗流線圈CH2所構成之雜音去除濾波器1〇〇之 至1MHz爲止之衰減量的頻率特性如第4圖所示，改變尺度 之至100MHz爲止之衰減量的頻率特性則如第5圖所示。參 照第4圖的話，0.8MHz周邊約48dB之衰減量之峰値，代表 至1 MHz爲止有良好之衰減特性。此外，參照第5圖的話， 隨著頻率之增高，衰減量降低，約35MHz之衰減量降至約 17dB，約70MHz時，衰減量也降至約16dB。而且，70MHz 以上之頻率時，衰減量逐漸增加，約100MHz時，雖然有 峰値但只得到約21dB之衰減量。是以，利用Μη-Ζη系之相 對磁導率// s爲約25 00之環狀核心的雜音去除濾波器100, 低通之衰減特性雖然優良，高通部於70MHz附近則只能得 到約16dB之衰減量，可以得知高通之衰減特性較差。 其次，於以Ni-Zn系作爲環狀核心之內徑爲約27亳米 、相對磁導率// s爲約800之環狀核心，捲繞18圈電線來構 成第1抗流線圈CH1及第2抗流線圈CH2。由該第1抗流線圈 CH1及第2抗流線圈CH2所構成之雜音去除濾波器1〇〇之至 1MHz爲止之衰減量的頻率特性如第6圖所示，改變尺度之 -11 - 201230672 至100 MHz爲止之衰減量之頻率特性如第7圖所示。參照第 6圖的話，衰減量逐漸增加，然而，1 MHz周邊只能得到約 2 3dB之衰減量，至1MHz爲止衰減特性較差。此外，參照 第7圖的話，隨著頻率之增高，衰減量增加，約35MHz周 邊之衰減量增加至約46d。此時，於約7MHz至約55MHz之 寬頻帶，可以得到40dB以上之衰減量。而且，60MHz以上 之頻率時，衰減量逐漸降低，約95MHz時，只能得到約 12dB之衰減量。是以，使用Ni-Zn系之相對磁導率ys爲約 800之環狀核心的雜音去除濾波器100，高通之衰減特性雖 然優良，但低通部只能得到約20dB前後之衰減量，可以得 知低通之衰減特性較差。 如以上所示，發現Mn-Zn系之環狀核心及Ni-Zn系之環 狀核心，其衰減量之頻率特性不同，因而本發明之第1實 施例之雜音去除濾波器1的構成電路圖，如第8圖所示。 第8圖所示之第1實施例之雜音去除濾波器1，係利用2 條平行電線及電力線等之電線時的雜音去除濾波器。第1 實施例之雜音去除濾波器1，係將直列連接之；由將電線 捲繞於低通之衰減特性優良之Mn-Zn系環狀核心所構成之 第1抗流線圈CH 1 -1 ;及由將電線捲繞於高通之衰減特性優 良之Ni-Zn系環狀核心所構成之第2抗流線圈CH1-2 ;連接 於第1輸入端子IN1及第1輸出端子OUT1之間。此外，將直 列連接之：由將電線捲繞於低通之衰減特性優良之Mn-Zn 系環狀核心所構成之第3抗流線圈CH 1 -3 ;及由將電線捲繞 於高通之衰減特性優良之Ni-Zn系環狀核心所構成之第4抗 -12- 201230672 流線圈CHI-4;連接於第2輸入端子IN2及第2輸出端子 OUT2之間。捲繞於第1抗流線圈CH1-1至第4抗流線圈CiU-4之電線，可以爲單線，也可以爲絞線。該第1抗流線圈 CH 1-1至第4抗流線圈CH 1-4，係被收容於屏蔽外殼1〇內。 針對上述所說明之第1實施例之雜音去除濾波器1之使 用方法的一例進行說明的話，如下所示，將第1台雜音去 除濾波器1之第1輸入端子IN 1及第2輸入端子IN2，例如， 連接於變流器裝置之輸出側，而於該雜音去除濾波器1之 第1輸出端子OUT 1及第2輸出端子OUT2，分別連接2條平行 電線及電力線等之電線。此外，將第2台雜音去除濾波器1 之第1輸出端子OUT1及第2輸出端子OUT2，例如，連接於 變流器裝置之輸入側，而於該雜音去除濾波器1之第1輸入 端子IN1及第2輸入端子IN2，分別連接2條連結於太陽能面 板之平行電線等之電線。是以，藉由於發生雜音之變流器 裝置之輸入側及輸出側，分別連接著雜音去除濾波器1， 而極力防止變流器裝置所發生之高頻雜音，由連接於太陽 能面板之電線或連接於變流器裝置之電力線放射出來。 此處，針對第1實施例之雜音去除濾波器1之具體構成 的一例進行說明。使用於第1抗流線圈CH 1 -1及第3抗流線 圈CH 1-3之Mn-Zn系環狀核心，係內徑爲約31亳米’相對 磁導率/zs爲約2500，捲繞著22圈電線來構成第1抗流線圈 CH 1 -1及第3抗流線圈CH 1 -3。此外，使用於第2抗流線圈 CH1-2及第4抗流線圏CH1-4之Ni-Zn系環狀核心，內徑爲約 27亳米，相對磁導率爲約800’捲繞著18圈電線來構成 -13- 201230672 第2抗流線圈CHI-2及第4抗流線圈CHI-4。 由如上述構成之第1抗流線圈CH1-1至第4抗流線圈 CH1-4所構成之第1實施例之雜音去除濾波器1之至1MHz爲 止之衰減量的頻率特性’如第10圖所示’改變尺度之至 10 0MHz爲止之衰減量的頻率特性則如第1 1圖所示。參照 第10圖的話，至約〇·8ΜΗζ爲止，衰減量逐漸增加，於 0.8MHz周邊，有約44dB之衰減量的峰値，表示至1MHz爲 止有良好之衰減特性。此外，參照第1 1圖的話，於2.3MHz 附近，衰減量雖然降低至約35dB’然而，其以上之頻率時 ，衰減量增力□，約35MHz周邊，衰減量增加至約58dB。此 時，從約4MHz至75MHz之寬頻帶可以得到40dB以上之衰 減量。並且，80MHz以上之頻率時，衰減量逐漸降低，約 95MHz時，降低至約25dB之衰減量。是以，本發明之第1 實施例之雜音去除濾波器1，不但低通之衰減特性優良， 同時，高通之衰減特性也十分優良，於約0.5 MHz〜約 9 0 MHz之寬頻帶可以得到安定而大之衰減量。此外，不論 公用模式或正常模態之雜音，全部模態之高頻雜音皆可去 除。 其次，本發明之第2實施例之雜音去除濾波器2的構成 電路圖，如第9圖所示。 第9圖所示之第2實施例之雜音去除濾波器2，係使用 包含平行電線及電力線等之接地線在內之3條電線時的雜 音去除濾波器。第2實施例之雜音去除濾波器2，以去除接 地線上之高頻雜音爲目的，於第1實施例之雜音去除濾波 -14- 201230672 器1，附加了 ：將由將電線捲繞於Mn_Zn系環狀核心所構成 之第5抗流線圈CH2-1、及由將電線捲繞於Ni-Zn系環狀核 心所構成之第6抗流線圏CH2-2直列連接於連接至接地線之 第3輸入端子IN3及第3輸出端子OUT3之間的構成；其他構 成，係與第1實施例之雜音去除濾波器1相同。捲繞於第1 抗流線圈CH1-1至第6抗流線圈CH2-2之電線，可以爲單線 ，也可以爲絞線。該第1抗流線圈CH 1 -1至第6抗流線圈 CH2-2，係被收容於屏蔽外殼20內。 針對上述所說明之第2實施例之雜音去除濾波器2之使 用方法的一例進行說明的話，如下所示，將第1台雜音去 除濾波器2之第1輸入端子IN1及第2輸入端子IN2，例如， 連接於變流器裝置之輸出側，而且，將第3輸入端子IN3連 接於變流器裝置之接地線，於該雜音去除濾波器2之第1輸 出端子OUT 1及第2輸出端子OUT2，分別連接平行電線及電 力線等之2條電線，同時，將接地線連接於第3輸出端子 OUT3。此外，將第2台之雜音去除濾波器2之第1輸出端子 OUT1及第2輸出端子OUT2，例如，係連接於變流器裝置之 輸入側，而且，將第3輸出端子OUT3連接至變流器裝置之 接地線，於該雜音去除濾波器2之第1輸入端子IN 1及第2輸 入端子IN2，分別連接著連接於太陽能面板之平行電線等 之2條電線，同時，第3輸入端子IN3則連接著接地線。是 以，藉由於發生雜音之變流器裝置之輸入側及輸出側分別 連接雜音去除濾波器2’而極力防止變流器裝置所發生之 高頻雜音，由連接於太陽能面板之電線或連接於變流器裝 -15- 201230672 置之電力線放射出來。此外，只有2條連接太陽能面板及 變流器裝置之電線而無接地線時，將第1實施例之雜音去 除濾波器1連接於變流器裝置之輸入側，再以2條電線連接 太陽能面板即可。 此處，針對第2實施例之雜音去除濾波器2之具體構成 的一例進行說明。使用於第1抗流線圈CH 1 -1、第3抗流線 圈CH1-3、及第5抗流線圈CH2-1之Mn-Zn系環狀核心，係 內徑爲約31亳米，相對磁導率# s爲約2500，捲繞著22圈 電線來構成第1抗流線圈CH1-1、第3抗流線圈CH1-3、及 第5抗流線圈CH2-1。此外，使用於第2抗流線圈CH1-2、 第4抗流線圈CH1-4、及第6抗流線圈CH2-2之Ni-Zn系環狀 核心，係內徑爲約27亳米，相對磁導率# s爲約800，捲繞 著18圈電線來構成第2抗流線圈CH1-2、第4抗流線圈CH1-4、及第6抗流·線圈CH2-2。 如上所述之構成之本發明之第2實施例的雜音去除濾 波器2，因爲不但低通之衰減特性優良，高通之衰減特性 也十分優良，與第1實施例之雜音去除濾波器1相同，於約 0.5MHz〜約90MHz之寬頻帶，可以得到安定而大之衰減量 。此外，不論公用模式或正常模態之雜音，全部模態之高 頻雜音皆可去除。 其次，本發明之第3實施例之雜音去除濾波器3的構成 電路圖，如第12圖所示。 第1 2圖所示之第3實施例之雜音去除濾波器3，係使用 2條平行電線及電力線等之電線時的雜音去除濾波器。第3 -16- 201230672 實施例之雜音去除濾波器3，係於第1實施例之雜音去除濾 波器1，附加了 ：於第1抗流線圈CH 1 -1之前，直列連接低 通之衰減特性優良之相對磁導率不同於第1抗流線圈CH1-1 之由將電線捲繞於Μη-Ζη系環狀核心所構成的第5抗流線圈 CH3-1 ；及於第3抗流線圏CH 1 -3之前，直列連接低通之衰 減特性優良之相對磁導率不同於第3抗流線圈CH1-3之由將 電線捲繞於Μη-Ζη系環狀核心所構成之第6抗流線圈CH3-2 的構成；其他構成，則與第1實施例之雜音去除濾波器1相 同。此外，捲繞於第1抗流線圈CH 1-1至第6抗流線圈CH3-2之電線，可以爲單線，也可以爲絞線。該第1抗流線圈 CH1-1至第6抗流線圈CH3-2，係被收容於屏蔽外殻30內。 上述說明之第3實施例之雜音去除濾波器3的使用方法 ，與上述第1實施例之雜音去除濾波器1相同。省略其詳細 說明，然而，藉由於發生雜音之變流器裝置之輸入側及輸 出側分別連接雜音去除濾波器3，可以極力防止變流器裝 置所發生之高頻雜音，由連接於太陽能面板之電線及連接 於變流器裝置之電力線放射出來。 此處，針對第3實施例之雜音去除濾波器3之具體構成 的一例進行說明。使用於第1抗流線圏CH1-1及第3抗流線 圈CH 1-3之Μη-Ζη系環狀核心，係內徑爲約31亳米’相對 磁導率V s爲約2 5 0 0，捲繞著2 2圈電線來構成第1抗流線圈 CH 1 -1及第3抗流線圈CH 1 -3。此外，使用於第2抗流線圈 CH1-2及第4抗流線圈CH1-4之Ni-Zn系環狀核心’係內徑爲 約27亳米，相對磁導率爲約800，捲繞著18圈電線來構 -17- 201230672 成第2抗流線圈CHI-2及第4抗流線圈CHI-4。此外’使用 於第5抗流線圏CH3-1及第6抗流線圈CH3-2之Mn-Zn系環狀 核心，係內徑爲約4 0亳米’相對磁導率# s爲約5 0 0 0 ’捲 繞著2 4圈電線來構成第5抗流線圈C Η 3 -1及第ό抗流線圈 CH3-2。 由如上述構成之第1抗流線圈CH 1-1至第6抗流線圈CH 3-2所構成之第3實施例之雜音去除濾波器3之至1MHz爲止 之衰減量的頻率特性，如第14圖所示，改變尺度之至 1 0 0MHz爲止之衰減量的頻率特性則如第1 5圖所示。參照 第14圖的話，至約0.2MHz爲止，衰減量急速增加，於 0.2MHz周邊，可以得到約40dB之衰減量。此外，隨著頻 率之增高，衰減量增加，於0.8MHz周邊，有約51dB之衰 減量的峰値，表示至1MHz爲止有良好之衰減特性。此外 ，參照第14圖的話，於2.3MHz附近，衰減量雖然降低至約 42dB，然而，其以上之頻率時，衰減量增加，約30MHz周 邊，衰減量增加至約7 OdB。超過30MHz的話，衰減量緩慢 下降，然而，至100MHz爲止，可以得到約49dB以上之衰 減量。所以，於約0.2MHz至約100MHz之寬頻帶，可以得 到4 OdB以上之衰減量。是以，本發明之第3實施例之雜音 去除濾波器3，不但低通之衰減特性優良，同時，高通之 衰減特性也十分優良，於約0.2MHz〜約100MHz之寬頻帶 可以得到安定而大之衰減量。此外，不論公用模式或正常 模態之雜音，全部模態之高頻雜音皆可去除。 其次’本發明之第4實施例之雜音去除濾波器4的構成 •18- 201230672 電路圖，如第1 3圖所示。 第13圖所示之第4實施例之雜音去除濾波器4，係使用 包含平行電線及電力線等之接地線在內之3條電線時的雜 音去除濾波器。第4實施例之雜音去除濾波器4，係於第2 實施例之雜音去除濾波器2，附加了 ：於第1抗流線圈CH 1 -1之前，直列連接低通之衰減特性優良之相對磁導率不同 於第1抗流線圈CH1-1之由將電線捲繞於Mn-Zn系環狀核心 所構成的第7抗流線圈CH3-1 ;於第3抗流線圈CH1-3之前 ，直列連接低通之衰減特性優良之相對磁導率不同於第3 抗流線圈CH 1-3之由將電線捲繞於Mn-Zn系環狀核心所構 成之第8抗流線圈CH3-2;及於第5抗流線圈CH2-1之前， 直列連接低通之衰減特性優良之相對磁導率不同於第5抗 流線圈CH2-1之由將電線捲繞於Mn-Zn系環狀核心所構成 之第9抗流線圈CH3-3的構成；其他構成，則與第2實施例 之雜音去除濾波器2相同。此外，捲繞於第1抗流線圈CH1· 1至第9抗流線圈CH3-3之電線，可以爲單線，亦可以爲絞 線。該第1抗流線圖CH1-1至第9抗流線圈CH3-3，係被收 容於屏蔽外殼40內。 上述說明之第4實施例之雜音去除濾波器4的使用方法 ，與上述第2實施例之雜音去除濾波器2相同。省略其詳細 說明，然而，藉由於發生雜音之變流器裝置之輸入側及輸 出側分別連接雜音去除濾波器4，可以極力防止變流器裝 置所發生之高頻雜音，由連接於太陽能面板之電線及連接 於變流器裝置之電力線放射出來。此外，只有2條連接太 -19- 201230672 陽能面板及變流器裝置之電線而無接地線時，將第3實施 例之雜音去除濾波器3連接於變流器裝置之輸入側，再以2 條電線連接太陽能面板即可。 此處，針對第4實施例之雜音去除濾波器4之具體構成 的一例進行說明。使用於第1抗流線圈CH 1 -1、第3抗流線 圏CH1-3、及第5抗流線圈CH2-1之Mn-Zn系環狀核心，係 內徑爲約31亳米，相對磁導率爲約2500，捲繞著22圈 電線來構成第1抗流線圈CH 1 -1、第3抗流線圈CH 1 -3、及 第5抗流線圈CH2-1。此外，使用於第2抗流線圈CH卜2、 第4抗流線圈CH1-4、及第6抗流線圈CH2-2之Ni-Zn系環狀 核心，係內徑爲約2 7亳米，相對磁導率// s爲約8 0 0，捲繞 著18圈電線來構成第2抗流線圈CH1-2、第4抗流線圈CH1-4、及第6抗流線圏CH2-2。此外，使用於第7抗流線圈 CH3-1、第8抗流線圈CH3-2、及第9抗流線圈CH3-3之Mn-Zn系環狀核心，係內徑爲約40亳米，相對磁導率v s爲約 5 00 0，捲繞著24圈電線來構成第7抗流線圈CH3-1、第8抗 流線圈CH3-2、及第9抗流線圈CH3-3。 如上所述之構成之本發明之第4實施例的雜音去除濾 波器4，因爲不但低通之衰減特性優良，高通之衰減特性 也十分優良，與第3實施例之雜音去除濾波器3相同，於約 0.2MHz〜約100MHz之寬頻帶，可以得到安定而大之衰減 量。此外，不論公用模式或正常模態之雜音，全部模態之 高頻雜音皆可去除。 以上說明之本發明的雜音去除濾波器，將電線捲繞 -20- 201230672 Μη·Ζη系環狀核心時，因爲Mn-Zn系之肥粒鐵的電阻率爲 較小之10〜數百Ω. cm，故採用於捲繞於Μη-Zn系環狀核 心之電線實施絕緣覆蓋之構造的電線。此外，雖然Ni-Zn 系之肥粒鐵的電阻率爲極高之1〇5Ω · cm以上，然而，爲了 防止捲繞電線彼此短路，捲繞於Ni-Zn系環狀核心之電線 ，也以採用實施絕緣覆蓋之構造的電線爲佳。 此外，上述之說明中，係採用環狀之環狀核心，然而 ，本發明並未受限於此，也可使用剖面形狀爲橢圓形或矩 形之環狀核心。此外，上述說明之環狀核心的形狀、尺寸 、及電線之捲數只是一例，本發明亦可以爲其他環狀核心 之形狀、尺寸、及電線捲數。此外，直列連接於輸出入端 子之間的抗流線圈之數亦可以爲4以上。此時’於高通’ 至少直列連接一個可得到優良衰減量之抗流線圈’而於低 通，也至少直列連接一個可得到優良衰減量之抗流線圈。 此外，藉由將平行電線捲繞於第1、2之輸出入端子共 用之環狀核心，可以成爲只去除公用模式雜音之公用模式 濾波器。 【圖式簡單說明】 第1圖係實現本發明之雜音去除濾波器之經過之未具 備電容之雜音去除濾波器的構成電路圖。 第2圖係第1圖所示之雜音去除濾波器之利用Mn-Zn系 之環狀核心時之衰減量的頻率特性圖。 第3圖係第1圖所示之雜音去除濾波器之利用Mn_Zr^^ -21 - 201230672 之環狀核心時之衰減量之其他的頻率特性圖。 第4圖係第1圖所示之雜音去除濾波器之利用Mn-Zn系 之其他之相對磁導率之環狀核心時之衰減量的頻率特性圖 〇 第5圖係第1圖所示之雜音去除濾波器之利用Mn-Zn系 之其他之相對磁導率之環狀核心時之衰減量之其他的頻率 特性圖。 第6圖係第1圖所示之雜音去除濾波器之利用Ni-Zn系 之環狀核心時之衰減量的頻率特性圖。 第7圖係第1圖所示之雜音去除濾波器之利用Ni-Zn系 之環狀核心時之衰減量之其他的頻率特性圖。 第8圖係本發明之第1實施例之雜音去除濾波器的構成 電路圖。 第9圖係本發明之第2實施例之雜音去除濾波器的構成 電路圖。 第10圖係本發明之第1實施例之雜音去除濾波器之衰 減量的頻率特性圖。 第11圖係本發明之第1實施例之雜音去除濾波器之衰 減量之其他的頻率特性圖。 第12圖係本發明之第3實施例之雜音去除濾波器的構 成電路圖。 第13圖係本發明之第4實施例之雜音去除濾波器的構 成電路圖。 第14圖係本發明之第3實施例之雜音去除濾波器之衰 -22- 201230672 減量的頻率特性圖。 第15圖係本發明之第3實施例之雜音去除濾波器之衰 減量之其他的頻率特性圖。 第16圖係傳統之基本LPF電路的構成電路圖。 第17圖係使用π型之LPF電路之傳統線路濾波器的構成 電路圖。 第18圖係使用Τ型之LPF電路之傳統線路瀘波器的構成 電路圖。 第19圖係只使用抗流線圈之傳統線路濾波器的構成電 路圖。 【主要元件符號說明】 1 :雜音去除濾波器 2 :雜音去除濾波器 3 :雜音去除濾波器 4 :雜音去除濾波器 1 〇 :屏蔽外殼 20 :屏蔽外殼 3 0 :屏蔽外殻 40 :屏蔽外殻 100 :雜音去除濾波器 200 :線路濾波器 300 :線路濾波器 400 :線路濾波器 -23- 201230672 410 :數據機 4 1 1 :第1抗流線圈 4 1 2 :第2抗流線圈 4 1 3 :插頭 -24-201230672 VI. Description of the Invention: [Technical Field] The present invention relates to a noise removing filter for removing common mode noise on at least two wires. [Prior Art] In recent years, solar panels have become very popular, and they have been actively used for the supplement of power consumption in homes and factories, and for the purpose of selling electricity. At this time, since the electric power generated by the solar panel is DC, in order to convert it into an AC power source of the same voltage as the commercial power source, a converter device called a power conditioner is provided. However, since the converter device interrupts the direct current with a chopper circuit, a pseudo-sine wave is created to convert direct current into alternating current, and intense harmonic noise occurs as the direct current of the chopper circuit is intermittent. The high-frequency noise is also reversed from the converter device to the solar panel side, and the high-frequency noise is radiated into the space by using a wire connecting the converter device and the solar panel as an antenna. Therefore, high-frequency noise is reduced by installing a line filter in the output portion of the converter device as a measure for preventing unnecessary radiation. However, in general, since a parallel electric wire is used as the power supply line, the transmission mode is equivalent to the normal mode (differential mode) of the balanced mode of the high-frequency circuit. At this time, for the noise component of the normal mode, it is easy to suppress the noise component by inserting a capacitance between the parallel wires. However, it is impossible to suppress the noise component of the common mode equivalent to the unbalanced mode of the high frequency circuit. In addition, parallel wires that transmit DC power generated by solar panels, -5-201230672, do not take into account high frequencies, nor do they take into account the common mode. Therefore, if a noise of the common mode occurs, even if a line filter is provided, it is radiated to the space without being sufficiently attenuated, and noise interference occurs. Therefore, since the noise of the common mode propagates on the parallel wires without the ground line, that is, in the common mode, it propagates on the incomplete line, and is in a situation where unnecessary radiation is likely to occur. When the high-frequency circuit performs an unbalanced transmission equivalent to the common mode, the low-pass filter (LPF) can be used to reduce the harmonic component with respect to the pass frequency. The conventional basic LPF circuit is shown in Figure 16 (a) and (b). The LPF circuit shown in Fig. 16(a) is a π type, and the inductor L201 is connected in series between the input terminal IN and the output terminal OUT, and between the two ends of the inductor L201 and the ground line, capacitors C201 and C202 are connected in parallel. . In addition, the LPF circuit shown in Figure 16 (b) is T-type, the inductors L202 and L203 are connected in series between the input terminal IN and the output terminal OUT, and the connection points of the inductors L202 and L203 are connected in parallel with the ground line. Capacitor C203. The LPF circuit as shown in Fig. 16 (a) (b) can be used as a line filter, using the circuit of the conventional line filter 200 of the π-type LPF circuit shown in Fig. 16 (a), Figure 17 shows. In the line filter 200 shown in FIG. 17, between the first input terminal IN 201 and the first output terminal OUT201, the inductor L2 10 is connected in series, and the two ends of the inductor L2 10 and the ground line E are juxtaposed. Connect capacitors C2 1 0, C2 1 1 . In addition, between the second input terminal IN202 and the second output terminal OUT202, the inductance L 2 1 1 is connected in series. The two ends of the inductor L 2 1 1 and the ground line E are respectively connected in parallel with the capacitors C212 and C213. . -6- 201230672 Next, the circuit of the conventional line filter 300 using the T-type LPF circuit shown in Fig. 16(b) is as shown in Fig. 18. The line filter 300 shown in Fig. 18 is connected between the first input terminal IN 301 and the first output terminal OUT30 1 in series with the inductance L3 1 0, L3 1 1 and the inductance L3 1 0 and L31 1 . Between the point and the ground line E, the capacitor C310 is connected in parallel. Further, between the second input terminal IN3 02 and the second output terminal OUT3 02, the inductors L312 and L313 are connected in series, and between the connection point of the inductors L312 and L313 and the ground line E, the capacitor C3 1 is connected in parallel. 1. The line filter 200 shown in Fig. 17 or the line filter 300 shown in Fig. 18 is connected to a parallel electric wire or the like, however, when parallel wires are present, there is no clear ground line necessary for the common mode. An unclear ground line, such as a stray capacitance between the ground and the ground. Therefore, when the line filters are 200 and 300, the ground E of the capacitors connected in parallel is incomplete, and the original electrical function cannot be exerted. Therefore, for the noise component of the common mode, the capacitance of the line filter 200 or the line filter 300 cannot be expected to attenuate the harmonic noise. Therefore, even if the parallel wires connecting the solar panel and the converter device are connected, the line filter 200 or the line filter 300 is connected, and the harmonic noise emitted by the converter device cannot be removed. The short-wavelength band is used in the main system close to the house. Cases in which radio waves are often generated in amateur radio stations, AM, short-wave, and FM-band radio broadcast waves. Therefore, it has been proposed in the past to apply the line filter 400 shown in Fig. 9 which uses only the anti-flow line 应用于 to the line filter for suppressing the common mode current. The line filter 400' shown in Fig. 9 is connected to the data 201230672, and is inserted into the power line for transmitting the communication signal. At the front end of the power line, a plug 413 is provided, and the plug 413 is inserted into the socket in the house. The line filter 400 is connected in series to the first choke coil 4 1 1 and the second choke coil 412, and the impedance of the first choke coil 41 1 disposed on the data processor 410 side is higher than the second choke coil. The impedance of the coil 4 1 2 . Therefore, the number of turns of the first choke coil 4 1 1 is larger than the number of turns of the second choke coil 41 2 . [Patent Document 1] Japanese Laid-Open Patent Publication No. 2006-166015. SUMMARY OF THE INVENTION In the conventional line filter 40 using only the choke coil shown in Fig. 9, the choke coil 41 2 disposed on the power line side is provided. The lower impedance is to reduce the adverse effects caused by the impedance mismatch with the power line. However, even if the impedance of the data unit 410 is already specified, the impedance of the power line is not specified, and the impedance of the power line is greatly different due to the wiring condition of the power line. Therefore, since the impedance of the power line is different in each place where the line filter 400 is provided, even if the line filter 400 is inserted into the power line, there is a problem that the high frequency noise caused by the impedance influence of the power line cannot be removed. . In addition, since the impedance of the solar panel and the converter device is not specified, even the conventional line filter 400 shown in FIG. 19 is disposed on the output of the parallel wire or converter device connected to the solar panel and the converter device. In addition, there is still the problem that the high frequency noise cannot be effectively removed due to the above reasons. Accordingly, it is an object of the present invention to provide a noise removing filter which can effectively remove high frequency noise. -8- 201230672 The main feature of the present invention is that a first anti-flow coil in which at least one of the conductor wires is wound around the ring-shaped core of the Mn-Zn system, and a conductor wound around the ring-shaped core of the Ni-Zn system The in-line connection circuit ' of at least one of the second choke coils of the line is connected between the input terminal and the output terminal, and the pair of input terminals and the output terminal are at least two pairs. According to the present invention, the first anti-flow coil in which the conductor wire is wound around the Mn-Zn-based annular core and the second anti-flow in which the conductor wire is wound around the Ni-Zn-based annular core are connected in series. The coil is configured to form a noise removing filter, and a large attenuation amount from a low pass to a high pass can be obtained. [Embodiment] To implement the noise removing filter of the present invention, as shown in the first to the first Figure 7 shows. Fig. 1 is a circuit diagram of a noise removing filter having no capacitance, and Fig. 2 is a relative magnetic permeability ys of a Mn-Zn (manganese/zinc) system using the noise removing filter shown in Fig. 1 A frequency characteristic diagram of the attenuation amount at a ring core of about 5,000, and Fig. 3 is a ring of about 5 000 in which the relative magnetic permeability β s of the Mn-Zn system is used in the noise removing filter shown in Fig. 1. The other frequency characteristic diagram of the attenuation amount at the core is 'Fig. 4'. The noise removal filter shown in Fig. 1 uses the Mn-Zn system whose relative magnetic permeability / / s is a ring core of about 2,500. The frequency characteristic diagram of the attenuation amount is shown in Fig. 5 as the other frequency characteristic of the noise removal filter using the Mn_Zn system whose relative magnetic permeability # s is a ring core of about 2500. Fig. 6 is a diagram showing the fading of the noise removal filter shown in Fig. 1 using the Ni-Zn (nickel -9-201230672 zinc) system whose relative magnetic permeability # s is a ring core of about 800 The frequency characteristic map of the decrement, Fig. 7, is the magnetic permeability of the noise removal filter shown in Fig. 1 using the Ni-Zn system "s is about 800 Other frequency attenuation characteristic diagram of the time-like core. The noise removing filter 1A having the configuration shown in Fig. 1 is a noise removing filter when two wires such as parallel wires and power lines are used. The noise removing filter 100 is connected between the first current blocking coil CH1 connected between the first input terminal IN1 and the first output terminal OUT1, and between the second input terminal IN2 and the second output terminal OUT2. The second choke coil CH2 is constructed. The first choke coil CH 1 and the second choke coil CH2' are formed by winding an electric wire around the annular core. The wire can be a single wire or a stranded wire. The ring core of this specification refers to a core in which a composite ferrite of Mn-Zn or Ni-Zn is sintered at a high temperature into a ring. The Mn-Zn system is used as a ring-shaped core having an inner diameter of about 40 mm and a relative magnetic permeability A s of about 5,000. The electric coil is wound 24 times to form the first choke coil CH1 and the second. The frequency characteristic of the attenuation amount of the noise-removing coil CH2 » which is composed of the first choke coil CH1 and the second choke coil CH2 up to 1 MHz is as shown in Fig. 2, and the scale is changed. The frequency characteristics of the attenuation amount up to 1 0 0 Μ Η z are as shown in Fig. 3. Referring to Fig. 2, the peak 値' of the attenuation of about 39 dB around 0.3 MHz has a good attenuation characteristic up to 1 Μ Η z. Further, the term "refer to Fig. 3" decreases as the frequency increases, and the amount of attenuation decreases by about 40 MHz to about 14 dB. Further, when the frequency of 40 MHz or more is gradually increased by about 90 MHz, there is a peak, but only about 22 degrees of attenuation is obtained. It is a noise removal filter 100 using a Mn-Zn system with a relative magnetic permeability μ s of about 5,000. The low-pass attenuation characteristic is excellent, and the high-pass portion is only available at around 40 MHz. With an attenuation of about 14 dB, it can be known that the attenuation characteristics of Qualcomm are poor. Next, a first anti-flow coil CH1 is formed by winding 22 turns of an electric wire with an inner diameter of about 301 nm and a ring-shaped core having a relative magnetic permeability μ s of about 2,500 as a ring-shaped core. The second choke coil CH2. The frequency characteristic of the attenuation amount up to 1 MHz by the noise removing filter 1B composed of the first choke coil CH1 and the second choke coil CH2 is as shown in Fig. 4, and the deterioration of the scale to 100 MHz is changed. The frequency characteristics of the decrement are shown in Figure 5. Referring to Fig. 4, the peak value of the attenuation of about 48 dB around 0.8 MHz represents a good attenuation characteristic up to 1 MHz. Further, referring to Fig. 5, as the frequency increases, the amount of attenuation decreases, the attenuation of about 35 MHz drops to about 17 dB, and at about 70 MHz, the amount of attenuation also drops to about 16 dB. Moreover, at frequencies above 70 MHz, the amount of attenuation gradually increases. At about 100 MHz, although there is a peak, only about 21 dB of attenuation is obtained. Therefore, the noise removing filter 100 of the ring core having a relative magnetic permeability / / s of about 260 is used, and the low-pass attenuation characteristic is excellent, and the high-pass portion can obtain only about 16 dB in the vicinity of 70 MHz. The attenuation amount can be known to be poor in the attenuation characteristics of Qualcomm. Next, a Ni-Zn-based annular core having an inner diameter of about 27 mm and a relative magnetic permeability //s of about 800 is wound around an electric coil to form a first anti-current coil CH1 and The second choke coil CH2. The frequency characteristic of the attenuation amount of the noise removing filter 1 including the first choke coil CH1 and the second choke coil CH2 up to 1 MHz is as shown in Fig. 6, and the scale is changed from -11 - 201230672 to The frequency characteristics of the attenuation up to 100 MHz are shown in Figure 7. Referring to Fig. 6, the attenuation amount is gradually increased. However, the attenuation around 1 MHz is only about 23 dB, and the attenuation characteristic is poor until 1 MHz. Further, referring to Fig. 7, as the frequency increases, the amount of attenuation increases, and the amount of attenuation around the periphery of 35 MHz increases to about 46d. At this time, an attenuation amount of 40 dB or more can be obtained in a wide frequency band of about 7 MHz to about 55 MHz. Moreover, at frequencies above 60 MHz, the amount of attenuation gradually decreases, and at about 95 MHz, only about 12 dB of attenuation is obtained. Therefore, the noise removal filter 100 using a Ni-Zn-based ring-shaped core having a relative magnetic permeability ys of about 800 is excellent in attenuation characteristics of the high-pass, but the low-pass portion can only obtain an attenuation amount of about 20 dB before and after. It is known that the low-pass attenuation characteristics are poor. As described above, it has been found that the Mn-Zn-based ring core and the Ni-Zn-based ring core have different frequency characteristics of the attenuation amount. Therefore, the circuit diagram of the noise removing filter 1 of the first embodiment of the present invention is As shown in Figure 8. The noise removing filter 1 of the first embodiment shown in Fig. 8 is a noise removing filter when two parallel wires and electric wires are used. The noise removing filter 1 of the first embodiment is connected in series; the first choke coil CH 1 -1 is formed by winding a wire around a Mn-Zn ring core having excellent low-pass attenuation characteristics; And a second choke coil CH1-2 composed of a Ni-Zn-based annular core having a high-pass attenuation characteristic of a high-pass, and is connected between the first input terminal IN1 and the first output terminal OUT1. Further, the third anti-current coil CH 1 -3 composed of a Mn-Zn-based annular core excellent in attenuation characteristics in which the electric wire is wound around the low-pass is wound in series; and the attenuation by winding the electric wire around the high-pass The fourth anti--12-201230672 current coil CHI-4 composed of a Ni-Zn-based annular core having excellent characteristics is connected between the second input terminal IN2 and the second output terminal OUT2. The electric wire wound around the first choke coil CH1-1 to the fourth choke coil CiU-4 may be a single wire or a stranded wire. The first choke coil CH 1-1 to the fourth choke coil CH 1-4 are housed in the shield case 1A. When an example of the method of using the noise removing filter 1 of the first embodiment described above is described, the first input terminal IN 1 and the second input terminal IN2 of the first noise removing filter 1 are as follows. For example, the output side of the converter device is connected to the first output terminal OUT1 and the second output terminal OUT2 of the noise removing filter 1, and two wires such as parallel wires and power lines are connected. Further, the first output terminal OUT1 and the second output terminal OUT2 of the second noise removing filter 1 are connected to, for example, the input side of the converter device, and the first input terminal IN1 of the noise removing filter 1 is connected. And the second input terminal IN2 is connected to two electric wires connected to parallel wires or the like of the solar panel. Therefore, the noise removing filter 1 is connected to the input side and the output side of the converter device where the noise is generated, and the high frequency noise generated by the converter device is prevented as much as possible, and the wire connected to the solar panel or A power line connected to the converter device is radiated. Here, an example of a specific configuration of the noise removing filter 1 of the first embodiment will be described. The Mn-Zn-based annular core used in the first choke coil CH 1 -1 and the third choke coil CH 1-3 has an inner diameter of about 31 'm and a relative magnetic permeability / zs of about 2,500. The first choke coil CH 1 -1 and the third choke coil CH 1 -3 are formed around 22 coils of electric wire. Further, the Ni-Zn-based annular core used in the second choke coil CH1-2 and the fourth choke coil 1-4CH1-4 has an inner diameter of about 27 mm and a relative magnetic permeability of about 800 Å. The 18-turn wire constitutes the -13-201230672 second choke coil CHI-2 and the fourth choke coil CHI-4. The frequency characteristic of the attenuation amount up to 1 MHz of the noise removing filter 1 of the first embodiment constituted by the first choke coil CH1-1 to the fourth choke coil CH1-4 configured as described above is as shown in FIG. The frequency characteristics of the attenuation amount up to the 10 0 MHz as shown in the figure are shown in Fig. 11. Referring to Fig. 10, the attenuation amount is gradually increased until about 〇·8ΜΗζ, and there is a peak of about 44 dB of attenuation around 0.8 MHz, indicating that there is good attenuation characteristics up to 1 MHz. Further, referring to Fig. 1, the attenuation amount is reduced to about 35 dB' at around 2.3 MHz. However, at the above frequencies, the attenuation amount is increased by □, and the attenuation amount is increased to about 58 dB around 35 MHz. At this time, a wide band of about 4 MHz to 75 MHz can obtain a attenuation of 40 dB or more. Also, at frequencies above 80 MHz, the amount of attenuation gradually decreases, and at about 95 MHz, the amount of attenuation is reduced to about 25 dB. Therefore, the noise removing filter 1 of the first embodiment of the present invention has excellent low-pass attenuation characteristics and excellent high-pass attenuation characteristics, and can be stabilized in a wide frequency band of about 0.5 MHz to about 90 MHz. And the amount of attenuation. In addition, all modal high-frequency noise can be removed regardless of the common mode or normal mode noise. Next, a circuit diagram of the configuration of the noise removing filter 2 of the second embodiment of the present invention is shown in Fig. 9. The noise removing filter 2 of the second embodiment shown in Fig. 9 is a noise removing filter when three wires including a grounding wire such as a parallel electric wire and a power line are used. In the noise removing filter 2 of the second embodiment, for the purpose of removing high-frequency noise on the ground line, in the noise removing filter of the first embodiment - 14 to 201230672, it is added that the electric wire is wound around the Mn_Zn ring. The fifth choke coil CH2-1 composed of the core and the sixth choke coil CH2-2 formed by winding the electric wire around the Ni-Zn loop core are connected in series to the third line connected to the ground line. The configuration between the input terminal IN3 and the third output terminal OUT3 is the same as that of the noise removing filter 1 of the first embodiment. The electric wire wound around the first choke coil CH1-1 to the sixth choke coil CH2-2 may be a single wire or a stranded wire. The first choke coil CH 1 -1 to the sixth choke coil CH2-2 are housed in the shield case 20. When an example of the method of using the noise removing filter 2 of the second embodiment described above is described, the first input terminal IN1 and the second input terminal IN2 of the first noise removing filter 2 are as follows. For example, it is connected to the output side of the converter device, and the third input terminal IN3 is connected to the ground line of the converter device, and the first output terminal OUT 1 and the second output terminal OUT2 of the noise removing filter 2 are connected. Connect two wires such as parallel wires and power wires, and connect the ground wires to the third output terminal OUT3. Further, the first output terminal OUT1 and the second output terminal OUT2 of the second noise removing filter 2 are connected to, for example, the input side of the converter device, and the third output terminal OUT3 is connected to the variable current. The grounding line of the device is connected to two electric wires connected to the parallel wires of the solar panel, and the third input terminal IN3, respectively, at the first input terminal IN1 and the second input terminal IN2 of the noise removing filter 2. Then connect the ground wire. Therefore, by connecting the noise removing filter 2' to the input side and the output side of the converter device in which the noise is generated, the high frequency noise generated by the converter device is prevented as much as possible, and the wire connected to the solar panel is connected or connected to Converter -15- 201230672 The power line is emitted. In addition, when there are only two wires connecting the solar panel and the converter device without a grounding wire, the noise removing filter 1 of the first embodiment is connected to the input side of the converter device, and the solar panel is connected by two wires. Just fine. Here, an example of a specific configuration of the noise removing filter 2 of the second embodiment will be described. The Mn-Zn-based annular core used in the first choke coil CH 1 -1, the third choke coil CH1-3, and the fifth choke coil CH2-1 has an inner diameter of about 31 nm and a relative magnetic The conductivity # s is about 2,500, and 22 turns of electric wires are wound to form the first choke coil CH1-1, the third choke coil CH1-3, and the fifth choke coil CH2-1. Further, the Ni-Zn-based annular core used in the second choke coil CH1-2, the fourth choke coil CH1-4, and the sixth choke coil CH2-2 has an inner diameter of about 27 mm, and is relatively The magnetic permeability # s is about 800, and 18 coils of electric wires are wound to form the second choke coil CH1-2, the fourth choke coil CH1-4, and the sixth anti-flow coil CH2-2. The noise removing filter 2 of the second embodiment of the present invention having the above-described configuration is excellent in attenuation characteristics of low-pass, and excellent in attenuation characteristics of high-pass, and is the same as the noise removing filter 1 of the first embodiment. In a wide frequency band of about 0.5 MHz to about 90 MHz, a stable and large attenuation can be obtained. In addition, all modes of high-frequency noise can be removed regardless of the common mode or the normal mode noise. Next, a circuit diagram of the configuration of the noise removing filter 3 of the third embodiment of the present invention is shown in Fig. 12. The noise removing filter 3 of the third embodiment shown in Fig. 2 is a noise removing filter when two wires such as parallel wires and power lines are used. 3 - 16 - 201230672 The noise removing filter 3 of the embodiment is the noise removing filter 1 of the first embodiment, and the attenuation characteristic of the in-line connection low-pass is added before the first current-carrying coil CH 1 -1 The excellent relative magnetic permeability is different from that of the first choke coil CH1-1 by winding the electric wire around the 抗η-Ζη-ring core, the fifth choke coil CH3-1; and the third choke coil 圏Before CH 1 -3, the relative magnetic permeability of the in-line connection low-pass attenuation characteristic is different from that of the third anti-current coil CH1-3, which is formed by winding the electric wire around the Μη-Ζη-ring core. The configuration of the coil CH3-2; the other configuration is the same as that of the noise removing filter 1 of the first embodiment. Further, the electric wires wound around the first choke coil CH 1-1 to the sixth choke coil CH3-2 may be single wires or stranded wires. The first choke coil CH1-1 to the sixth choke coil CH3-2 are housed in the shield case 30. The method of using the noise removing filter 3 of the third embodiment described above is the same as that of the noise removing filter 1 of the first embodiment. Although the detailed description is omitted, the high-frequency noise generated by the converter device can be prevented as much as possible by connecting the noise removing filter 3 to the input side and the output side of the converter device in which the noise is generated, and is connected to the solar panel. The wires and the power lines connected to the converter device are radiated. Here, an example of a specific configuration of the noise removing filter 3 of the third embodiment will be described. The Μη-Ζη-ring core used in the first anti-flow line 圏CH1-1 and the third choke coil CH 1-3 has an inner diameter of about 31 'm and a relative magnetic permeability V s of about 2 50. 0, the second coil wire is wound around the second choke coil CH 1 -1 and the third choke coil CH 1 -3. Further, the Ni-Zn system-shaped core core used in the second choke coil CH1-2 and the fourth choke coil CH1-4 has an inner diameter of about 27 mm and a relative magnetic permeability of about 800. 18-ring wire is used to construct -17-201230672 into the second anti-flow coil CHI-2 and the fourth anti-flow coil CHI-4. Further, the Mn-Zn-based annular core used in the fifth anti-flow line 圏CH3-1 and the sixth choke coil CH3-2 has an inner diameter of about 40 亳m and a relative magnetic permeability # s of about 5 0 0 0 'The 4th coil wire is wound to form the 5th choke coil C Η 3 -1 and the third choke coil CH3-2. The frequency characteristic of the attenuation amount up to 1 MHz of the noise removing filter 3 of the third embodiment constituted by the first choke coil CH 1-1 to the sixth choke coil CH 3-2 configured as described above As shown in Fig. 14, the frequency characteristics of the attenuation amount up to the frequency of 1000 MHz are as shown in Fig. 15. Referring to Fig. 14, the amount of attenuation increases rapidly to about 0.2 MHz, and an attenuation of about 40 dB can be obtained around 0.2 MHz. Further, as the frequency increases, the amount of attenuation increases, and around the 0.8 MHz, there is a peak of about 51 dB of attenuation, indicating that there is good attenuation characteristics up to 1 MHz. Further, referring to Fig. 14, the attenuation amount is reduced to about 42 dB in the vicinity of 2.3 MHz, however, at the above frequencies, the attenuation amount is increased, and the attenuation amount is increased to about 7 OdB around the periphery of about 30 MHz. When the frequency exceeds 30 MHz, the amount of attenuation gradually decreases. However, up to about 100 dB, a reduction of about 49 dB or more can be obtained. Therefore, an attenuation of more than 4 OdB can be obtained in a wide frequency band of about 0.2 MHz to about 100 MHz. Therefore, the noise removing filter 3 of the third embodiment of the present invention has excellent low-pass attenuation characteristics and high-pass attenuation characteristics, and can be stabilized and wide in a wide frequency band of about 0.2 MHz to about 100 MHz. The amount of attenuation. In addition, high-frequency noise of all modes can be removed regardless of the common mode or the normal mode noise. Next, the configuration of the noise removing filter 4 of the fourth embodiment of the present invention is shown in Fig. 13 of the circuit diagram of 18-201230672. The noise removing filter 4 of the fourth embodiment shown in Fig. 13 is a noise removing filter when three wires including a ground wire such as a parallel wire and a power line are used. The noise removing filter 4 of the fourth embodiment is a noise removing filter 2 of the second embodiment, and a magnetic field having excellent attenuation characteristics of a low-pass in-line connection before the first current-carrying coil CH 1 -1 is added. The conductivity is different from that of the first choke coil CH1-1 by winding the electric wire around the Mn-Zn-based core core, and the seventh choke coil CH3-1; before the third choke coil CH1-3, the in-line The relative magnetic permeability excellent in the attenuation characteristic of the connection low-pass is different from that of the third choke coil CH 1-3 by winding the electric wire around the Mn-Zn-based annular core, the eighth choke coil CH3-2; Before the fifth choke coil CH2-1, the relative magnetic permeability of the in-line connection low-pass attenuation characteristic is different from that of the fifth anti-current coil CH2-1, and the electric wire is wound around the Mn-Zn-based annular core. The configuration of the ninth choke coil CH3-3 is the same as that of the noise removing filter 2 of the second embodiment. Further, the electric wires wound around the first choke coil CH1·1 to the ninth choke coil CH3-3 may be single wires or stranded wires. The first dam graph CH1-1 to the ninth choke coil CH3-3 are housed in the shield case 40. The method of using the noise removing filter 4 of the fourth embodiment described above is the same as that of the noise removing filter 2 of the second embodiment. Although the detailed description is omitted, the high-frequency noise generated by the converter device can be prevented as much as possible by connecting the noise removing filter 4 to the input side and the output side of the converter device in which the noise is generated, and is connected to the solar panel. The wires and the power lines connected to the converter device are radiated. In addition, when there are only two wires connecting the -19-201230672 solar panel and the converter device without the grounding wire, the noise removing filter 3 of the third embodiment is connected to the input side of the converter device, and then 2 wires can be connected to the solar panel. Here, an example of a specific configuration of the noise removing filter 4 of the fourth embodiment will be described. The Mn-Zn-based annular core used in the first choke coil CH 1 -1, the third choke coil 1-3CH1-3, and the fifth choke coil CH2-1 has an inner diameter of about 31 ,m, and is relatively The magnetic permeability is about 2,500, and 22 coils of electric wires are wound to form the first choke coil CH 1 -1, the third choke coil CH 1 -3, and the fifth choke coil CH2-1. Further, the Ni-Zn-based annular core used in the second choke coil CHb2, the fourth choke coil CH1-4, and the sixth choke coil CH2-2 has an inner diameter of about 27 mm. The relative magnetic permeability / / s is about 800, and the 18th coil wire is wound to form the second choke coil CH1-2, the fourth choke coil CH1-4, and the sixth choke coil CH2-2. Further, the Mn-Zn-based annular core used in the seventh choke coil CH3-1, the eighth choke coil CH3-2, and the ninth choke coil CH3-3 has an inner diameter of about 40 mils, and is relatively The magnetic permeability vs. is about 50,000, and 24 turns of electric wires are wound to constitute the seventh choke coil CH3-1, the eighth choke coil CH3-2, and the ninth choke coil CH3-3. The noise removing filter 4 of the fourth embodiment of the present invention having the above-described configuration is excellent in attenuation characteristics of low-pass, and excellent in attenuation characteristics of high-pass, and is the same as the noise removing filter 3 of the third embodiment. In the wide frequency band of about 0.2 MHz to about 100 MHz, a stable and large attenuation can be obtained. In addition, all modes of high frequency noise can be removed regardless of the common mode or normal mode noise. In the noise removing filter of the present invention described above, when the electric wire is wound around the -20-201230672 Μη·Ζη-based core, the resistivity of the Mn-Zn-based ferrite is 10 to hundreds of Ω. In the case of cm, an electric wire having a structure in which an electric wire wound around a Μη-Zn-based annular core is insulated is used. In addition, although the resistivity of the Ni-Zn-based ferrite is extremely high at 1〇5 Ω·cm or more, in order to prevent the wound wires from being short-circuited to each other, the wires wound around the Ni-Zn-based core are also It is preferable to use an electric wire having a structure in which insulation is applied. Further, in the above description, a ring-shaped annular core is used. However, the present invention is not limited thereto, and a ring-shaped core having an elliptical or rectangular cross-sectional shape may be used. Further, the shape, size, and number of windings of the annular core described above are merely examples, and the present invention may also be the shape, size, and number of coils of other annular cores. Further, the number of the anti-flow coils connected in series between the input and output terminals may be 4 or more. At this time, 'the high-pass' is connected at least in series with a choke coil ‘which can obtain an excellent attenuation amount, and at the low pass, and at least one anti-flow coil which can obtain an excellent attenuation amount is connected in series. Further, by winding a parallel electric wire around the ring core shared by the first and second output terminals, it is possible to use a common mode filter which removes only the common mode noise. BRIEF DESCRIPTION OF THE DRAWINGS Fig. 1 is a circuit diagram showing a configuration of a noise removing filter having no capacitance which is passed through the noise removing filter of the present invention. Fig. 2 is a frequency characteristic diagram showing the attenuation amount when the Mn-Zn-based annular core is used as the noise removing filter shown in Fig. 1. Fig. 3 is another frequency characteristic diagram of the attenuation amount when the ring-shaped core of Mn_Zr^^ -21 - 201230672 is used as the noise removing filter shown in Fig. 1. Fig. 4 is a frequency characteristic diagram of the attenuation amount when the ring-shaped core of the Mn-Zn-based other relative magnetic permeability is used as the noise removing filter shown in Fig. 1. Fig. 5 is a view showing Fig. 1 Another frequency characteristic diagram of the attenuation amount of the noise removing filter using the ring core of the other relative magnetic permeability of the Mn-Zn system. Fig. 6 is a graph showing the frequency characteristics of the attenuation amount when the ring-shaped core of the Ni-Zn system is used as the noise removing filter shown in Fig. 1. Fig. 7 is a view showing another frequency characteristic of the attenuation amount when the Ni-Zn system is used as the noise removing filter shown in Fig. 1. Fig. 8 is a circuit diagram showing the configuration of a noise removing filter according to a first embodiment of the present invention. Fig. 9 is a circuit diagram showing the configuration of a noise removing filter according to a second embodiment of the present invention. Fig. 10 is a graph showing the frequency characteristics of the attenuation of the noise removing filter of the first embodiment of the present invention. Fig. 11 is a view showing another frequency characteristic of the amount of attenuation of the noise removing filter of the first embodiment of the present invention. Fig. 12 is a block diagram showing the construction of a noise removing filter according to a third embodiment of the present invention. Figure 13 is a block diagram showing the construction of a noise removing filter of a fourth embodiment of the present invention. Fig. 14 is a diagram showing the frequency characteristic of the reduction of the noise removing filter of the third embodiment of the present invention -22-201230672. Fig. 15 is a view showing another frequency characteristic of the attenuation amount of the noise removing filter of the third embodiment of the present invention. Fig. 16 is a circuit diagram showing the structure of a conventional basic LPF circuit. Fig. 17 is a circuit diagram showing a configuration of a conventional line filter using a π-type LPF circuit. Fig. 18 is a circuit diagram showing a configuration of a conventional line chopper using a LPF circuit of a Τ type. Figure 19 is a circuit diagram of a conventional line filter using only a choke coil. [Main component symbol description] 1 : Noise removal filter 2 : Noise removal filter 3 : Noise removal filter 4 : Noise removal filter 1 〇: Shielding case 20 : Shielding case 3 0 : Shielding case 40 : Shielding case 100 : noise removal filter 200 : line filter 300 : line filter 400 : line filter -23 - 201230672 410 : data machine 4 1 1 : first choke coil 4 1 2 : second choke coil 4 1 3 : Plug-24-