KR20200127709A - Active current compensation device - Google Patents

Abstract

The present invention provides a current compensation device which actively compensates for a first current inputted in a common mode to each of at least two large current paths connected to a first device. The current compensation device comprises: at least two large current paths transmitting a second current supplied by a second device to a first device; a sensing unit sensing a first current in a large current path to generate an output signal corresponding to the first current; an amplification unit amplifying the output signal of the sensing unit to generate an amplification current; a compensation unit generating a compensation current based on the amplification current and allowing the compensation current to flow to each of the at least two large current paths; and a decoupling capacitor unit configured to satisfy a predetermined condition for an output impedance from the compensation unit to the second device.

Description

Active current compensation device {ACTIVE CURRENT COMPENSATION DEVICE}

Embodiments of the present invention relate to an active current compensating device, and to an active current compensating device for actively compensating a current input in a common mode on two or more large current paths connecting two devices.

In general, electric appliances such as home appliances, industrial electric appliances, and electric vehicles emit noise during operation. For example, noise may be emitted through the power line due to the switching operation of the power conversion device in the electronic device. If such noise is left unattended, it is not only harmful to the human body, but also causes malfunction or failure of peripheral parts and other electronic devices. As such, electromagnetic interference from an electronic device to other devices is referred to as EMI (Electromagnetic Interference), and among them, noise transmitted through wires and board wiring is referred to as Conducted Emission (CE) noise.

In order to ensure that electronic devices operate without causing breakdowns in peripheral components and other devices, EMI noise emission levels are strictly regulated in all electronic products. Therefore, most electronic products essentially include a noise reduction device (eg, an EMI filter) that reduces the EMI noise current in order to satisfy the regulation on the amount of noise emission. For example, in white home appliances such as air conditioners, electric vehicles, aviation, energy storage systems (ESS), and the like, an EMI filter is essentially included. Conventional EMI filters use a common mode choke (CM choke) to reduce common mode (CM) noise among conductive emission (CE) noise. The common mode (CM) choke is a passive filter and serves to suppress the common mode noise current.

The present invention was conceived to improve the above problems, and an object of the present invention is to provide an active current compensation device that outputs a compensation current to the side from which EMI noise is emitted, regardless of the size of the load on the side from which EMI noise is emitted. do. However, these problems are exemplary, and the scope of the present invention is not limited thereby.

According to an embodiment of the present invention, an active current compensating device for actively compensating for a first current input in a common mode to each of at least two or more high current paths connected to a first device is provided by the second device. At least two or more high current paths for transferring supplied second current to the first device; A sensing unit that senses the first current on the high current path and generates an output signal corresponding to the first current; An amplifying unit generating an amplified current by amplifying the output signal of the sensing unit; And a compensation unit generating a compensation current based on the amplified current and flowing a compensation current through each of the at least two large current paths. It may include.

According to an embodiment, it may further include a decoupling capacitor unit provided to adjust the output impedance from the compensation unit to the second device side.

According to an embodiment, the output impedance may be a combined impedance of an impedance of the second device and an impedance of the decoupling capacitor.

According to an embodiment, the compensation unit passes the compensation current to each of the at least two large current paths through the compensation capacitor unit, and the decoupling capacitor unit includes each of the at least two large current paths connecting the second device and the compensation capacitor unit. It may include at least two or more capacitors disposed on the path branching from.

According to an embodiment, the impedance of the at least two capacitors may be smaller than a threshold impedance within a certain frequency band.

Other aspects, features, and advantages other than those described above will become apparent from the following drawings, claims, and detailed description of the invention.

According to various embodiments of the present invention made as described above, it is possible to provide a current compensation device that does not significantly increase in price, area, volume, and weight even in a high power system. Specifically, the active current compensation device according to various embodiments may have a reduced price, area, volume, and weight compared to a passive filter including a CM choke.

In addition, the current compensating device according to various embodiments of the present disclosure may provide an active current compensating device capable of independently operating without parasitic to a CM choke.

In addition, the active current compensation device according to various embodiments of the present disclosure has an active circuit terminal electrically insulated from a power line, thereby stably protecting elements included in the active circuit stage.

Through this, the present invention can stably operate irrespective of the characteristics of the surrounding electrical system, has versatility as an independent component, and can provide a current compensation device that can be commercialized as an independent module.

Through this, the present invention can provide a current compensation device capable of performing a current compensation function regardless of the load in the surrounding situation on the side from which the EMI noise is emitted.

Of course, the scope of the present invention is not limited by these effects.

1 schematically shows the configuration of a system including an active current compensation device 100 according to an embodiment of the present invention.
FIG. 2 schematically shows a specific example of the active current compensation device 100A according to the embodiment shown in FIG. 1.
3 schematically shows the configuration of a system including the active current compensation device 100 according to another embodiment of the present invention.
4 schematically shows a specific example of the active current compensation device 100A according to the embodiment shown in FIG. 3.
5 schematically shows an active current compensation device 100A-1 according to another embodiment of the present invention.
6 schematically shows an active current compensation apparatus 100A-2 according to another embodiment of the present invention.
7 schematically shows an active current compensation device 100A-3 according to another embodiment of the present invention.
8 schematically shows a configuration of an active current compensation device 100C according to another embodiment of the present invention.
9 schematically shows a configuration of an active current compensation device 100D according to another embodiment of the present invention.

Since the present invention can apply various transformations and have various embodiments, specific embodiments are illustrated in the drawings and will be described in detail in the detailed description. Effects and features of the present invention, and a method of achieving them will be apparent with reference to the embodiments described later in detail together with the drawings. However, the present invention is not limited to the embodiments disclosed below and may be implemented in various forms.

Hereinafter, embodiments of the present invention will be described in detail with reference to the accompanying drawings, and when describing with reference to the drawings, the same or corresponding constituent elements are assigned the same reference numerals, and redundant descriptions thereof will be omitted. .

In the following embodiments, terms such as first and second are not used in a limiting meaning, but are used for the purpose of distinguishing one component from another component. In the following examples, the singular expression includes the plural expression unless the context clearly indicates otherwise. In the following embodiments, terms such as include or have means that the features or elements described in the specification are present, and do not preclude the possibility of adding one or more other features or elements in advance. In the drawings, components may be exaggerated or reduced in size for convenience of description. When a certain embodiment can be implemented differently, a specific process order may be performed differently from the described order. In the following embodiments, when a region, component, unit, unit, module, etc. are connected, not only the case where the region, component, unit, unit, module are directly connected, but also the region, component, unit, unit, module, etc. Other areas, components, units, units, and modules are interposed in the middle of them and are indirectly connected.

1 schematically shows the configuration of a system including an active current compensation device 100 according to an embodiment of the present invention. The active current compensation device 100 includes first currents I11 and I12 inputted in a common mode (CM) from the first device 300 through two or more high current paths 111 and 112 (e.g., EMI Noise current) can be actively compensated.

Referring to FIG. 1, the active current compensation device 100 may include a sensing unit 120, an amplifying unit 130, and a compensation unit 160.

In this specification, the first device 300 may be various types of devices that use power supplied by the second device 200. For example, the first device 300 may be a load that is driven using power supplied by the second device 200. In addition, the first device 300 may be a load (eg, an electric vehicle) that stores energy using power supplied by the second device 200 and is driven using the stored energy. However, it is not limited thereto.

In the present specification, the second device 200 may be various types of devices for supplying power to the first device 300 in the form of current and/or voltage. For example, the second device 200 may be a device that produces and supplies power, or may be a device that supplies power produced by another device (eg, an electric vehicle charging device). Of course, the second device 200 may be a device that supplies stored energy. However, it is not limited thereto. A power conversion device may be located on the side of the first device 300. For example, the first currents I11 and I12 may be input to the current compensating device 100 by the switching operation of the power conversion device. That is, the first device 300 side may correspond to the noise source, and the second device 200 side may correspond to the noise receiver.

The two or more high current paths 111 and 112 may be paths that deliver power supplied by the second device 200, that is, the second currents I21 and I22, to the first device 300, for example, a power line. have. For example, each of the two or more high current paths 111 and 112 may be a live line and a neutral line. At least a portion of the high current paths 111 and 112 may pass through the current compensation device 100. The second currents I21 and I22 may be AC currents having a frequency in the second frequency band. The second frequency band may be, for example, 50Hz to 60Hz band.

Also, the two or more high current paths 111 and 112 may be paths through which noise generated by the first device 300, that is, the first currents I11 and I12, is transmitted to the second device 200. The first currents I11 and I12 may be input to each of the two or more large current paths 111 and 112 in a common mode. The first currents I11 and I12 may be currents unintentionally generated in the first device 300 due to various causes. For example, the first currents I11 and I12 may be noise currents generated by a virtual capacitance between the first device 300 and the surrounding environment. Alternatively, the first currents I11 and I12 may be noise currents generated by a switching operation of the power conversion device of the first device 300. The first currents I11 and I12 may be currents having a frequency in the first frequency band. The first frequency band may be a higher frequency band than the aforementioned second frequency band. The first frequency band may be, for example, a 150KHz to 30MHz band.

Meanwhile, two or more high-current paths 111 and 112 may include two paths as shown in FIG. 1, or three paths or four paths as shown in FIGS. 8 and 9. The number of high current paths 111 and 112 may vary according to the type and/or type of power used by the first device 300 and/or the second device 200.

The sensing unit 120 may sense the first currents I11 and I12 on two or more high current paths 111 and 112 and generate an output signal corresponding to the first currents I11 and I12. That is, the sensing unit 120 may mean a means for sensing the first currents I11 and I12 on the high current paths 111 and 112. In the sensing unit 120, at least a part of the high current paths 111 and 112 may pass for sensing the first currents I11 and I12, but an output signal is generated by sensing in the sensing unit 120. The portion may be insulated from the high current paths 111 and 112. For example, the sensing unit 120 may be implemented as a sensing transformer. The sensing transformer may sense the first currents I11 and I12 on the high current paths 111 and 112 in a state insulated from the high current paths 111 and 112.

According to an embodiment, the sensing unit 120 may be differentially connected to the input terminal of the amplifying unit 130.

The amplifying unit 130 may be electrically connected to the sensing unit 120 to amplify the output signal output from the sensing unit 120 to generate an amplified output signal. In the present invention,'amplification' by the amplifying unit 130 may mean adjusting the size and/or phase of the amplification target. The amplification unit 130 may be implemented by various means, and may include an active element. In an embodiment, the amplification unit 130 may include an OP-AMP. For example, the amplification unit 130 may include a plurality of passive elements such as a resistor and a capacitor in addition to the OP-AMP. In another embodiment, the amplification unit 130 may include a Bipolar Junction Transistor (BJT). For example, the amplification unit 130 may include a plurality of passive elements such as a resistor and a capacitor in addition to the BJT. However, the present invention is not limited thereto, and the means for'amplification' described in the present invention may be used without limitation as the amplifying unit 130 of the present invention. The reference potential (reference potential 2) of the amplifying unit 130 and the reference potential (reference potential 1) of the current compensating device 100 may be different potentials.

The amplifying unit 130 amplifies and amplifies the output signal output from the sensing unit 120 by receiving power from the first device 300 and/or the third device 400 separated from the second device 200 It can generate electric current. In this case, the third device 400 may be a device that receives power from a power source irrelevant to the first device 300 and the second device 200 to generate input power to the amplifying unit 130. Optionally, the third device 400 may be a device that receives power from one of the first device 300 and the second device 200 and generates input power to the amplifying unit 130.

The compensation unit 160 may generate a compensation current based on the output signal amplified by the amplification unit 130. The output side of the compensation unit 160 may be connected to the high current paths 111 and 112 to pass the compensation currents IC1 and IC2 to the high current paths 111 and 112, but may be insulated from the amplification unit 130. For example, the compensation unit 160 may include a compensation transformer for the insulation. For example, an output signal of the amplifying unit 130 may flow through a primary side of the compensation transformer, and a compensation current based on the output signal may be generated at a secondary side of the compensation transformer.

The compensation unit 160 injects the compensation currents IC1 and IC2 into the large current paths 111 and 112 through each of the two or more large current paths 111 and 112 in order to cancel the first currents I11 and I12. ). The compensation currents IC1 and IC2 may have the same magnitude as the first currents I11 and I12 and have opposite phases.

FIG. 2 shows a more specific example of the embodiment shown in FIG. 1, and schematically shows an active current compensation device 100A according to an embodiment of the present invention. The active current compensation device 100A actively takes the first current I11, I12 (eg, noise current) input in a common mode to each of the two high current paths 111A and 112A connected to the first device 300A. You can compensate.

Referring to FIG. 2, the active current compensation device 100A may include a sensing transformer 120A, an amplifying unit 130A, and a compensation unit 160A.

In one embodiment, the above-described sensing unit 120 may include a sensing transformer 120A. In this case, the sensing transformer 120A may be a means for sensing the first currents I11 and I12 on the high current paths 111A and 112A while insulated from the high current paths 111A and 112A. The sensing transformer 120A may sense the first currents I11 and I12, which are noise currents input from the first device 300A to the high current paths 111A and 112A (eg, power lines).

The sensing transformer 120A may include a primary side 121A disposed on the high current paths 111A and 112A, and a secondary side 122A differentially connected to the input terminal of the amplifying unit 130A. have. The sensing transformer 120A is 2 based on the magnetic flux density induced by the first currents I11 and I12 at the primary side 121A (eg, primary winding) disposed on the high current paths 111A and 112A. An induced current may be generated in the secondary side 122A (eg, secondary winding). The primary side 121A of the sensing transformer 120A may be, for example, a winding in which a first large current path 111A and a second large current path 112A are wound around one core, respectively. However, the present invention is not limited thereto, and the primary side 121A of the sensing transformer 120A may have a shape in which a first high current path 111A and a second high current path 112A pass through the core.

Specifically, the magnetic flux density induced by the first current I11 on the first high current path 111A (for example, a live line) and the first current I12 on the second high current path 112A (for example, a neutral wire) The magnetic flux density induced by may be configured to overlap (or reinforce) each other. At this time, the second currents I21 and I22 also flow on the high current paths 111A and 112A, and the magnetic flux density induced by the second current I21 on the first high current path 111A and the second high current path 112A The magnetic flux densities induced by the first current I22 on) may be configured to cancel each other. In addition, for example, the sensing transformer 120A has the magnitude of the magnetic flux density induced by the first currents I11 and I12 in the first frequency band (for example, a band having a range of 150 KHz to 30 MHz) at the second frequency. It may be configured to be larger than the magnitude of the magnetic flux density induced by the second currents I21 and I22 of the band (for example, a band having a range of 50Hz to 60Hz).

As described above, the sensing transformer 120A is configured such that magnetic flux densities induced by the second currents I21 and I22 cancel each other, so that only the first currents I11 and I12 can be sensed. That is, the current induced in the secondary side 122A of the sensing transformer 120A may be a current obtained by converting the first currents I11 and I12 at a predetermined ratio.

For example, in the sensing transformer 120A, the turns ratio of the primary side 121A and the secondary side 122A is 1:N _sen, and the self-inductance of the primary side 121A of the sensing transformer 120A is L _{Speaking of sen} , the secondary side 122A may have a self inductance of N _sen ² L _sen . At this time, the current induced to the secondary side 122A is 1/N _sen times the first currents I11 and I12. For example, the primary side 121A and the secondary side 122A of the sensing transformer 120A may be combined with a coupling coefficient of k _sen .

The secondary side 122A of the sensing transformer 120A may be connected to an input terminal of the amplifying unit 130A. For example, the secondary side 122A of the sensing transformer 120A may be differentially connected to the input terminal of the amplifying unit 130A to supply an induced current to the amplifying unit 130A. Alternatively, according to the configuration of the amplifying unit 130A, the secondary side 122A of the sensing transformer 120A is a path connecting the input terminal of the amplifying unit 130A and the reference potential (reference potential 2) of the amplifying unit 130A. It can also be placed on top. That is, one end of the secondary side 122A may be connected to the input end of the amplifying unit 130A, and the other end of the secondary side 122A may be connected to the reference potential (reference potential 2) of the amplifying unit 130A. .

The amplification unit 130A may correspond to the amplification unit 130 described above. The amplifying unit 130A may amplify a current sensed by the sensing transformer 120A and induced to the secondary side 122A. For example, the amplification unit 130A may amplify the magnitude of the induced current at a predetermined ratio and/or adjust the phase.

The compensation unit 160A may correspond to the compensation unit 160 described above. The compensation unit 160A may include a compensation transformer 140A and a compensation capacitor unit 150A. The amplified current amplified by the above-described amplification unit 130A flows to the primary side 141A of the compensation transformer 140A.

The compensation transformer 140A may be a means for insulating the amplification unit 130A including the active element from the high current paths 111A and 112A. That is, the compensation transformer 140A generates a compensation current (to the secondary side 142A) for injecting into the large current paths 111A and 112A based on the amplified current in a state insulated from the large current paths 111A and 112A. It can be a means for.

The compensation transformer 140A may include a primary side 141A differentially connected to the output terminal of the amplifying unit 130A, and a secondary side 142A connected to the high current paths 111A and 112A. have. The compensation transformer 140A induces a compensation current in the secondary side 142A (eg, secondary winding) based on the magnetic flux density induced by the amplified current flowing through the primary side 141A (eg, primary winding). can do.

In this case, the secondary side 142A may be disposed on a path connecting the compensation capacitor unit 150A to be described later with the reference potential (reference potential 1) of the current compensation device 100A. That is, one end of the secondary side 142A is connected to the high current paths 111A and 112A through the compensation capacitor unit 150A, and the other end of the secondary side 142A is the reference of the active current compensation device 100A. It can be connected to a potential (reference potential 1). On the other hand, the primary side (141A) of the compensation transformer (140A), the amplification unit (130A), and the secondary side (122A) of the sensing transformer (120A) is separated from the remaining components of the active current compensation device (100A). It can be connected to the reference potential (reference potential 2). The reference potential (reference potential 1) of the current compensating device 100A and the reference potential (reference potential 2) of the amplification unit 130A may be distinguished.

As described above, the present invention uses a reference potential different from the remaining components for the component generating the compensation current, and by using a separate power source, the component generating the compensation current can operate in an insulated state. The reliability of the active current compensation device 100A may be improved.

In the compensation transformer 140A, suppose that the turns ratio of the primary side 141A and the secondary side 142A is 1:N _inj, and the self inductance of the primary side 141A of the compensation transformer 140A is L _inj , The secondary side 142A may have a self inductance of N _inj ² L _inj . At this time, the current induced in the secondary side 142A is 1/N _inj times the current flowing through the primary side 141A (ie, amplified current). The primary side 141A and the secondary side 142A of the compensation transformer 140A may be combined with a coupling coefficient of k _inj .

The current converted through the compensation transformer 140A may be injected as compensation currents IC1 and IC2 into the high current paths 111A and 112A (eg, power lines) through the compensation capacitor unit 150A. Accordingly, the compensation currents IC1 and IC2 may have the same magnitude as the first currents I11 and I12 and have opposite phases in order to cancel the first currents I11 and I12. Accordingly, the magnitude of the current gain of the amplifying unit 130A may be designed to be N _sen N _inj .

The compensation capacitor unit 150A may provide a path through which the current generated by the compensation transformer 140A flows through each of the two high current paths 111A and 112A, as described above.

The compensation capacitor unit 150A has two Y-capacitors, one end connected to the secondary side 142A of the compensation transformer 140A, and the other end connected to the high current paths 111A and 112A. Y-cap) may be included. One end of each of the two Y-caps shares a node connected to the secondary side 142A of the compensation transformer 140A, and the opposite ends of each of the two Y-caps have a first high current path 111A and a first 2 It may have a node connected to the high current path 112A.

The compensation capacitor unit 150A may pass the compensation currents IC1 and IC2 induced by the compensation transformer 140A to the power line. The current compensation device 100A can reduce noise by compensating (or canceling) the first currents I11 and I12 by the compensation currents IC1 and IC2.

Meanwhile, the compensation capacitor unit 150A may be configured such that the current IL1 flowing between the two large current paths 111A and 112A through the compensation capacitor is less than a first threshold size. In addition, the compensation capacitor unit 150A may be configured such that the current IL2 flowing between each of the two large current paths 111A and 112A and the reference potential 1 through the compensation capacitor is less than the second threshold.

The active current compensation device 100A can realize an isolated structure by using the compensation transformer 140A and the sensing transformer 120A.

3 schematically shows the configuration of a system including the active current compensation device 100 according to another embodiment of the present invention. Referring to FIG. 3, the current compensating device 100 may further include a decoupling capacitor unit 170 in the current compensating device illustrated in FIG. 1. Detailed descriptions of components overlapping with the embodiment shown in FIG. 1 will be omitted.

The decoupling capacitor unit 170 may be a means for allowing the output impedance from the compensation unit 160 to the second device 200 to satisfy a predetermined condition. In other words, the decoupling capacitor unit 170 allows the compensation current to be output to the second device 200 side along at least two or more high current paths 111 and 112 and prevents returning to the active current compensation device 100 side. It can be a means.

For example, when the active current compensation device 100 satisfies the condition that the output impedance of the compensation unit 160 is equal to or less than the impedance of the compensation unit 160 itself, the first current generated by the first device 300 is Can increase the reward effect of According to the embodiment, the amount of the compensation current flowing toward the second device 200D is that at least a portion of the compensation current is reduced to the inside of the current compensation device 100 along each of the two or more high current paths 111 and 112. A condition greater than the amount flowing to the side can be satisfied.

The impedance of the second device 200 may be arbitrarily changed according to the surrounding conditions of the power system and filter. For example, a home appliance may have various impedance values depending on its constituent elements (eg, an electric motor, an electric heater, a light emitting device, etc.).

The decoupling capacitor unit 170 prevents the output performance of the compensation current of the active current compensation device 100 from varying significantly according to the change of the impedance value of the second device 200 so that it can be applied to various systems.

The active current compensation device 100 may be a feedforward type compensation filter that compensates noise input from the first device 300 at the front end, which is the power side. That is, in the active current compensation device 100, the sensing unit 120 may be disposed on the side of the first device 300 that is a noise source, and the compensation unit 160 may be disposed on the side of the second device 200, which is the power supply side. have.

4 schematically shows a specific example of the active current compensation device 100A according to the embodiment shown in FIG. 3. Referring to FIG. 4, the active current compensating device 100A may further include a decoupling capacitor unit 170B in the active current compensating device illustrated in FIG. 2.

The decoupling capacitor unit 170B may be a means for allowing the output impedance from the compensation unit 160A to the second device 200A to satisfy a predetermined condition. In other words, the decoupling capacitor unit 170B allows the compensation current to be output to the second device 200A side along at least two or more large current paths 111A and 112A, and prevents returning to the active current compensation device 100A side again. It can be a means.

The impedance Z _n of the first device 300A and/or the impedance Z _line of the second device 200A may be arbitrarily changed according to the surrounding conditions of the power system and the filter. For example, a home appliance may have various impedance values depending on its constituent elements (eg, an electric motor, an electric heater, a light emitting device, etc.).

The decoupling capacitor unit 170B prevents the output performance of the compensation current of the active current compensation device 100A from varying significantly according to the change of the impedance value of the second device 200A, so that it can be applied to various systems.

The decoupling capacitor unit 170B includes at least two capacitors disposed on a path branching from each of the at least two high current paths 111A and 112A connecting the second device 200A and the compensation capacitor unit 150A. Can include.

4, one end of each of the two capacitors included in the decoupling capacitor unit 170B may be connected to a reference potential (reference potential 1) of the active current compensation device 100A, and opposite ends of each of the two capacitors May be connected to the first high current path 111A and the second high current path 112A, respectively. The decoupling capacitor unit 170B may be connected to the power side (ie, the second device 200A) of the active current compensation device 100A. Accordingly, it is possible to further increase the compensation accuracy of the second device 200A. However, it is not limited thereto.

The impedance Z _Y of the decoupling capacitor unit 170B may be designed to have a sufficiently small value in the first frequency band to be subjected to noise reduction. For example, the impedance Z _Y of the decoupling capacitor unit 170B may satisfy Equation 1.

는, 감결합 커패시터부(170B)로 인해 임의의 Z_line 값과 상관없이 설계된 Z_Y의 값을 가질 수 있다. 예를 들어 감결합 커패시터부(170B)의 임피던스 Z_Y는, 지정된 주파수 대역(예: 제1 주파수 대역) 내에서 지정된 값보다 작은 값을 가지도록 설계될 수 있다. 감결합 커패시터부(170B)의 임피던스(Z_Y)가 노이즈 저감의 대상이 되는 제1 주파수 대역에서 충분히 작은 값을 가짐으로써, 전류 보상 장치(100A)가 제2 장치(200A) 측 임피던스(Z_line)에 상관없이 정상적으로 동작할 수 있다. Referring to Equation 1, impedance viewed from the current compensation device 100A toward the second device 200A

May have a designed value of Z _Y regardless of an arbitrary Z _line value due to the decoupling capacitor unit 170B. For example, the impedance Z _Y of the decoupling capacitor unit 170B may be designed to have a value smaller than a specified value within a specified frequency band (eg, a first frequency band). Since the impedance (Z _Y ) of the decoupling capacitor unit 170B has a sufficiently small value in the first frequency band to be subjected to noise reduction, the current compensating device 100A is applied to the second device 200A side impedance (Z _line ), it can operate normally.

Due to the combination of the decoupling capacitor unit 170B, the active current compensation device 100A can be used as an independent module in any system.

The active current compensation device 100A according to an embodiment of the present invention may not include a common mode (CM) choke. Since the CM choke functions as a passive filter, it must have a very large inductance to suppress leakage of the first current (I11, I12) (eg, noise current). Accordingly, the number of windings of the CM choke increases, and the size of the core becomes very large. Unlike such a CM choke, the sensing transformer 120A included in the current compensating device 100A according to an embodiment of the present invention is intended to sense the first noise current I11 and I12, so it is necessary to have a large impedance. There is no The sensing transformer 120A may have an impedance of one thousandth to one hundredth of the impedance of the CM choke. Therefore, the size of the sensing transformer 120A may be much smaller than that of the CM choke. The active current compensating device 100A according to an embodiment of the present invention can operate independently without parasitic to the CM choke. In some cases, the active current compensating device 100A may be operated in combination with an external CM choke independent from the active current compensating device 100A.

5 schematically shows an active current compensation device 100A-1 according to another embodiment of the present invention. The active current compensation device 100A-1 illustrated in FIG. 5 is an example of the current compensation device 100A illustrated in FIG. 4. In an embodiment, if the decoupling capacitor unit 170A is omitted from the active current compensation device 100A-1, it may be an example of the current compensation device 100A shown in FIG. 2. The amplifying unit 130A-1 included in the active current compensating device 100A-1 is an example of the amplifying unit 130A of the active current compensating device 100A.

In the active current compensating device 100A-1, the amplifying unit 130A of the active current compensating device 100A is implemented as an amplifying unit 130A-1 having a non-inverting amplifier structure including an op-amp. In the amplifying unit 130A-1, power of Vcc and -Vcc may be supplied from the third device 400A to the OP-amp based on the reference potential 2. R ₁ , R ₂ , R _f1 , C _f1 , R _f2 , and C _f2 included in the amplifying unit 130A-1 are elements for adjusting the gain of the non-inverting amplifier according to the frequency. Specifically, the values of R ₁ , R ₂ , R _f1 , C _f1 , R _f2 , and C _f2 are in order to satisfy the limiting standard of conductive emission (CE) within the first frequency band (eg, 150KHz to 30MHz). Can be determined. For example, R ₁ , R ₂ , R _f1 , C _f1 , R _f2 , and C _f2 so that the first currents I11 and I12 and the compensation currents IC1 and IC2 have the same magnitude and opposite phases. Values can be determined.

For example, in the sensing transformer 120A, when the turns ratio of the primary side 121A and the secondary side 122A is 1:N _sen , the current induced to the secondary side 122A is the first current I11 , 1/N _sen times I12). In addition, in the compensation transformer 140A, when the turns ratio of the primary side 141A and the secondary side 142A is 1:N _inj , the current induced in the secondary side 142A is in the primary side 141A. It is 1/N _inj times the flowing current (ie, amplification current).

Therefore, in order to cancel the first currents I11 and I12, in order to generate the compensation currents IC1 and IC2 having the same magnitude as the first currents I11 and I12 and opposite in phase, the amplification unit 130A-1 The magnitude of the current gain may have to satisfy N _sen N _inj . Accordingly, the values of R ₁ , R ₂ , R _f1 , C _f1 , R _f2 , and C _f2 may be satisfied such that the magnitude of the current gain of the amplifying unit 130A-1 is N _sen N _inj .

The amplification unit 130A-1 may include a high pass filter 401. The elements R ₀ and C ₀ included in the high pass filter 401 may block the amplifying unit 130A-1 from operating in a low frequency lower than or equal to the first frequency band to be subjected to noise reduction.

According to an embodiment, the decoupling capacitor unit 170A may be disposed on the output side of the active current compensation device 100A-1 (ie, the second device 200A side). That is, the decoupling capacitor unit 170A includes two capacitors disposed on a path branching from each of at least two or more high current paths 111A and 112A connecting the second device 200A and the compensation capacitor unit 150A. can do. One end of each of the two capacitors may be connected to a reference potential (reference potential 1) of the current compensating device 100A-1, and opposite ends of each of the two Y-caps have a first high current path 111A and a second It may be connected to the high current path 112A.

According to an exemplary embodiment, the decoupling capacitor 170A may be omitted in the active current compensation device 100A-1.

6 schematically shows an active current compensation apparatus 100A-2 according to another embodiment of the present invention. The active current compensating device 100A-2 shown in FIG. 6 is an example of the active current compensating device 100A shown in FIG. 4. In an embodiment, if the decoupling capacitor unit 170A is omitted from the active current compensation device 100A-2, it may be an example of the active current compensation device 100A illustrated in FIG. 2. The amplifying unit 130A-2 included in the active current compensating device 100A-2 is an example of the amplifying unit 130A of the active current compensating device 100A.

In the active current compensating device 100A-2, the amplifying unit 130A of the active current compensating device 100A is implemented as an amplifying unit 130A-2 having a push-pull amplifier structure including npn BJT and pnp BJT. Became.

The induced current induced in the secondary side 122A by the sensing transformer 120A may be differentially input to the amplifying unit 130A-2. At the input terminal of the amplifying unit 130A-2, a resistor R _in may be connected in parallel to the secondary side 122A. R _in may adjust the input impedance of the amplifying unit 130A-2. C _b and C _e can selectively couple only AC signals.

The third device 400A supplies a DC low voltage V _DC based on the reference potential 2 in order to drive the amplifying unit 130A-2. C _DC is a decoupling capacitor for DC and may be connected in parallel to the third device 400A. C _DC can selectively couple only AC signals between the collectors of npn BJT and pnp BJT.

In the amplification unit 130A-2, R _npn , R _pnp , R _bb , and R _e may adjust the operating point of the BJT. R _npn , R _pnp , R _bb , and R _e may be designed according to the operating point of the BJT. R _npn may connect the collector terminal and the third device 400A terminal of the npn BJT and the base terminal of the npn BJT. R _bb may connect the base end of the npn BJT and the base end of the pnp BJT. R _pnp can connect the collector terminal and reference potential 2 of the pnp BJT and the base terminal of the pnp BJT.

On the other hand, in the sensing transformer 120A, when the turns ratio between the primary side 121A and the secondary side 122A is 1:N _sen , the current induced to the secondary side 122A is the first currents I11 and I12 ) Is 1/N _sen times, and in the compensation transformer 140A, if the turns ratio of the primary side 141A and the secondary side 142A is 1:N _inj , the current induced in the secondary side 142A is, It is 1/N _inj times the current flowing through the primary side 141A (that is, the amplification current). Therefore, in order to cancel the first currents I11 and I12, in order to generate the compensation currents IC1 and IC2 having the same magnitude as the first currents I11 and I12 and opposite in phase, the amplification unit 130A-2 The current gain can be designed to be N _sen N _inj .

Meanwhile, according to the voltage applied between the base and the emitter of the BJT, the current flowing through the collector and the emitter varies. In the case of a positive swing in which the input voltage of the amplifying unit 130A-2 due to noise is greater than 0, the npn BJT may operate. In this case, the operating current may flow through the first path 501. In the case of a negative swing in which the input voltage of the amplifying unit 130A-2 due to noise is less than 0, the pnp BJT may operate. In this case, the operating current may flow through the second path 502.

라고 하면, 증폭부(130A-2)의 전체 트랜스컨덕턴스(transconductance)

는 수학식 2와 같이 나타낼 수 있다. On the other hand, the transconductance of the BJT device (ratio of the output current to the input voltage of the BJT)

Speaking of, the total transconductance of the amplifying unit 130A-2

Can be expressed as in Equation 2.

는, 상술한 바와 같이, BJT가 피드백 루프 없이 스스로 가지는 트랜스컨덕턴스(입력 전압에 대한 출력 전류의 비)를 나타낸다. In Equation 2, I _out is an output current of the amplifying unit 130A-2 and is a current flowing through the primary side 141A of the compensation transformer 140A. V _sen is an input voltage of the amplifying unit 130A-2 and is a potential difference between both ends of the differential input terminal of the amplifying unit 130A-2, that is, a voltage induced to the secondary side 122A of the sensing transformer 120A.

As described above, denotes the transconductance (ratio of output current to input voltage) that the BJT has without a feedback loop.

Therefore, the current gain of the amplifying unit 130A-2 can be expressed as in Equation 3.

는, 증폭부(130A-2)의 전류이득을 나타낸다. I_sen은 증폭부(130A-2)의 입력 전류로써, 센싱 변압기(120A)에 의해 2차 측(122A)에 유도되는 전류이다. I_out은, 증폭부(130A-2)의 출력 전류로써, 보상 변압기(140A)의 1차 측(141A)에 흐르는 전류이다. In Equation 3

Denotes the current gain of the amplifying unit 130A-2. I _sen is an input current of the amplifying unit 130A-2, and is a current induced to the secondary side 122A by the sensing transformer 120A. I _out is an output current of the amplifying unit 130A-2 and is a current flowing to the primary side 141A of the compensation transformer 140A.

From this, the current gain of the amplifying unit 130A-2 may be approximated as shown in Equation 4.

이 N_senN_inj가 되도록 설계함으로써, 보상 전류(IC1, IC2)와 제1 전류(I11, I12)의 크기가 같아질 수 있고, 보상 전류(IC1, IC2)로 제1 전류(I11, I12)를 상쇄할 수 있다. On the other hand, as described above, the current gain of the amplification unit (130A-2)

By designing to be N _sen N _inj , the magnitudes of the compensation currents IC1 and IC2 and the first currents I11 and I12 can be the same, and the first currents I11 and I12 as the compensation currents IC1 and IC2 Can be offset.

(

R_in/R_e)은, N_senN_inj가 되도록 설계될 수 있다.In order to cancel the first currents I11 and I12 with the compensation currents IC1 and IC2, the current gain of the amplifier 130A-2

(

R _in /R _e ) may be designed to be N _sen N _inj .

According to an embodiment, the decoupling capacitor unit 170A may be disposed on the output side of the active current compensation device 100A-2 (ie, the second device 200A side). That is, the decoupling capacitor unit 170A includes two capacitors disposed on a path branching from each of at least two or more high current paths 111A and 112A connecting the second device 200A and the compensation capacitor unit 150A. can do. One end of each of the two capacitors may be connected to a reference potential (reference potential 1) of the current compensating device 100A-2, and opposite ends of each of the two Y-caps have a first high current path 111A and a second It may be connected to the high current path 112A.

According to an embodiment, in the active current compensation device 100A-2, the decoupling capacitor unit 170A may be omitted.

7 schematically shows an active current compensation device 100A-3 according to another embodiment of the present invention. The active current compensating device 100A-3 shown in FIG. 7 is an example of the active current compensating device 100A shown in FIG. 4. In an embodiment, if the decoupling capacitor unit 170A is omitted from the active current compensation device 100A-3, it may be an example of the active current compensation device 100A illustrated in FIG. 2. The amplifying unit 130A-3 included in the active current compensating device 100A-3 is an example of the amplifying unit 130A of the active current compensating device 100A.

In the active current compensating device 100A-3, the amplifying unit 130A of the active current compensating device 100A is implemented as an amplifying unit 130A-3 having a push-pull amplifier structure including npn BJT and pnp BJT. Became.

The induced current induced in the secondary side 122A by the sensing transformer 120A may be differentially input to the amplifying unit 130A-3. Unlike the amplification unit 130A-2 of FIG. 4, the amplification unit 130A-3 may not include a resistor R _in . C _b and C _e can selectively couple only AC signals.

The third device 400A supplies a DC low voltage V _DC based on the reference potential 2 in order to drive the amplification unit 130A-3. C _DC is a DC decoupling capacitor for the V _DC and may be connected in parallel to the third device 400A. C _DC can selectively couple only AC signals between the collectors of npn BJT and pnp BJT.

In the amplification unit 130A-3, R _npn , R _pnp , R _bb , and R _e may adjust the operating point of the BJT. R _npn may connect the collector terminal and the third device 400A terminal of the npn BJT and the base terminal of the npn BJT. R _bb may connect the base end of the npn BJT and the base end of the pnp BJT. R _pnp can connect the collector terminal and reference potential 2 of the pnp BJT and the base terminal of the pnp BJT.

Meanwhile, in one embodiment, the secondary side 122A side of the sensing transformer 120A may be connected to the base and the emitter end of the two BJTs, and the primary side 141A side of the compensation transformer 140A is the collector of the two BJTs. And can be connected to the base. The amplification unit 130A-3 may have a regression structure in which the output current is injected back to the base of the BJT. Due to the regression structure, the amplification unit 130A-3 can stably obtain a constant current gain for the operation of the active current compensation device 100A-3.

In the case of a positive swing in which the input voltage of the amplifying unit 130A-3 due to noise is greater than 0, the npn BJT may operate. In this case, the operating current may flow through the first path 601. In the case of a negative swing in which the input voltage of the amplifying unit 130A-3 due to noise is less than 0, the pnp BJT may operate. In this case, the operating current may flow through the second path 602.

는, 수학식 5와 같이 나타낼 수 있다. On the other hand, the current gain of the BJT device itself

Can be expressed as in Equation 5.

는 BJT 소자 자체가 가지는 전류 이득을 나타내고, I_sen은, 센싱 변압기(120A)에 의해 유도되는, 2차 측(122A)에 흐르는 전류이고, I_out,BJT는, 보상 변압기(140A)의 1차 측(141A)에 흐르는 전류이다. I_sen을

의 함수로 나타내면 수학식 6과 같다. In Equation 5,

Denotes the current gain of the BJT element itself, I _sen is the current flowing through the secondary side 122A, induced by the sensing transformer 120A, and I _{out, BJT} is the primary of the compensation transformer 140A It is a current flowing through the side 141A. I _sen

It is expressed as a function of Equation 6.

는 수학식 7과 같이 나타낼 수 있다. Therefore, the current gain of the amplification unit 130A-3

Can be expressed as in Equation 7.

는 1보다 매우 큰 값(예: 100 이상)을 가지므로,

는 -1로 근사될 수 있다. 따라서, 능동형 전류 보상 장치(100A-3)의 경우, N_senN_inj = 1을 만족하도록 설계함으로써, 보상 전류(IC1, IC2)로 제1 전류(I11, I12)를 상쇄할 수 있다. 즉, 센싱 변압기(120A)의 1차 측(121A) 대 2차 측(122A)의 권선비와, 보상 변압기(140A)의 1차 측(141A) 대 2차 측(142A)의 권선비가 역수를 만족하도록 설계할 수 있다. BJT current gain

Has a value much greater than 1 (e.g. 100 or more),

Can be approximated by -1. Therefore, in the case of the active current compensation device 100A-3, by designing to satisfy N _sen N _inj = 1, the first currents I11 and I12 can be canceled with the compensation currents IC1 and IC2. That is, the turns ratio of the primary side 121A to the secondary side 122A of the sensing transformer 120A and the turns ratio of the primary side 141A to the secondary side 142A of the compensation transformer 140A satisfy the reciprocal. Can be designed to do.

)를 다시 입력단으로 귀환시키는 피드백 구조를 가질 수 있다. 따라서, 증폭부(130A-3)는 전류 이득에 제한적인 대신, 증폭부(130A-2)보다 안정적으로 전류 이득을 얻을 수 있다. Unlike the amplifying unit 130A-2 of the active current compensating device 100A-2 of FIG. 6, the amplifying unit 130A-3 of the active current compensating device 100A-3 does not have R _{in at the} input terminal and compensates Output current (

It can have a feedback structure that returns) back to the input terminal. Therefore, the amplifying unit 130A-3 may obtain a current gain more stably than the amplifying unit 130A-2, instead of being limited in the current gain.

According to an embodiment, the decoupling capacitor unit 170A may be disposed on the output side of the active current compensation device 100A-3 (ie, the second device 200A side). That is, the decoupling capacitor unit 170A includes two capacitors disposed on a path branching from each of at least two or more high current paths 111A and 112A connecting the second device 200A and the compensation capacitor unit 150A. can do. One end of each of the two capacitors may be connected to a reference potential (reference potential 1) of the current compensating device 100A-3, and opposite ends of each of the two Y-caps have a first high current path 111A and a second It may be connected to the high current path 112A.

According to an embodiment, in the active current compensation device 100A-3, the decoupling capacitor unit 170A may be omitted.

8 is a diagram schematically showing the configuration of an active current compensation device 100C according to another embodiment of the present invention. Hereinafter, descriptions of contents overlapping with those described with reference to FIGS. 1 to 7 will be omitted.

Referring to FIG. 8, the active current compensation device 100C actively applies first currents I11, I12, and I13 input in a common mode to each of the high current paths 111C, 112C, and 113C connected to the first device 300C. It can be compensated with.

To this end, the active current compensation device 100C according to another embodiment of the present invention includes three large current paths 111C, 112C, and 113C, a sensing transformer 120C, an amplification unit 130C, a compensation transformer 140C, and a compensation. It may include a capacitor unit (150C).

Looking in contrast to the active current compensating devices 100A and 100B according to the embodiment described in FIGS. 2 to 7, the active current compensating device 100C according to the embodiment illustrated in FIG. 8 includes three large current paths 111C and 112C. , 113C), and accordingly, there is a difference between the sensing transformer 120C and the compensation capacitor unit 150C. Therefore, hereinafter, the active current compensation device 100C will be described based on the above-described differences.

The active current compensation device 100C may include a first large current path 111C, a second large current path 112C, and a third large current path 113C, which are separated from each other. According to an embodiment, the first large current path 111C may be an R-phase, the second large current path 112C may be an S-phase, and the third large current path 113C may be a T-phase power line. The first currents I11, I12, and I13 may be input to each of the first high current path 111C, the second high current path 112C, and the third high current path 113C in a common mode.

The primary side 121C of the sensing transformer 120C is disposed in each of the first high-current path 111C, the second high-current path 112C, and the third high-current path 113C, and induced current to the secondary side 122C. Can be created. The magnetic flux densities generated in the sensing transformer 120C by the first currents I11, I12, and I13 on the three large current paths 111C, 112C, and 113C may be reinforced with each other.

Meanwhile, in the active current compensation device 100C, the amplification unit 130C may be implemented as one of an amplification unit including the amplification unit 130A-1, the amplification unit 130A-2, and the amplification unit 130A-3. . However, it is not limited thereto.

Meanwhile, in the compensation capacitor unit 150C, the compensation currents IC1, IC2, and IC3 generated by the compensation transformer flow through the first large current path 111C, the second large current path 112C, and the third large current path 113C, respectively. You can provide a path.

The active current compensation device 100C according to such an embodiment may be used to compensate (or cancel) the first currents I11, I12, and I13 moving from the load of the three-phase three-wire power system to the power source.

The active current compensation device 100C may further include a decoupling capacitor unit 170C on the output side (ie, the second device 200C side). The decoupling capacitor unit 170C may include three capacitors. One end of each of the three capacitors may be connected to a first high current path 111C, a second high current path 112C, and a third high current path 113C, respectively. Opposite ends of the three capacitors may be connected to a reference potential (reference potential 1) of the current compensating device 100C.

The impedance Z _Y of the decoupling capacitor unit 170C may be designed to have a value smaller than a specified value in the first frequency band to be subjected to noise reduction. Due to the coupling of the decoupling capacitor unit 170C, the current compensation device 100C can be used as an independent module in any system (eg, a three-phase three-wire system).

According to an embodiment, in the active current compensation device 100C, the decoupling capacitor unit 170C may be omitted.

9 is a diagram schematically showing a configuration of an active current compensation device 100D according to another embodiment of the present invention. Hereinafter, descriptions of contents overlapping with those described with reference to FIGS. 1 to 7 will be omitted.

Referring to FIG. 9, the active current compensation device 100D includes first currents I11, I12, I13 and I13 inputted in a common mode to each of the high current paths 111D, 112D, 113D, and 114D connected to the first device 300D. I14) can be actively compensated.

To this end, the active current compensation device 100D according to the embodiment includes four large current paths 111D, 112D, 113D, and 114D, a sensing transformer 120D, an amplifying unit 130D, a compensation transformer 140D, and a compensation capacitor unit ( 150D).

When looking in contrast to the active current compensation devices 100A and 100B according to the embodiment described in FIGS. 2 to 7 and the active current compensation device 100C according to the embodiment described in FIG. 8, according to the embodiment shown in FIG. The active current compensation device 100D includes four large current paths 111D, 112D, 113D, and 114D, and thus there is a difference between the sensing transformer 120D and the compensation capacitor unit 150D. Therefore, hereinafter, the active current compensation device 100D will be described based on the above differences.

The active current compensation device 100D may include a first large current path 111D, a second large current path 112D, a third large current path 113D, and a fourth large current path 114D that are separated from each other. According to an embodiment, the first large current path 111D is an R phase, the second large current path 112D is an S phase, the third large current path 113D is a T phase, and the fourth large current path 114D is It may be an N-phase power line. The first currents I11, I12, I13, and I14 are the first high current path 111D, the second high current path 112D, the third high current path 113D, and the fourth high current path 114D. ) Can be input in common mode.

The primary side 121D of the sensing transformer 120D is disposed in each of the first high current path 111D, the second high current path 112D, the third high current path 113D, and the fourth high current path 114D, and 2 An induced current can be generated in the vehicle side 122D. The magnetic flux densities generated in the sensing transformer 120D by the first currents I11, I12, I13, I14 on the four large current paths 111D, 112D, 113D, and 114D may be reinforced with each other.

Meanwhile, in the active current compensation device 100D, the amplification unit 130D may be implemented as one of an amplification unit including the amplification unit 130A-1, the amplification unit 130A-2, and the amplification unit 130A-3. . However, it is not limited thereto.

Meanwhile, in the compensation capacitor unit 150D, the compensation currents ID1, ID2, ID3, and ID4 generated by the compensation transformer include the first large current path 111D, the second large current path 112D, the third large current path 113D, and A path flowing through each of the fourth large current paths 114D may be provided.

The active current compensation device 100D according to this embodiment may be used to compensate (or cancel) the first currents I11, I12, I13, I14 moving from the load of the three-phase, four-wire power system to the power source. .

The active current compensation device 100D may further include a decoupling capacitor unit 170D on the output side (ie, the second device 200D side). The decoupling capacitor unit 170D may include four capacitors. One end of each of the four capacitors may be connected to a first large current path 111D, a second large current path 112D, a third large current path 113D, and a fourth large current path 114D, respectively. Opposite ends of the four capacitors may be connected to a reference potential (reference potential 1) of the current compensating device 100D.

The impedance Z _Y of the decoupling capacitor unit 170D may be designed to have a value smaller than a specified value in the first frequency band to be subjected to noise reduction. Due to the combination of the decoupling capacitor unit 170D, the active current compensation device 100D can be used as an independent module in any system (eg, a 3-phase 4-wire system).

According to an embodiment, in the active current compensation device 100D, the decoupling capacitor unit 170D may be omitted.

The active current compensation device according to various embodiments may stably operate regardless of the characteristics of the installed electric system. Accordingly, the active current compensation device does not need to be customized through repeated tests for each circuit or system, and can have versatility as an independent component. The active current compensation device can be commercialized as an independent module.

In addition, the active current compensation device according to various embodiments of the present invention can operate independently without parasitic to the CM choke, and can reduce area, volume, and weight compared to a passive filter including a CM choke.

In addition, unlike the CM choke, the active current compensating device according to various embodiments has an insignificant increase in size or increase in price even when used for high power consumption. Specifically, the passive filter including the CM choke rapidly increases in size, price, and weight in order to be used in a high power system due to magnetic saturation. However, the amplification units 130A, 130A-1, 130A-2, and 130A-3 included in the active current compensation device are not significantly affected by the change in the amount of power. In the active current compensation device, the volume increase rate of the sensing transformer 120A according to the increase in the amount of power may be much smaller than the increase rate of the volume (eg, size and/or number) of CM chokes. Accordingly, the active current compensation device according to various embodiments may be much more advantageous in terms of cost, volume, and weight than a passive filter in a high power system.

In addition, since the active current compensation device according to various embodiments of the present invention has a structure that is electrically insulated from a high current path (eg, a power line), the elements included in the amplifying unit 130A can be protected from electrical overstress (EOS). have. For example, since the amplifying unit 130A according to various embodiments of the present disclosure is insulated from a power line, a DC low voltage (eg, the third device 400, within 15V) used for the control board may be used. Therefore, the amplification unit 130A does not require a separate power conversion circuit. In addition, the active current compensation device according to various embodiments of the present invention, regardless of the reference potential (reference potential 1) of the power supply device (for example, the second device 200), to configure the amplifying unit (130A) Devices with a lower rated voltage can be used.

The specific implementations described in the present invention are examples, and do not limit the scope of the present invention in any way. For brevity of the specification, descriptions of conventional electronic configurations, control systems, software, and other functional aspects of the systems may be omitted. In addition, the connection or connection members of the lines between the components shown in the drawings exemplarily represent functional connections and/or physical or circuit connections, and in an actual device, various functional connections that can be replaced or additionally It may be referred to as a connection, or circuit connections. In addition, if there is no specific mention such as "essential", "important", etc., it may not be an essential component for the application of the present invention.

Therefore, the spirit of the present invention is limited to the above-described embodiments and should not be defined, and all ranges equivalent to or equivalently changed from the claims to be described later as well as the claims to be described later are the scope of the spirit of the present invention. It will be said to belong to.

Claims (5)

In the active current compensation device for actively compensating for a first current input in a common mode to each of at least two or more high current paths connected to the first device,
At least two or more high current paths for passing a second current supplied by a second device to the first device;
A sensing unit that senses the first current on the high current path and generates an output signal corresponding to the first current;
An amplifying unit generating an amplified current by amplifying the output signal of the sensing unit; And
Compensating unit for generating a compensation current based on the amplified current and flowing the compensation current through each of the at least two large current paths; including, active current compensation device. The method of claim 1,
The active current compensation device further comprises a decoupling capacitor unit provided to adjust the output impedance from the compensation unit to the second device side. The method of claim 2,
The output impedance is
An active current compensation device that is a combined impedance of the impedance of the second device and the impedance of the decoupling capacitor. The method of claim 2,
The compensation unit flows the compensation current through each of the at least two large current paths through the compensation capacitor unit,
The decoupling capacitor part
And at least two capacitors disposed on a path branching from each of the at least two high current paths connecting the second device and the compensation capacitor unit. The method of claim 4,
The impedance of the at least two capacitors is less than a threshold impedance within a certain frequency band, active current compensation device.

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