DE1763325A1 - AC power supply - Google Patents

Description

AC Power Supplies The invention relates generally to static Current alternation: converters and especially new inverter systems, the output transformers use that directly form multi-stage wave farms of a desired fundamental frequency. The inverter system can be used to generate single or multi-phase alternating current for moving or stationary. Facilities used: The inverter the invention is relatively effective and robust, and allows significant Nominal power with negligible harmonic content. He is particularly suitable as a fixed frequency source in aircraft. and bullet sex. Its output frequency leaves maintain itself accurately and can thereby improve navigational and other performance Improve plague frequency instruments and facilities. Primary power is obtained from suitable alternators that are driven directly by the motors. The high initial costs and the lavish maintenance of those at constant speed Working drives to maintain the alternator frequency are avoided. The thus generated variable or Ilwilde "frequency power becomes Feed the inverter rectified. As an advantage of the system can be an essential Part of the alternator power directly for other electrical power demand cases used on board. These concern heating, lighting and de-icing systems, Embodiments of multiphase inverters according to the invention enable less effort in terms of dimensions, weight and costs compared to single-phase executions. For a given total output power, the components of the Inverter, for example the controlled silicon rectifier in a multi-phase arrangement more economical. In addition, a large number of phase-related channels are available Forming a nominal output power arranged in series therein. By this feature the voltage and power requirements of the individual channel components accordingly reduced, thereby increasing the reliability and the cost of the invention Inverter degraded. In addition, the resulting multi-level Waveforms less harmonics when the number of channels of the inverter is increased, as will be described in detail below.

The static inverters of the present invention provide polyphase alternating current power at a desired frequency from a direct current input power. A direct current rectifier element is connected upstream of the inverter when the primary power changes. Power generator or one is alternating current power. If the power source is a battery, such as in a laboratory or a lift truck, such a rectifier is not required: the ability of the inverters to supply AC power is determined by the rating of the short-circuit ratio banks or their equivalent, the size of the assigned output transformers and the number of its channels. The inverters can, for example, be designed for 400 Hertz output in the range from 0.5 to 120 kilo volt amperes. With a common basic frequency, the outputs of several such inverters can be connected in parallel directly to a common bus line: The basic ideas of the invention can be applied to the high-voltage transmission of direct current power over distances. Cave power switch tubes such as "Tgnitrona" in place of the short circuit ratio banks could convert such DC power for AC power lines at 60 Hertz.

Some exemplary embodiments of the invention are shown in the figures and described below: FIG. 1 is a block diagram of an exemplary AC power supply for use on board an aircraft, FIG. 2 is a schematic circuit diagram of a two-channel three-phase current converter according to the invention Fig. 4 shows the square wave voltage inputs on the primary windings of the summing transformer of Fig. 3. Figs. 5 and 6 show the waveforms of the respective output signals on the secondary windings of the summing transformer of Fig. 3 at Input signals according to FIG. 4.

Fig. `1 shows waveforms in Sections A through D. training stepped signals at the sinusoidal output in the two-channel inverter, Fig, 8 is a schematic circuit diagram of a silicon controlled rectifier bank; the rectangular inputs of Fig. 4 to the primary windings of a summing transformer gives.

Pigo 9 is a circuit connection diagram of the two sets of secondary windings for generating a three-phase output power in the two-channel inverter, for example.

Fig. 14 shows the relative time phase relationship of the rectangular Inputs to the respective summing transformers of the two-channel inverter.

Fig. 11 is a schematic circuit diagram of a typical portion the example of the square wave generator for the two-channel inverter.

FIG. 12 is a block diagram of a follow-up ignition system that controls the controlled silicon rectifier banks of FIG. 11 in sequence. Fig. 13 is a schematic circuit diagram of a typical section of the subsequent ignition system stems of Figure 12; Fig. 14 is a schematic diagram of a Reference summing transformer. Fig. 15 is a plan view of the cell assembly an example of a summing transform mators., Figo 16 and 1'j are developed winding diagrams grams used to describe the construct tion of the summing transformers of a Two-channel inverter system used are. Figo 18 shows in sections A to F- the Summing transformers and their speaking waveform components for a NEN six-channel exchange according to the invention - judge. Fig. 19 shows the signal components from Fig. 18 formed waveform formation, which is a stepped output signal of the Six-channel inverter generated. FIG. 20 is a circuit connection diagram of FIG Six-channel summing transformers Inverter to generate the off. output signal from Fig. 19. Fig. 1 shows schematically an application of the AC power converter according to the invention for use on board an aircraft and which is suitable for commercial, military or private use. Each motor, not shown, is mechanically coupled to the drive shaft 26 of the power generator 25 for an individual inverter power supply section. A permanent magnet generator 27 is contained in the main generator 25, mainly for feeding its field winding 28. A constant DC voltage level is achieved by the Pestkörper rectifier 30 excited by the permanent magnet generator 27 via the line 31 and by a voltage regulator 32. The regulator 32 is connected to the rectifier 30 by the line 33. A protective circuit 35 that responds to errors is coupled to the voltage regulator 32 via the line 36, to the rectifier 30 via the newspaper 34 and to the alternating current output (41) of the system via the lines 37, 38 excited that the nominal output chaela voltage of the generator 25 is maintained within reasonable limits despite its variable output speed.

The current inverter 40 has a three-phase output... Alternating current of precisely predetermined frequency (f0). A typical output frequency for f. Is the normal 400 Hertz for operating instruments, gyros and electronic devices on board the aircraft. The four-wire three-phase output 41 of the inverter 40 contains a neutral line (N). An output filter 42 of appropriate size was fert a good einusförmige waveform for the Dreiphasena, usgang to the clipboard 44 of the frequency f0 on the three-phase Wechselstromleitungen43 with the neutral paper (N). A negligible harmonic content appears at the f0 output: Therefore, only a minimal electromagnetic shielding of the f0 power supply bus line or the cables is required. This results in a considerable saving in costs and weight. The inverter 40 is fed with direct current from a power rectifier 46 via the lines 47, 48. A basic frequency unit 45 feeds the inverter 40 with a fixed pulse sequence (f .

The generator 25 is preferably a multiphase alternator designed to operate reliably and efficiently in terms of power generation and has a favorable weight factor. @ Its output frequency (fg) is proportional its rotational speed, which in turn depends on that of the driving motor is. For example, jet motor pad speeds can range from 3300 to 6500 UPM fluctuates in flight. The generator (25), for example, has a three-wire, three-phase output line 50, to which the direct current rectifier 46 is connected via the cable 51. The power rectifier 46 is conventional for handling the nature of its input power and to convert it into direct current at the required nominal voltage and current output educated. The rectifier (46), for example, supplies at its output terminals at the newspapers 479 48 a DC voltage of 285 Y, whereby this to achieve greater Reliability should preferably be kept floating or floating.

For the same reason, the electronic units are 409 429 45 ungrounded; however, they can be earthed if necessary.

The output lines 50 of the main generator 25 run to one Terminal block 52 as a currency exchange newspaper source with variable or "wild" Frequency (f.).

As mentioned above, power is variable frequency (fx) for. many electrical functions are useful on board an aircraft. Typically the direct output frequency (fx) fluctuates over a range of 2: 1o Such wild, frequency performance (f.) is suitable for de-icing, heating, lighting and other purposes. The on Directly generated power (fx) used can be as 20% or even 506 of the respective board Nominal powers of the generators are predetermined. The rest of the capacity generated is used to drive the rectifier (46) for the power inverter (40).

Fig. 2 is a schematic circuit diagram of a three-phase inverter (40) arranged in two channels. Channel no. 1 contains the square-wave generator 55 which feeds an associated output or summing transformer ST-1. Channel no. 2 contains the square wave generator 569 which feeds its transformer ST-2. Both square wave generators 55, 56 are solid-state three-phase devices. They contain respective banks of controlled silicon rectifiers for the formation of voltages at the right time and in the right phase in a reasonable order of magnitude at the transformers ST-1 and ST-2. The operation d.of the short-circuit ratio banks is triggered by a follow-up ignition switch » achievements 5 ¢, which in turn from the fundamental frequency. pulses (fƒo) are controlled by the unit 45. the Ignition unit 54 is connected to the generators by cables 53, 53t 559 56 shown attached :. For example, circuits for units 54, 55 and 56 are related to the Figures 8: to 13 shown and described. The rectangle genes Rators (55, .56) are from the power rectifier (46) driven via the direct current output lines (47, 48), Your three-phase square-wave currents are each pri- märwicklungen given the transformer ST-1 over the Lines 579 and the transformer ST-2 via the line 58o The transformers ST-1 and ST-2 are three phaeig and have stationary iron sheet piles building. The. Secondary windings of the output transformers ST-1 and ST-2 are optimally stepped waveforms of the fixed fundamental frequency (f,) in series- switched. Such a connection is made possible by the wire cable 70 between transformers ST-1 and ST-2: indicated, optionally with a neutral fourth wire (R) is provided. Fig. 3 is a circuit diagram of the basic or reference summing transformer ST-1 from channel no; 1 (see Fig. 2) p Er has a sheet metal core 61, 61, in a preferred wise toroidal cell casing as in Fig. 15 is shown. : a primary winding 60 consists of the three phase windings 62, 63s 64 which in conventional arrangement for example according to the type of in connection with Fig. 16 below described loop like sound f are wrapped . The secondary winding 65 consists of the Three-phase windings 66, 67, 68 which are in spatial phase wound to the respective primary windings 62, 63, 64 are. The primary and secondary windings 60, 65 of the Trans. formats thus contain: the three phases: g1, 02 '0 The secondary windings of the summing transformers each Channel with the exception of that for the basic channel No. 1 are around predetermined amounts versus their respective primary. developments shifted in spatial phase. The time phases of the square-wave input signals to the respective ligen primary windings are in time phase shifted. The result of given and interrelated shifts of this kind in spatial and temporal phases se shows the already mentioned output signals summed up optimally graduated waveform formation. The here in question The underlying ideas are below, in particular in connection with FIGS. 7 and 18 explained in detail. The reference summing transformer ST-1 with its » the primary (60) and secondary (65) windings in star circuit shown; it goes without saying that instead Triangles can be used. The mid- lere or common terminal 69 of secondary winding 65 forms the neutral power connection (N) for the 44 in Pig. 2 indicated three-phase four-wire output. The cable 70 switches the secondary winding of the summing transformers in series, as in connection with Fig. 7c and 9 for the two-channel version and in FIGS. 18 and 19 for the six-channel version is shown and explained. This results in a balanced multi-phase output output signal summing, the optimally stepped waveforms relatively little distortion produced that easily are to be filtered. The generator 55 to the primary winding 60 of the summing transformer ST-1 given rights is in 4 shown graphically. Each winding 62, 63, 64 a square wave voltage becomes alternately positive (+) and negative (-) components imprinted the respectively a duration of 180 ° with the frequency of the system gangs, namely (f0). When the winding 62 the Reference phase 01 is: then winding 63 is phase 02 and gets a square wave voltage imprinted like shown is delayed by 1200 in time phase; and winding 64 is phase 03 and receives a tension voltage .uppressed, based on 01 at 240o, and on 02 is delayed by 120 °: In fact, the same as for multiphase transformers and motors a result generating rotating field; where the induction in the secondary winding 65 on an effective legal corner base as described below. A device for generating three-phase square wave power According to Fig4, banks of transistors can be controlled Silicon rectifiers or gas-filled tubes keep. For example, a short-circuit ratio switching The device for this is shown in FIGS. 8 and 11. Which he- inventive inverters require multiple Sets of such multiphase square voltages, respectively in a given time phase shift to excitation their respective channels. Circuits for achieving the required exact timing and ignition Formation of the subsequent input voltages are detailed described in connection with FIGS. 11 to 13, Figures 5 and 6 show the resulting waveforms of the signals at the secondary winding output (65) of the transformer ST-1 appear if the above th three-phase square-wave voltages on its primary winding input (60) are given, see Fig. 2 and 3: In each secondary winding 66, 67, 68 is one stepped waveform induced. Fig. 5 shows their waves. Form output at the starting point phase-to-ground 69. The one on winding 66 (phase 01) is in time phases relation to the 01 rectangular entrance (Fis. 4), whose (+) and (-) half-waves are each 1800 long. the Secondary phases 02 and 03 are accordingly around 1200 and 240o shifted in a temporal phase, like the - FachmEnn readily understandable Each stage of the shafts of Fig. 5 is 60o long and has a re- lative size of 0, 5. Each full wave over 3600 thus consists of eight stages, that of a period for the f0 output. The plateau peaks have a size of 1, o. Such stepped output waveforms result from the induced by the multiphase field induction th tensions due to around 1200 in spatial Phase shifted windings of the transformer ST-1 and its three-phase square inputs in the effect Show rotating field. The corresponding phase - against .- Phase waveforms, for example in the phases 01 to 02 are shown in Fig. 6; the 0 ° time reference also corresponds to that of the phase 01 input (Fis. 4). It should be noted that this output signal (0lbis 02) only a duration of 120o for both (+) and Section with 60o reactive values or zero current between has. In addition, its relative Amplitude 0.866 compared to phase-to-ground Waveform (F #, 5), The waveform of the output signal nals between phases 02 and 03 is the same as between phases 01 to 02 apart from the fact that they is delayed by 120 ° in order to commence with the input phase 02. collapse; and that between phases 03 and @ l1 is delayed by another 1200. It goes without saying that the multi-phase # -Reehteekeingang- voltages on the multi-phase primary windings of the Summing transformers (ST-1, ST-2) the idealized Waveforms of Pigö 4 correspond. Although sharp increasing square waveforms shown the system according to the invention too. at initial waveform men with rounded corners or inclined slopes and Waste form effective. Special means of production such multi-phase square currents in comparison application of the system according to the invention optionally be seen. Mercury vapor control tubes as well Festkörpervorrchtungen are intended for the The three-phase rectangular arrangement shown in Fig. 4 is speaks of the electromotive force measurements of each-- the output line (or cable 57) to a virtual one or voltage center of the generator (55) or to the opposite link during the newspaper, like is understandable to the person skilled in the art. The phase versus phase However, the voltage of the generator output (57) is based as shown in Fig. 6 for the secondary winding 65, on a three phase basis. The size of the secondary Voltage depends on the turns ratio of the primary secondary winding (60) to secondary winding (65) from how will be explained. After all, the corresponding the parameter of the polyphase outputs of the other right corner generators in the system compared to the basic gate (55) shifted in a temporal phase, as already was interpreted. Fig :. 7A to 7D show the basic ideas of the initial Waveform design of the system for two-channel alternating judge (40). Figure 7A corresponds to Figures 3 and 5 and shows the reference summing transformer ST-1 with at its pri- märwicklungen (60) applied square wave voltage E1 (three-phase). The phase-to-ground secondary waveform (e1) for the reference winding at 00 (and with the other windings on Dreiphasenbaais) is the eight-step waveform of FIG. 5. This waveform (e1) has a peak magnitude of b on the unit level 1, o with their Intermediate stages a at the level of 0.5, the secondary windings (65) of the transformer ST-1 are in phase with its primary windings in the manner described in connection with FIG. 16 below.

Figo 7B shows the operation of the second summing transformer (ST-2) of the two-channel inverter (40). The three-phase transformer ST-2 is the same Transformer ST-1 apart from having its secondary windings in spatial phase are vetachoben with respect to its associated primary windings by 30a. This training feature is explained below in connection with FIG. The resulting (+) and (-.) Waveform (e2) of the ST-2 secondary windings phase-to-phase neutral is the same as that shown in Fig. 6 for phase-to-phase of the ST-1 secondary windings. The spatial phase shift of 30o in the ST-2 provides such resultant Waveform (with blank values changing 60o) and size of 0.866 for (c), for the (+) and (-) 1200 sections according to Fig. 5.

However, in order to produce the desired twelve-step output waveform of FIG. 70, the secondary output of the ST-2 is shifted so that it is delayed in time by 300 from the 00 reference, as with the ST-1 output. This is achieved by The three-phase square input (via 58) is pressed on the transformer ST-2 with a delay of 300 in relation to the reference input (at 57) on the ST-1. Such an arrangement is described in more detail in connection with FIGS. 9 and 10 and is provided by the follow-up ignition circuits according to FIGS. 12 and 13 arranged. The net result is an output wave. form (e2) on the ST-2 secondary windings. is pushed at the 30o delay point and in proper three-phase alignment begins as in Fig. 7P is shown and as will be understood by those skilled in the art. Figo 70 shows how the respective secondary windings the 8T-1 and ST-2 to generate the desired stepped th output waveform (e3) for the inverter in Are connected in series. Each secondary winding of the trans- formators ST-1 is connected in series to the respective ligen secondary winding of the transformer ST-2. Her generate combined induced voltages (e1 + e2) the sum voltage waveform e3 on an instant. Time base: To achieve the resulting output e3 the connections run from the neutral point n1 of the 8T-1 to the series connection of the winding lungs. Similar connections are made for the two other winding sets of three-phase transformers ST-1 and ST-2, as will be seen. The optimal twelve-step waveform of the output signal. nale e3 runs over 360o in alternating (+) and (-) sections of 1800 each: their peaks at d have a relative size of 1,866 and connect the b and c levels of the signal components e1 and e2. Your peak zen plateaus each run over 600, with their intermediate intermediate steps are 30o. This twelve-step waveform (e3) becomes stable and relatively easy here in two channels with two output transformers 8T-1, ST-2- produced, such an advantageous twelve-step world lenform is in itself well-known in inverter technology known. The current inverter according to the invention applies such twelve-step waveforms to advantage sticky in the two-channel embodiment; and waveforms with a significantly higher number of stages still ahead more beneficial in designs with more channels. Example way, Pigo 19 shows the 36-step waveform of a Six-channel inverter. The twelve-step waveform (e3) is thus for all three Phases 01 9 02, 03 of the two-channel inverter (40) placed, each 120o apart in a temporal phase lying there. The connection of the secondary windings each other in three-phase with the newspaper Neutral (N) is shown schematically in Fig. 9, the output cable 41 is connected to the three-phase filter (42), that the harmonious content of the initial tiered Waveforms removed, allowing for clean multi-phase output supplies output currents with the frequency of the system (f0). Fig. 7D shows the resulting output in sinusoidal ger waveform e0 for each phase. The twelve-stage waves. form does not contain any harmonics below the eleventh level; and contains the 11th and 13th harmonics of the fundamental frequency f o. In the balanced three-phase system, the next- apparent harmonics the 23, and 25, second magnitude order. The latter are easy to use for f0 frequencies zen of. 400 Hertz or higher to filter. A controlled silicon rectifier bank provides the Multi-phase square input currents. For the rectangular genes rators (55, 56) for the summing transformers Se-1, ST-2 becomes a three-phase bridge Weohselrichterkreis used. Such bridge inverter are in GR essential terms in the art. The change. The rectifier of the generator 55 for Se-1 is shown schematically in 8 shown. Each phase 01, 02, 03 contains a service. Short circuit ratio niapair 75a = 1.76-1; 75. »2, 76 # 2i 75- = 3, 76: 3. An air core induction or choke coil with a central Tap is between each short circuit ratio pair for the switchover is connected in series and forms the induction tion coil sections: 77-1, 78-1 #, 77-2, 78-2; 77-3, 78r3. The output power connection of each short-circuit ratio couple is relieved from the junction of its induction pair of bobbins removed. The respective bridge exit conduct 79. »1, 79-2, 79-3 are on, the windings 62T 6-3-r 6 ¢ of the primary winding 60 of the transformer ST-1 closed over: newspaper 57-1 for ß (,; newspaper 57-2: for 02 Newspaper 57f3 for 03o The generator 55 is driven by the same .. power cable 47-48 powered. The from the cathode and the grid electrodes of the short-circuit proportions in Figy 8 are running newspapers shown unconnected for the sake of simplicity of the schematic. They are connected to other components for the short-circuit relay ignition and conversion in a given pole position drawing connected. An example circuit for this is shown and described in connection with FIG. ben *. Exact positive ignition and extinction of the short-circuit ratio elements of the square wave generator provides sharp Square waveforms with rise times of a few micro-. Seconds and with the required multiphase setting @ and timing for optimal operation of the inverters (see Figo 4 @ 0 The secondary developers 65, 651 of the summing transformers (ST-19 ST-2) .. are connected in series to the above illustrated three-phase, twelve-stage waveform outputs to create. Fig. 70 shows this circuit for a phase se; 9 shows its three-phase circuit. The respective se- secondary windings 66, 67, 68 of the ST-1 are each in electrical series locking with their assigned Phase windings of transformer ST-2 through three line cables 70 and a common neutral newspaper (N). The series connection relationship is also indicated by the direction of the arrows on the windings.

An important advantage of this series arrangement of the output windings is that at a nominal output voltage the voltage of each transformer (ST-1, ST-2) need only be about half the final tension. Through this there are less expensive short-circuit ratio elements for the generators (55.56). In fact, the result is a current multiplication for any given Rated output power. The use of multiple channels in the inverters is more economical with inverter systems of higher power. The relative Advantages of using six channels are related to below 18 to 20 are described as well as the general basic ideas.

It should be noted that the temporal phase relationship of the secondary windings 66 ', 67', 68 'of the second transformer ST-2 of the two-channel inverter (40) is shifted by 30 ° with respect to the reference (ST-2) primary windings, as explained above became. In addition, the three-phase square input (58) on the primary windings of the ST-2 transformer is 30 ° behind the corresponding input phases (57) on the transformer ST-1 in a temporal phase. Fig. 10 shows the time phase shift by 30o of the phase 1 currents for the transformers ST-1 and ST-2. Each is a rectangular wave with the fundamental frequency (fo), with the one for ST-2 at 30 o compared to the 0 ° reference start for ST-1 starting (delayed) later. the the other two phases are 021 03 of the input .at S1-2 similarly offset to the required three-phase. Generate the right signal input (58) on the transformer ST-2. The fol- lowing described in connection with Fig. 12, 13 ignition circuits (54) control this temporal phase relationship for the respective three-phase electricity generation of the short-circuit ratio units 55, 56. 11 is a schematic diagram of phase 01 of the three-phase bridge rectangular generator 55 for the Two-channel inverter (40). The other two phases sensors are similar in circuit and mode of operation. lichd, ho by 120 °, or 240o in a temporal phase pushed. The section of phase 01 has a controlled tes silicon rectifier pair 75-1a 76-1 and a pair Short-circuit ratio switch 80-1, 81-1. The nominal current of the short-circuit ratio switch is un- about 30% of the power shortage ratios. Of the Capacitor 85r1 is used to generate enough electrical Energy to delete the short-circuit ratio elements 75-1 or 75-.2 when switching to save as will be described. The diodes 82-1, g3-1 are control diodes. During operation, the short-circuit ver .. members of the relationship. 75e1 and 81a-1 open at the same time, while the failure ratio elements 76-1 and 80-1 be locked; and also in reverse order. For this purpose the phases or directions are the applied continuous signals for the short-circuit ratio. gliederh 15-li g1 "i on one side in phase, and for the Xarzschlaß membership members 76-1 g0 "1 1ä_'1.80'0 delayed " Gate transformer 6T-1 has a primary winding Center tapping from Sections 86, 867 which is published by the newspapers 87-1, 88 »1, 89w1 at the pole ignition circuit (54) are connected. For the Short-circuit ratio control circuits are four independent ones Secondary windings for gate control 91 # »1, 92.1, 93.-1, 94-1 used. The secondary windings 91-1 and 94-1 are to the respective gates of the corresponding short connection ratio members 75-1, 81-1 connected; the Secondary windings 92 # »1, 93-1 to those of links 76-1, 80-1. The connections of the latter secondary winding the couple are relatively opposed to those of the former. switched. The left terminals of the gate control winding gen 91-1 and 94-1 are therefore linked to the gates of the short connection ratio members 75.-1 and 81-1, while the right terminals of the windings 92 # »1, 93.1 to those of the short-circuit ratio elements 76-1 and 80.-1 are connected. A current-limiting protective resistor stand (90) is preferably in with each gate line Series connection used. The secondary windings for Gate controls are also attached to the respective cathodes of the four short-circuit ratio elements placed. Between the respective short-circuit ratio members and cathodes are resistor-capacitor networks 95 to 98 and condenser Sators (99) between the phases in the manner shown switched to achieve stability and wild frequencies to regulate zen. The square wave generation of phase o1 works like follows: If the gate terminals of the gate control like sounded 91. »1 and 94-1 in their positive period are located, the short-circuit ratio-power element 75-1 and the short-circuit ratio switch 81..1 operated and opened. The current then flows from the 'positive manifold 47 via the link 75-1 and the Induction sink 77 # -1 to output line 79--1 of the Phase 01 and to coil 61 of the summing transformer ST-1 via newspaper 57- »1 (see Fig. 8). While the- This period - is the opposite power element 76-1 blocked, in which no current to the ne- negative manifold 48 flows. However, electricity flows at the same time by the short-circuit ratio switch 81a1 and essentially charges the capacitor 85-1 the voltage between buses 47 and 48 .on, with its assignment positive on the left will. When the capacitor 85-1 is added in this way is charged, the current through the element 81a1 is sub- broke and it switches itself off as an automatic switch * Positive current from the bus 47 overflows the short circuit ratio element 75-1 to the output line 79-1 over a full 1800, as 01 signal in square form (see Figa 4), whereupon this member is blocked . A polarity reversal of the 01 output current of the newspaper 79-1 is activated by quickly locking the link 75-.1 and opening its double short-circuit ratio power link des 76: b1 never achieved in the exact time ratio. This short Closing ratio, timing is determined on the successive the points of 1800 and 3600 at the f0 period counter- recovery by the ignition circuit to be described (54) achieved. The reciprocal primary half 86 'of the trans- formator T-1 is energized and the primary half 86 stimulates. The phase of the control signals through the secondary control windings are thereby reversed. The Gattersig- nals on links 75-1 and 81-1 become negative Brought phase and the gates of members 76-i and 80-1 directly into the positive. The timing element 76-1 is ignited, the direction of current through the 01 - newspaper 79-1 is reversed, and the current flows through the induction section 78-1 and the now open element 76-1 to the negative collecting line 48. The duration of this reverse current flow is 180o and supplies the negative (-) square output half of phase 01. The f. period is then repeated in the manner described here. It is important that at the end of the 180o period the newspaper of the power element 75-1 is interrupted as quickly as possible and then its opposite power element 76-1 is ignited as quickly as possible, and vice versa. The switching circuit , for example, fulfills this function and generates square waves with sharp rise times. As already mentioned, the gates of members 75-1 and 8'1-1 are blocked at the end of the positive (+) half-period and their opposite members 76-1, 80-1 are opened, ie their side is positive. The latter members then become conductive. The capacitor 85-1 has been charged in the positive half cycle to essentially the voltage between the direct current lines 47, 48, where .. at its left assignment is positive. When the short-circuit ratio switch 80-1 is connected, approximately twice the voltage of the bus is applied to the cathode of the power element 75-1. This increases the negative grid voltage of the element 75-1 and this is canceled, as is well understood by those skilled in the art. The switching function of the capacitor 85-1 is then reversed. His right occupancy acts thereupon e the conductive member 80-1 positively to the potential of the manifold 47Wenn the capacitor 85-1 then charged, the current is interrupted by the member 80-1 and is locked. At the 360 ° point of the 01 period, the positive control signals on the gates of the short circuit ratio elements 76-1, 80-1, and. the links 75-1, 81-1 are opened directly. Through the newspaper of the element 81-1, the charged capacitor 85-1 is placed on the negative bus line 48 and thereupon the negative grid voltage on the power element 76-1 is increased and this is extinguished. This switching period is repeated with each square generation of phase 01 of 360e with frequency f o.

The switching period with a negative voltage increase for the power element is intended to ensure that it is safely blocked. For this purpose, the capacitor 85r1 is connected to the inductive tion coil sections 77-1, 78-1 on the basis of a time constant related to ensure that the duration of the Increase in negative grid voltage is greater than that to delete the special short-circuit protection used ratio power switches required minimum Period. For example, an inverter (40) with a nominal output of 10 kilovolt amperes short- termination ratio power elements with a nominal power of 110 A 600 V (G, E type C 152), short-circuit protection ratio switch with 35 Ap 600 V, control diodes (82-1, 83--1) with 25 A, 600 V (GE type IN 1197) 9 induction coil sections (77-1, 78-1) with 70 microhenries each, 280 Mkrohenry from end to end, and short-circuit Ratio shunt diodes 100-19-101-1, type IN 1197. The shutdown time of 15 microseconds for such Short-circuit ratio power circuits as a practical minimum are reliably fulfilled by the listed Z-0 components (77-1, 78-1, 85-1), which increase the negative grid voltage over 30 microseconds. Shunt diodes 100-1, 101-1 are each connected across the short-circuit ratio power elements: diode 100r1 between bus 47 and newspaper 79-1 for element 75-1; Diode 101-1 between bus 48 and newspaper 79-1 for link 76-1. The diodes 100-1, 101-1 provide return lines for the discharge of the capacitor 85-1 when it switches: (a) via the control diode 82-1, the coil 77-1 and the diode 100-1 to the bus 479 when the negative Grid voltage of member 75-1 is increased; and (b) through diode 101-1, coil 78-1 and control diode 83-1 when member 76-1 is cleared. In addition, the shunt diodes 100-1, 101-1 form return lines for reactive currents which can arise during the operation of the short-circuit ratio power elements under inductive loading conditions. It will be readily understood by those skilled in the art that other switching arrangement may be used instead.

12 is a schematic block diagram of the sequential firing circuit 54 (STG) for the dual channel inverter 40. It includes six sections with respective control transformers T-1 through T-6 to provide drive signals for the gates of the short circuit ratio square generators 55 and 56. Each phase of each generator contains a bridge short circuit ratio pair gated by a single control transformer and several at a time Secondary windings has (91 to 94) m three such Control transformers provide the drive signals for a three-phase generator in correct time phases " relationship. As. above in connection with Fig. 7B and 10 are those on the second. Summing transformer (ST-2) given three-phase right # - leakage currents of the generator 56 in a temporal phase opposite above those from generator 55 to transformer ST-1 delayed by 30o. When using the positive half-wave starts of the Phase 01 of the generator 55 as a reference, are the time - borrow phases of its respective generated phases 0d, 0 2, 'ö3 following 0 °, 12009 240 °, and 300, 1500, 270 for the generator 56, a square wave switch follows for every consecutive 300 (temporally) while taking into account the negative Right-hand wave halves o Six 'consecutive 300 Clock pulses occur at 0 °, 30c, 600, 900a 120ƒ, 1500o Four of these impulses are positive Half-wave starts together, namely: at 00 and 300 for the 01 APaar; at 1200 and 1500 for the 02 Paaro By reversing the secondary winding connections for the said 600 and 90 ° pulses, so that the straight "negative:" short-circuit ratio elements thereby would ignite, the negative side of the short-circuit ratio elements for the 03 phase of the generator b 55 at (600), and the generator 56 at (90®) each in correct time sequence: Such an attachment of the tax. Windings of the corresponding transformers (T-3 and T®4) for the short-circuit ratio not shown members of phase «3 achieve this result, your every occasional 2400 and 2700- positive rectangular-shaped Half-waves then occur in the correct time phase ai.ehung on (180® later) r around the three-phase rectangular power sets to complete. The following 300 ignition pulses generate the second 1800 half-wave sections (1800 to 3600) of the aforementioned six square waves and complete the two sets of three-phase currents with 30ƒ separation. The ignition taking place in this way at 300 uses twelve clock pulses for each 3600 output period with the fundamental frequency f0 with continuous generation, The six drive transformers T-1 through T-6 will be. each rectangular waves impressed in such a way that in turn, the said rectangular tax currents for the short circuit ratio generators 55,56 deliver. Individual, block-shaped at M1% 1 to MV-6 interpreted multivibrators produce the rectangular Ripples in these transformers. Primary winding lines 87-1 to 87-6, or 89-1 to 89. »6 are to these Multivibrator units connected. The primary Center taps 88-1 to 88..6 are each to the positive collecting line 47 connected. The primary transformer halves are alternately excited and induce in their respective secondary windings 91-1 up to 94-1 etco square-wave control signals with the f0 period number. The multivibrators MV-1 to MV-6 are in chronological order through ring counter circuits with AND circuits A-1 to A-67 and an electronic rule fundamental frequency clock 45 controlled. The A- means MV-1 is fired in sequence when its U N D- Unit A-1 by turn-over activation or Ignition of the previous section (MV-6) over Newspapers 108-6, 109-6 toughened or "discontinued" has been and if: the subsequent impulses of the clock 45 via the clock line 105 and the lines 106. »1, 107-1 are applied. Such Simultaneity takes place through newspapers 126-1 or 127-1, u the cultivibrator KV-1 in its opposite phase blocked. convict. Thereupon the polarity the control currents through the primary and secondary windings gen 91-1 bia 94-1 of transformer T-1 reversed. One such switching activation of the multivibrator KV-1 in turn causes a bias 11 position signal directly to the next AND unit (A-.2) via the line tungen 108-1 ,: 109-1 is given. One example The circuit for the MV-1 and A-1 units is 13 shown and described. The tilted MV-1 unit remains in this state a duration of 180®, whereupon they in their previous the state is tilted back. There are thus alternating Seldom positive (+ ) and negative (-) rectangular ones Shaft halves in the windings of the transformer T.-1 generated with the fa period number. The flp-flop shares Fourth of the multivibrators is in each case by a duration by six pulses apart. The first of these impulses tipped the multivibrator MV-1, which is the AND unit A-2, as explained, directly through lines 108®1g 109-1 "discontinued". The next pulse occurs 300 later the clock generator line 105 and already reached "set" AND unit A-2 via lines 106-2, 107-2 and tilts at the same time and causes direct Switching of the cultivibrator MV-2 in its opposite set state via the newspapers 126-2s 12p # 20 The six multivibrators are in this way in the Order KV-1 to MV-6 tilted. The next (seventh) pulse from clock 45 occurs 180 later than the first one that flipped the MV-1 unit and hits its AND unit (A-1) which has already passed through the MV-6 unit has been "discontinued". This will then the MV-1 unit straight back to its original one Position tilted back, as above at the beginning, and the phase of their output is reversed, the exact timed changeover drives of the multi vibrators continue in sequence and that Tilting back takes place in cyclical repetition. the Tilt phases generate the first 180o part of the right angular waves; the tilt back phases the second 180o part, sequentially complete each .360 ° @ period. The mentioned (6) legal corner currents as two three-phase movements in time Phase separation of 30o made. When the MV-2 Unit 30o later than the MV-1 unit. tilts, as mentioned above, she gives her- on the other hand a "setting" signal to the A-3 AND unit of the MV-3, not shown, by the newspapers 108-2, 109-2. The next clock pulse on line 105 will be given to the AND unit A "3 to reverse the phase initiate in the MV-3; and similarly in pulsed sequence for KV-4, MV-5 and MV-6, Die sixth AND unit A # -6 is through lines 108-5, 109-5 "set" when the fifth MV-5 unit has tilts. The flip-flop operation of the six MV-1 multivibrators until MV-6 successively changes the polarity of the right-- ' corner stream halves, which on their assigned TraAhr-- mators T-1 to T-.6 , if one'd-in @ - .: T # rans- formator T-1 as a reference, then begins at this m'die- Oo and the "negative" (180o) uiPhase. These concern the relative time phase of the T-1. by the MV-1 for the short circuit ratio bridge pair of phase 01 of the Generaters 55 (Pig * 11) generated alternating halves: » Periods. The relative time phase of the rebar tariff .. sgnale from transformer T2 is thus 30o and (2100), - as stated; whereby the Multivbrator MY-2 has one clock. impc @ ls -later than the XV-1 -is actuated .: Die aufein. other outputs not shown - occur with: - (600) and 240 ° for T-3-9 (9400 ') and 2700 for T.4; 1200 and (3U *) for T-o5- and: 1500 and (3300) for TwC. Your floodplain. walk and your turn through the two Dreiphaeen @ r - Final course relationship @ Brtakengeneratoren 55, 56 is like has been described above. 74.4 13. Is an aohematic a 'circuit diagram the initial. but without the health management (54) of Fig: 12 and contains the Beeugamultivibrstor MY - 1 1 the AND unit A m and the clock pulse generator 45 The 7requene fo the clock Impulses is twelve times t the Aaagangentromfre- quena, (f4) 1 namely 4800 pulses per second for one 4Q0 Hertz output. The fundamental frequency unit 45 can be a electronic oscillator be # that with a level, - traistort a tuning fork t a temperature-controlled one Crystals one. RV0 Sohwingkreie or the like * built up. is * The housing and stability of the clock unit 4 essentially determines the accuracy of the phases setting and. Proeuens the system build $ s The binary 110i'45 is used by denrli: cheet> es_ell.el u via the oriderstd 102 excitedq their impulses are Resistor 104 d: 4r base the transistor 110 pushed on de ssin.etraetite -egati gerttete impulses with the pre: 0, o-on the @eifiru 105 gives * D itted0Treietere 110 is about the diode 111 the negative 13 parts line (48) must be given. ollektu to ditto. Bones @ ktgeberle @ itu1 * The example multivibrators are unstable and each contain a transistor amplifier pair, the Magnetically via the assigned regulating transformer are coupled. The respective collectors of the Traneis Torpaaren 11 ?, 11'4 of the cult ghrator MV-1 Bind. the Primary winding , 86-8P of the Tranafermatorn T.-1 through the Newspapers 87.1t 89001 placed, their bases are 3a cross- switch on, the winding in feedback via the Repplungewideerst4o 1159 '116 lied. Your em itte electrodes go to the ge »in®gae newspaper 120» die via llipdea 1179 118 and 111 to the negative l # Leiturig 48 runs. The diodes 121 bswo 122 l "ea die Wedge these transistors to a geensea @ s Line 13g, and via the Xiderstand-Kondenesteraartz 137 due Bmitterlei t ux g 120. Each level of vibration with the one from the volt seconds line to my orderly transfarmatore al requenz, run free or swinging is due to the clock generator Cfoa) synchronized with the number of periods. The Plip] Flop 8ynohreenization of every cultivibrator is thereby achieved. is enough to ensure that the sequence of a such Umsehaltungsaktivierungt HRE namely with you, guenz to is greater than its low frequency, like that Pachwa, is readily understandable. / used The ul.ti; vilerata @ r @ raua.aletreri 11'2t 114 wecbaeln in their 'lip-plop.iktvierung under. the Steeaerus g des. AND-Traneieetorpaareee 123 ,. 124 of the unit A # -1- nee Base electrodes of the '-Traneistoreen 112 "114; About the Koppluadteden 1ä # 129 and the i 12fw 4 e 12`, 1: dec11et o r der U. . 123e, 124 applies * ü: Leee "en Bind mbenteel 1, eg Sbew, Idegetä <adee 131, 132 .t der gtmleei 13,5 and, wieederux with the ae ig atiwea g «wo ileitüber e . Diodes 111, 118 connected. The emitters of the AND transistor ren 1239 1:24 are placed on the clock generator line 105 , the the negatively directed pulses from transistor 110 be pressed. The base electrodes of the AND transistors 1239 124 are connected to the negative manifold 48 across Capacitor shunt resistors 133 or 134 coupled, and via coupling resistors 137, 138 with the voltage # or "setting" »lines from the previous one Multivibrator (MV-6 in this case), namely the line lines 108-.6 '109-6, The adjustment line 108-6 runs from the "opposite" Transistor of the final multivibrator MV-6, namely that of the 1500 output signal phase corresponding as on the left side of transformer T-6 in Fig. 12 is: The line 109 # 6 runs from the transistor on the right side of the MV-6 corresponding to the (3300) output signal phase, In order to achieve the required work sequence aim; is the "setting" by the multivibrator MV-6 reversed to MV-1, with the newspaper 108.-6 from the 1500 phase to the AND transistor 124 for the (1800) phase of MV-1 is placed; and line 109-6 from (3300) to AND transistor 123 for the next 00 Phase in the period repetition: The "setting" - Couplings between the other sections are symmetrical trisch 'namely: the collectors of the KV-1 transistors 112, 114 are each connected to the AND transistors of the next section (A # -2) via the "setting" lines 108-1, 109-1 in left-to-left and right-to-right loading drawing coupled ,. like those from M7-2 to A-3, MV-3 to A-4 etc. So if the left M7-1 transistor 112 is at the beginning the 0 ° phase blocks, the left: AND transistor of the A..2 "set" for the next 30o phase. Corresponding is at the (180 °) phase of the right transistor 114 des MV-1 the right AND transistor of the A-2 for its (210 °) Actuation "set" at the next clock pulse. These Coupling in sections, with MV. - 6 to A-1, MV-1 to A-2 begins and continues through MV-5 to A-6 and MV-6 back to A-1 results in an effective ring counter, which the Output sequence of currents from transformers T-1 bis T-6 for pole control of the generators 55, 56 regulates. The ring counter principle tilts every multivibrator every six clock pulses once. The 0o phase "beginning" starts on the left side of A-1, MV-1 and T, .1; and becomes 30o after the start of the (330o) phase on the right th side of A-6, MV-6 and T # -6 activated. When the mul- vibrator transistor on the (330o) side of the MV-6 is blocked, an increased positive signal is through the "setting" newspaper 109-6 on the basis of the 0o-Pha- sen transistor 123 via the coupling resistor 1'37 directed. This "setting" signal is over 1800 's Maintain fo period. The next negative directed clock pulse goes to the emitter of the Transistor 123, whereupon the base electrode of the MV-1 Transistor 112 with respect to its emitter negatively after- drags and locks directly. In the case of the multivibrator system described here, it leads the transistor 112 in the open state current through the half-winding 86 of the transformer T-1 in the direction in which the (180o) control currents - in the secondary windings are generated 91-1 to 94-1, while the Transistor 114 remains blocked. The right transistor (114) of the multivibrator is blocked while the displayed control current phase (180 °) is effective. When locking the left MV transistor 112 through the left AND transistor 123- in the manner mentioned, the right multivibrator- Transistor (114) opened directly via the coupling. There- Current then flows through from the center tap 88-1 the half-turn 86t, around the opposite rectangle » Signal in the secondary windings 91-1 to 94-1, here at To generate 0o phase period start. It is kicking. then one increased voltage on "adjust" line 108-.1 to the from the blocked transistor 112 to the left AND transistor the next unit leads (A-2), the next clock pulse leads to simultaneity in A # »2 and blocking of the left one Transistor of MV-2, whereby the output of the transformer tor e T- # 2 from its (210 °) phase to the 30o phase output is switched, as is now readily apparent to the person skilled in the art will be understandable. This process continues pulsed through the clock line 105 to the 30 ° apart two sets of three-phase To generate output signals o The structure of the remaining part of the follow-up ignition circuit (54) is now readily understandable to the person skilled in the art. be. It. reference is made to the continuous newspapers on the right hand side of Fig. 13. The positive collecting line 47 is common to all six sections and is connected to the central tapping of the remaining control transforma- gates as shown in FIG. The setting Zetungspaar 4a ,, (108-1, 109-1) - is- to the following AND Unit A-2_Kelegt. Newspaper sentence b consists of the three common newspapers 120, 135, 136 for all multi- vibrator transistors. The cable set e consists of negative bus 48 and clock line 105. The returning "set" lines 108-6, 109-6 from MV-6 to A-1 are at d. The clock transistor 110, the diodes 111, 117, 118 and the RC unit 137 are common for the STC System 54. Of course, other their equivalent means and / or circuits are used to activate the pole firing function of the unit 54 achieve. Structure of the summing transformer Fig. 14 is a schematic diagram of a typical summing transfer formators (150) for a three-phase inverter system of the kind described here. In order to be more effective magnetic Effect it has, he has an iron core. The primary windings 151, 152, 153 correspond to the three indicated phases 01 '02' 03 and have 154 star scarf on the "End" terminal tion. The summing transformer 150 corresponds to the above transformer ST-1 described above with the pri- primary section 60 and the secondary winding 65 (see Fig. 39 7A, 8). The secondary windings 155, 156, 157 are tight overall with their respective primary windings 151, 152, 153 couples, as will be explained below. When loading train summing transformer (ST-1) are these secondary winding lungs in spatial phase with their primary windings wrapped. However, the secondary windings are in spatial phase to the winding positions of the primary winding lungs in the other transformers. As already mentioned, the secondary windings (65f) are at Transformer ST-2 of a two-channel inverter (40) in spatial phase by 30o compared to their primary lungs displaced (see Figs. 7B and 9). In practice such a shift can be 30o plus (+) or minus (-) direction, that is , in their spatial phase clockwise or counterclockwise draw be apart. The resulting rectangular Waves have an extension of 120 °, at 0.866 relative size and with 60 ° blank values, as they are induced in each secondary winding. The resulting secondary coil voltages are the same as they appear on the phase to phase basis of the reference transformer (ST-1), the secondary windings of which are star-connected, as shown in FIG. 6 is shown. The spatial phase shifts by 30 ° of the ST-2 secondary windings (65 ') generate such rectangular waveforms in the individual windings and are directly connected to the ST-1 secondary windings (65) in order to produce the desired output waveform, as shown in connection with Fig. 70 and 9 is described. As already mentioned, there is also the temporal phase of the three-phase input current on this ST-2 Trans. » transformer delayed by 30 ° compared to that at the reference transformer ST-1 (see Fig. 7B and 10). -The use of an individual. "Output" or summing transformer for each alternating channel proves to be a very practical arrangement for the following reasons: (1) The nominal output power of the system is divided between the output transformers on the basis of essentially equal proportions. (2) The nominal output voltage is distributed over the secondary windings of the transformer and adds up, as will be explained in more detail below in connection with Figs Spatial phase corresponding signals shifted in the time phase are induced for the correct alignment in the signal summation. (4) The industrial transformers provide the required flexibility of the output current without any significant increase in weight or cost compared to a theoretical transformer with a single output: The structure and / or the formation of the summing transform mators (150) can take many forms. One two example arrangement is in Fig. 15 for the laminated Structure shown * Its core 160 has a variety of radial spokes 162, 162, which are supported by an annular gene magnetic member 161 are surrounded. In the three-phase formation are twelve spokes ( 162) with corresponding different bordering winding slots provided at 1 to 12. The core 160 and the outer member 161 each form La. plate arrangement of high sheet steel quality such as M. »15; .Best quality steel for weight reduction in flight tool applications; or generally good silicon steel as used for transformers to avoid loss, Er.- To decrease fawns, etc. The slat thickness is optional wise, for example 0.152 [/ 0.1016 mm; or thicker up for example to 0.381 mm. The transformer (150) with a slotted core ring (160, 161) is by weight much easier and more effective for those in question here # - standing purposes than conventional E-1, UU, Matel., Core." or other known static transformers to-- regulations. The multi-phase windings have both sides the core (160) and the ring stator (161) in more effective Magnetic effect. The core 160 has a central opening 165. A preferred training factor for the Grölt® of his labe from the opening 165 radially to the base of the spoke is 1991 times the width (W) of the spokes (162) 1 Die same dimension, namely 1, g1 x W is as a radial tie " fee of the ring lamellas (161) Used course k8 = eex other training criteria are used instead, For example, dimensions for a c, ertre @ tför @ tor (150) with the characteristic power 7e5 kilovcslt «p4.r6 Damellenhühee von Kern (1eo> and Ring (161) 44f 45 f Width of the spokes (162) 10j16 mm with: essentially equally wide parallel sides maghetisnhes Arbeiterre Dafchtienger den Rehbraehc (165) 15.87mm hub and ring radial dimensions 19.30 mm, diameter of the spoke lamellas (160) 101'6mm and the outer diameter of the ring lamellas (161) 13997 mm. It is advantageous to keep the magnetic scattering low keep. For this purpose, the wrapped spoke plate lamellar arrangement (160) in the annular lamellar arrangement (1.61) tight fit. A sliding fit with a fragrance gap of 0.0254 mm or less per side is appropriate. Through this a spread factor of less than 5% is possible. At sol- Chen transformers. (150) are electrical powers easily over 90% with excellent weight factors targetable. A close coupling of the primary: and secondary wicks lungs with little electrical loss and education for low magnetic scattering, give an excellent. Output voltage regulation for the system: In the example of the summing transformer (150) according to Fig. 15 are the primary and secondary multiphase windings in the slot areas 1 to 12 wound. It is understood, however, that one of these winding instead put on the cylindrical inner surface (161) the ring arrangement (161) in corresponding slot that correspond to the slot areas 1 to 12 of the storage chen opposite, could be wound. The Trans formator 150T is an effective integrated multi-phase Electromagnetic transmission with a primary three-phase input, the star or delta connection. can, Its secondary output windings are as mentioned for system coupling individually. Dax also have Secondary windings similar training as the frimäe- windings, for a 115/200 rms voltage output of the Syst.ema (when using a 285 V direct current Manifold 47, 48) became a downwind ratio of 2: 1 primary. used to secondary winding. Other Nominal voltages are of course at the f. Output terminals (44) feasible. So if a 285Y phase-to-phase AC output is required, the turns proportion correspondingly lower. The wind ratio can also depending on the short-circuit ratio nominal power and Output voltage are stretched. Mention should also- times that with a two-channel inverter (4Q) every Transformer & ST-1, ST-2) approximately half the voltage as well as half of the output power. 16 and 17 show developed winding diagrams of a Exemplary embodiment for the transformer windings. Of the indicated winding type is: two-layer loop in twelve- stepped training for slots 1 to 12 of the spoke Core ring assembly 161, 162 (Fig. 15). It can be different effective multi-phase winding arrangements are used the, as the expert for motor weighing and transfer. matortechnik is easily understandable. For the For example, a 7.5 KVA transformer (150) was The following wire size is used: wire gauge No. 12 B & S, approximately 0.506 x 10'3 sqmm per AmpAre. The primary wind treatment was wound with six turns per coil. Fig. 16 shows the winding diagram for the three-phase primary windings 151, 152, 153 of the transformer 150th phase 01: Starts in slot 411, continues to slot # 5, the 120o away, then return to the adjacent slot 2 back at 300 , and then runs to slot 4 6, the 300 is behind ß 5; then there is a change to 180 ° to slot, # 11, back to slot .4 7, the 1200 away from this, from. there to the neighboring Slot, # 12; the 01 primary winding ends at the slot) # 8 with a terminating end line. Actually connect the end lines become a common neutral Terminal 154 at the output shown in star connection leadership example. The second primary winding 152 begins as phase 02 120 0 behind the beginning of phase 01 in slot / 5 and is then in an identical to phase 01 Pattern wrapped only that each slot used corresponding to 1200 from its phase 01 counterpart is removed as seen in the diagram of FIG. The same applies to the third winding 153 as a phase 03 .: It starts in slot # 9 'of the 1200 behind the At the beginning of phase 02 at slot # 5 runs to the slot # 1 (which is repeated in the developed sequence holt is shown) and follows the same phase relationship shift pattern of the other two phases. It's closed Note that the phase 03 winding is also the Phase 0, 120'o advance as required, The Secondary windings 1:55, 156, 157 for the reference trans- formator (ST-1) are with their primary counterparts 151, 152, 153 are in phase and fall with these in the winding arrangement together. Its secondary coil phase 01 (155) starts in the same slot (# 1) like-for the primary winding and follows the same 16 except for the pattern shown in FIG required turns ratio. The same goes for for the secondary coils 156, 157. The secondary windings 155 #, 156 ', 157 # for the formator the second office (ST-2). by 30 ° each time shifted in spatial phase, in both directions as already mentioned. Fig. 17 shows the relative Winding pattern for the secondary windings of one with transformer with twelve slots, the three- has phase reference primary windings. His second Phase 01 winding (155 '): starts in the slot , «29 of the 300 behind the reference start slot j« 1, runs to slot 6, which is 1200 away, to- back to the adjacent slot 3, then to slot / 7, which is 300 away from # 6; then there is a change 180o to slot, instead of # 12, back to the neighboring one / 8, on to slot 1 and back to # 9 to get 01 break up. Secondary winding 155t is phase jö1 . so the arrangement is identical to the secondary winding development (155) of phase 01 of an ST-1 transformer, only that they are spatially by 30o or by a slot Turn-by-turn in the required manner is set. The secondary windings of phases 02 and 03 of the ST-2, namely 156 ', 1571 are similar in stood from 30 @ across from their ST-1 counterparts 156, 157 wrapped, as would be readily apparent to a person skilled in the art will be understandable. Six-channel inverter There are a number of practical advantages to having one larger number of channels in the inverter system. stem of the present invention is used. This is especially important for higher nominal output powers. Of the Output of the transformer of each channel is in Series connection switched. This puts the load on the output transformers are essentially the same Splits. The nominal output voltage is obtained from Addi. tion of the individual voltages from a transformer each channel. The nominal voltage of the controlled silicon The rectifier of the respective square-wave generators is speaking reduced:, practically by a factor n at an n-channel system. Therefore, the economic secure short-circuit ratio elements in each channel be turned. The nominal power of each of the n-output output transformers is close to 1 / n of the required nominal power of the system: The result is a Current multiplication by channel increase, since for a given nominal output voltage with f0 the higher nominal load through the use of garallelatromes in the course proportions and sections: output transform mators is achieved. It is also extremely advantageous to have a corresponding Increase in the number of levels of the output waveform men.-This results in less distortion; result outputs that are filtered to a greater extent can with less complex and lighter filter units. A four-channel inverter (40) supplies - twelve-step waveforms, see Fig. 70. A four-channel Inverter can generate 24-step waveforms. A six-channel inverter provides 36-stage wave forms per period - see Fig. 19. In general, a n-channel inverter cyclic waveforms: with 6n- Stages. The said four-channel system has four output transformers mators, the secondary windings of which one after the other at 0 °, 1509 300, and 45o in spatial phase with theirs respective primary windings are shifted: The time. borrowed phase of their primary windings Multiphase currents are at 0 °, 150, 300 and 450, respectively moved compared to the 00 channel as a reference (ST-1). the first pronounced harmonic in the resulting 24-step waveform are the 23, and the 25th, the are easier to filter than the twelve-step two-channel exit. In addition, the respective four Summing transformers at a given power rating half the nominal power of each of the two canal system. The reverse is double the nominal power possible if all output transformers have the same measure are. The same applies to the square wave generators for these two systems. Fig. 18 shows the six transformers ST-1 to ST-6 and their corresponding output waveforms in one Three-phase six-channel system. These transformers have ben similarly oriented primary windings 171 to 176 with respective three-phase inputs on it E1 to E6, like is shown in Sections A to F. Each- the secondary winding set is in each case in spatial Phase compared to its primary winding set (171-176) successively increasing by 100 in the manner shown shifted: in phase, namely - at 0 0 in the reference trans- formator ST-1; at 10o in ST-2; at 20o in the ST-3; at 30o im ST. * 6; around 40o in the ST-5; and by 50o in the ST-6. as well it is essential that the time phase of the respective Three-phase inputs E1 to E6 on the transformer primary windings 171 to 176 accordingly by 100 each taking is delayed. This results in the cyclical cliché output voltages of the secondary coils e1 bis e6 with the results shown in idealized form in Fig. 18 respective time phase delay occurring verse. postponements. The primary multi-phase inputs E1 to E6 have the right angular waveform as in connection with the two-channel System (40) is described above. The graded each individual channel output waveforms of each transformer ST-1 to ST-6 are the result of the composite elec- tromagnetic influences in these due to the respective spatial phase shifts in their windings, and the corresponding delayed time phase inputs in the manner explained here and as the person skilled in the art now will be readily understandable: it is important to that the output waveforms e29 e3 * e5 and e6 zy- clichéd run beyond 3600 in such a shifting their temporal phase. The so extended Sections are smaller in size and are dashed indicated accordingly at their equilibrium phase beginnings their effective presence in the system. 19 shows the single phase (e) of the summing output waves. shapes for the hexagon, nal inverter. Any positive (+) 1800 half of the periods (e) has 18, levels in the same Way like any negative (-a) half: a total of 36 levels per Period (s) .with fo or 400 Hertz. Fi.g. 19 indicates the six-channel waveform formation by the six each added section or channel waveforms e1 to e6 of Fig. 18, those in the positive (+) half of stepped waveform (s) shown thin construction lines indicate their complex additions (from e1 to e6) an instantaneous but continuous in-time Basis, as is readily understandable to a person skilled in the art. Fig. 20 shows the simple series connection coupling the corresponding phase of each of the six summation trans- formatoren ST - 1 to ST-6o Your circuit is theoretical that for the two-channel system in connection with FIG. 7 9 9 and 10 described similarly. The end line clamp n1 of the secondary coil for e1 of the ST-1 can be the neutral Newspaper n of the system. - The secondary voltages e1 to e6 are connected in such a way that they add up through their respective secondary coils in the direction of their arrows from the start lines to the end lines m2 to m6 in order to form the output e for phase 01. The other phases 02 and 03 are similarly coupled for the three-phase output of FIG. 9 of the two-channel system. More or less than three phases can be used; in the broadest sense, any practical multi-phase training can be used. Such a six-channel inverter system provides a waveform output with the 36-stage formation of relatively less distortion than the two- or four-channel systems. Before filtering out, its harmonic content is only about 3.5% and can easily be filtered down to a very small residual content for the desired f0 output.

The multichannel (n) inverter system of the present invention thus directly provides multistage optimal output waveforms, each period having 6n steps, which are very easy to use in all practical applications with the f, o Fr multiphase output of the system at frequency f0 . The nominal voltage and conductance of each channel is essentially 1 / n of the nominal power of the system. Its output transformers are powerful and effectively isolate the short-circuit ratio square wave generators against adverse actuation during inductive loads. It is also essential that the summing transformers prevent the passage of direct current to the f0 output (44) in the event of a failure in a short circuit ratio section. This will damage the associated with the f. Newspaper Wechseletromeinrichtung prevents the described here Inverter system is stable, robust and effective. from Pole ignition circuit monitored by an electronic clock se keep the inverter channels in their correct Zet phase shifts and deliver the necessary multi-phase multi-current sets. Close monitoring of a-. from a single source enables practical parallel drove a number of inverters of this type In the preferred arrangements, the n channels are one System in temporal and spatial phase in (n-1) equal- before steps within a spread of 60 0 for three- phase embodiments shifted. This allows the use of the rather simplified, on the ring Pole ignition circuit based on the counter principle in as described above, and in a similar manner Way for other arrangements that do not involve three phases turn around. The six-channel three-phase system runs from 0 ° to 500 with five 10 ° steps; the specified square nal three-phase system over ¢ 5o in three 150 steps; and the two-channel three-phase Syatem described above by 30 ° in one step. Systems with a larger number of Channels are for higher powers and / or outputs lower distortion indicated.

Claims (2)

Claims 1. AC power supply, characterized by a plurality of generators, each delivering a multiphase set of shaped alternating signals, each signal set being generated with a predetermined time phase shift between respective opposing signal sets of the generators and at a common rate, and by transformer means in circuit with each generator to generate a composite polyphase output signal set of predetermined shape and at a common rate from the generated signal set. 2, AC power supply, characterized by a plurality of generators, each of which delivers a multiphase set of alternating signals of essentially rectangular waveform, each set of signals being generated with a predetermined time phase shift between respective counter signals of the generators and with a fundamental frequency, and by transformer means in circuit with each generator for generating a composite polyphase output signal set of stepped waveform from the generated polyphase signal set at the fundamental frequency. 3, power supply system according to. Claim 1 or 2, thereby marked that the transformer means have a single separate transformer section for each generator a polyphase primary winding in circuit with theirs have respective generator, the secondary Developments of the transformer technology to achieve of the multiphase output are coupled. 4, power supply system according to claim 19 characterized indicates that the multiphase counter signal sets essentially the same shape as given Time phase shift compared to the other th signal sets, and the transformer means a single polyphase transformer section for each generator, with each transmission corresponding multi-phase primary developments in coupling with its respective has generated polyphase signal set, and the se- secondary windings of the transformer sections for Achieving the multi-phase output signal set are coupled. 5, power supply system according to claim 2, characterized in that indicates that the multiphase counter signal sets rectangular waveform is essentially the same Form in a given time phase shift with respect to above the other signal sets generated, where the transformer means one with each generator coupled individual transformer section assign each transformer section corresponding Has multi-phase primary windings on his adjust respective generated multiphase signal sets.:. chen, and the - secondary windings of the transformer- sections to achieve the composite multiple phase output signal set are coupled. 6. Power supply system according to one of the preceding Claims, characterized in that the secondary windings of the transformer sections multi-phase arranged and in respective phased rows. connection are coupled, 7. Power supply system according to claim 3, characterized in that the secondary windings of the transformer sections are arranged in multiple phases and are in a predetermined spatial phase shift with respect to their respective polyphase primary signals in order to form the composite multi-phase output signal set in a predetermined relationship. B. Power supply system according to claim 4 or 5, characterized in that the secondary windings of the transformer sections are each arranged in multiple phases and in a predetermined spatial phase shift with respect to their respective polyphase primary windings in order to form the composite multi-phase output signal set in symmetrical and predetermined relationship. 9. Power supply system according to claim 2 or any claim related to claim 2, characterized in that the generators are controlled silicon power. have rectifier in successive gate circuit for generating the square-wave alternating signals. 10. Power supply system according to claim 5 or any claim related to claim 5, characterized in that the generators have controlled silicon power rectifiers with a gate circuit in regular sequence for generating the square-wave alternating signals in time phase shifting. 11. Power supply system according to claim 7 or 8, characterized in that the spatial phase shifts successive transformer sections by im substantially the same amounts increase, '(2, power supply system according to claim 11, characterized in that denotes that the space phase shifts are a corresponding signal phase under the transformer total sections are less than 60o. 13- power supply system according to claim 11 'characterized indicates that the relative time phase shift of each generated signal in degrees essentially is exactly as large as the spatial phase shift its corresponding transformer section in Degrees.