CN117712820B - Driving circuit of laser linear power supply and laser - Google Patents
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- CN117712820B CN117712820B CN202410162056.0A CN202410162056A CN117712820B CN 117712820 B CN117712820 B CN 117712820B CN 202410162056 A CN202410162056 A CN 202410162056A CN 117712820 B CN117712820 B CN 117712820B
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Abstract
The invention relates to the technical field of electric elements, and particularly discloses a driving circuit of a laser linear power supply and a laser, wherein the driving circuit of the laser linear power supply comprises an MCU (micro control unit), a direct current power supply unit, a load end current sampling unit and an adjusting circuit, the adjusting circuit comprises n route current control units, n is an integer larger than 1, the direct current power supply unit is connected with each route current control unit, each route current control unit is connected with a DAC (digital-to-analog converter) interface of the MCU and is connected with the load end current sampling unit, the load end current sampling unit is used for collecting real-time current of a laser load, and the MCU respectively adjusts the output current of each linear current control unit according to current data fed back by the load end current sampling unit and combines the output current of each route current control unit to the laser load. The invention can realize large current output, ensure the linearity of the power supply to be adjustable, and has low ripple and stability.
Description
Technical Field
The invention relates to the technical field of semiconductors, in particular to a driving circuit of a laser linear power supply and a laser.
Background
In driving applications of optical devices, it is desirable to provide a control scheme that provides low ripple, constant, finely divided adjustable current. With the application of high-speed high-power lasers, a current control mode which provides larger current, is continuous and stable and has low ripple is required. There are two main forms of application today. The linear direct current power supply utilizes the working principle of an amplifying region of a triode or a MOS tube, is equivalent to a variable resistor, and is connected into a power supply loop in series to adjust the current of the triode or the MOS tube in real time so as to realize constant current control. The other is a switching power supply, namely, a mode of converting direct current into alternating current and then converting the alternating current into direct current, and current is regulated by utilizing inductance energy storage and on-off frequency of a switching tube. The first mode has the characteristics of low ripple and good current regulation linearity, but the output current is smaller, usually about 100mA, and the power consumption of the circuit is larger because the device works in an amplifying region, if the current is required to be increased, the sampling resistance is required to be reduced, but the adjustable range is smaller. The second mode has the advantages of large output current and low circuit power consumption, but because the device works in a switching state, ripple noise of a loop is additionally added besides the ripple noise of the power supply, and generally the ripple wave can reach more than mV level and has the frequency of between 500KHz and 1.5MHz, which is very unfavorable for the transmission signal of the high-speed optical device.
Disclosure of Invention
The invention aims to provide a driving circuit of a laser linear power supply and a laser applying the driving circuit, which realize large current output and ensure the linear adjustable, low ripple and stable output of the power supply.
In order to achieve the above object, the present invention provides the following technical solutions:
The driving circuit of the linear power supply of the laser comprises an MCU, a direct current power supply unit, a load end current sampling unit and an adjusting circuit, wherein the adjusting circuit comprises n route current control units, n is an integer larger than 1, the direct current power supply unit is connected with each route current control unit, each route current control unit is connected with one DAC interface of the MCU and connected with the load end current sampling unit, the load end current sampling unit is used for collecting real-time current of a laser load, the MCU respectively adjusts output current of each linear current control unit according to current data fed back by the load end current sampling unit, and the output current of each route current control unit is combined and output to the laser load.
In the scheme, the direct current power supply unit is utilized to directly provide direct current, low-ripple stable output can be realized, the adjusting circuit consists of multiple paths of linear current control units, the output currents of the linear current control units are combined and output to the laser load, compared with single-path adjustment, larger current output can be realized, linear adjustment can be further refined, the load current is sampled in real time through the load end current sampling unit, and the MCU adjusts the output of the linear current control units according to the real-time sampling current, so that the output control of the adjusting circuit is more accurate.
The direct current power supply unit comprises a first triode, a second operational amplifier, a third resistor, a variable resistor, an eighth resistor and a ninth resistor, wherein the collector electrode of the first triode is connected with a power supply, the base electrode of the first triode is connected with the output end of the second operational amplifier through the third resistor, the positive electrode end of the second operational amplifier is connected with the variable resistor, the negative electrode end of the second operational amplifier is grounded through the ninth resistor and is connected with the emitter electrode of the first triode through the eighth resistor, and the emitter electrode of the first triode is also connected with the linear current control unit.
In the scheme, the voltage of the positive electrode end of the second operational amplifier is stabilized by adjusting the voltage division coefficient of the variable resistor, so that the output voltage of the whole direct current power supply unit is stabilized.
The direct current power supply unit further comprises a first capacitor and a fourth capacitor, one end of the first capacitor is connected with the collector electrode of the first triode, and the other end of the first capacitor is grounded; one end of the fourth capacitor is connected with the positive end of the second operational amplifier, and the other end of the fourth capacitor is grounded.
In the scheme, the alternating current component in the direct current power supply is filtered through the first capacitor and the fourth capacitor, so that the output voltage is more stable, and the ripple is low.
The linear current control unit comprises a first resistor, a second triode, a first operational amplifier, a fourth resistor and a switch tube, wherein the first resistor is connected with an emitter of the first triode, the other end of the first resistor is connected with the emitter of the second triode, a collector of the second triode is connected with the switch tube, the switch tube is connected with the load end current sampling unit, a base of the second triode is connected with an output end of the first operational amplifier through the fourth resistor, a negative electrode end of the first operational amplifier is connected with the emitter of the second triode through the second resistor, and a positive electrode end of the first operational amplifier is connected with a DAC interface of the MCU.
In the scheme, the adjusting circuit is composed of multiple paths of linear current control units, and the linear current control unit circuits which need to be turned on or turned off are selected through the switching tube, so that finer and larger-range linear current control can be realized. For the single-path linear current control unit, the voltage of the positive electrode terminal of the first operational amplifier can be adjusted through the DAC, so that the current flowing into the first resistor can be adjusted, namely the output current of the single-path linear current control unit is adjusted, and finer current adjustment can be realized through configuration selection of the DAC.
The switching tube is a PMOS tube, a source electrode of the PMOS tube is connected with a collector electrode of the second triode, a drain electrode of the PMOS tube is connected with the load end current sampling unit, a grid electrode of the PMOS tube is connected with a control signal, and a tenth resistor is connected between the grid electrode and the drain electrode of the PMOS tube.
In the scheme, the PMOS tube is adopted as the switch tube, so that the implementation mode is simpler.
The linear current control unit also comprises a fifth resistor and a second capacitor, and the fifth resistor and the second capacitor form a low-pass filter circuit which is connected between the MCU and the positive electrode end of the first operational amplifier.
In the scheme, the fifth resistor and the second capacitor form a low-pass filter circuit, so that the voltage of the DAC is more stable after low-pass filtering.
The load end current sampling unit comprises a seventh resistor and a differential amplifier, the output end of the n-line linear current control unit is connected with the laser load through the seventh resistor, the seventh resistor is connected in parallel with the positive electrode end and the negative electrode end of the differential amplifier, and the output end of the differential amplifier is connected with an ADC interface of the MCU.
In the above scheme, the differential amplifier is used for collecting the voltage at two ends of the seventh resistor, and the voltage divided by the resistor is the real-time current of the laser load. I.e. the current sampling implementation is simple and reliable.
The load end current sampling unit also comprises a sixth resistor and a third capacitor, and the sixth resistor and the third capacitor form a low-pass filter circuit which is connected to the output end of the differential amplifier.
In another aspect, the present invention further provides a laser, including a driving circuit of the laser linear power supply according to any one of the above embodiments of the present invention.
The invention has the following beneficial effects:
Low noise and low ripple, which helps to reduce high speed optical device signal noise.
Realize the heavy current output function, can be according to the nimble configuration current output scope of demand.
The current linearity adjustable function is realized and is dynamically adjusted.
The current regulation subdivision function is effectively realized by the multistage combination mode, and the multistage combination type current regulation subdivision device is applicable to various driving requirements.
Drawings
Fig. 1 is a schematic diagram of a driving circuit of a linear power supply of a laser according to an embodiment.
Fig. 2 is an electrical schematic diagram of a dc power supply unit according to an embodiment.
Fig. 3 is an electrical schematic diagram of a linear current control unit in an embodiment.
Fig. 4 is an electrical schematic diagram of a load side current sampling unit according to an embodiment.
Fig. 5 is a circuit diagram used in the test experiment.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. The components of the embodiments of the present invention generally described and illustrated in the figures herein may be arranged and designed in a wide variety of different configurations. Thus, the following detailed description of the embodiments of the invention, as presented in the figures, is not intended to limit the scope of the invention, as claimed, but is merely representative of selected embodiments of the invention. All other embodiments, which can be made by a person skilled in the art without making any inventive effort, are intended to be within the scope of the present invention.
Referring to fig. 1, the driving circuit of the laser linear power supply provided in this embodiment includes an MCU, a dc power supply unit, a load side current sampling unit, and an n-line current control unit, where n is an integer greater than 1. The load end current sampling unit is connected with the optical device laser to collect the current of the laser load. Each route current control unit is connected with one DAC interface of the MCU and connected with the direct current power supply unit and the load end current sampling unit. The MCU feeds back the current data of the load end current sampling units in real time through the ADC interface, adjusts the current output of each linear current control unit through n paths of DACs respectively, and combines and outputs the output currents of the n paths of linear current control units to the laser load so as to realize the function of current combination.
As shown in fig. 2, as an example, the dc power supply unit includes a first triode Q1, a second operational amplifier U2, a first capacitor C1, a third resistor R3, a variable resistor R6, a fourth capacitor C4, an eighth resistor R8, and a ninth resistor R9, where a collector of the first triode Q1 is connected to the power supply VCC and grounded through the first capacitor C1, a base thereof is connected to an output terminal of the second operational amplifier U2 through the third resistor R3, a positive terminal of the second operational amplifier U2 is connected to the variable resistor R6 and grounded through the fourth capacitor C4, a negative terminal of the second operational amplifier U2 is grounded through the ninth resistor R9, and connected to an emitter of the first triode Q1 through the eighth resistor R8, and the emitter of the first triode Q1 is also connected to the linear current control unit.
Assuming that the positive terminal of the second operational amplifier U2 is V1, the negative terminal is V2, the output voltage is Vo, the output voltage of the first transistor Q1 is V3, the collector current of the first transistor Q1 is Icc, the base current is Ibb, and there is icc=βibb, where β is the fixed amplification gain of the first transistor Q1. The size of the Ibb can be adjusted to adjust the size of the Icc. The principle is as follows: v2=r9/(r9+r8) ×v3, assuming that r9/(r9+r8) =1/2, v2=1/2×v3, v1=v2, and thus v1=1/2×v3, that is, v3=2×v1, according to the characteristics of the second operational amplifier U2. By adjusting the voltage division coefficient of the variable resistor R6, stable V1 is obtained, and stable V3 is obtained, for example, V1 is 1.5V, and V3 is 3V. If the voltage of V3 changes when the load of the subsequent stage connected with V3 changes, the stabilizing principle is as follows: when V3 decreases, V2 also decreases, the positive terminal V1 of the second operational amplifier U2 is unchanged, V1 is larger than V2, the output terminal Vo of the second operational amplifier U2 increases, if the emitter voltage drop of the first triode Q1 is V12, ibb= (Vo-V12-V3)/R3, since V12 is fixed, vo increases, V3 decreases, ibb increases, and accordingly Icc increases, corresponding to an increase in current flowing through the load connected to V3, and V3 increases. Similarly, when V3 increases, V2 will be greater than V1, the Vo output by the second operational amplifier U2 decreases, ibb decreases, icc decreases, and V3 decreases.
Through the voltage division feedback loop formed by the second operational amplifier U2 and the first triode Q1, the first triode Q1 works in an equivalent variable resistance region, and V3 can be stably output due to hardware real-time feedback. The voltage stabilizing principle is different from a switching power supply, no alternating current ripple is generated, and the power supply works in a linear adjustment state. That is, the dc power supply unit shown in fig. 2 can provide a stable low-ripple dc current for the load at the subsequent stage, and the total output power of the dc power supply unit is equal to the sum of the load power and the power of each linear current control unit.
The structure and principle of the n-way current control unit are the same, and therefore only one of them will be described here. As shown in fig. 3, as an example, the linear current control unit includes a first resistor R1, a second resistor R2, a second triode Q2, a first operational amplifier U1, a fifth resistor R5, a second capacitor C2, a fourth resistor R4, a tenth resistor R19, and a PMOS transistor Q5, where the first resistor R1 is connected to an emitter of the first triode Q1, another end of the first resistor R1 is connected to an emitter of the second triode Q2, a collector of the second triode Q2 is connected to a source of the PMOS transistor Q5, a drain of the PMOS transistor Q5 is connected to the load current sampling unit, a gate of the PMOS transistor Q5 receives a control signal CTL1, and a tenth resistor R19 is connected between the gate and the drain of the PMOS transistor Q5, a base of the second triode Q2 is connected to an output terminal of the first operational amplifier U1 through the fourth resistor R4, a negative terminal of the first operational amplifier U1 is connected to the emitter of the second triode Q2 through the second resistor R2, and a positive terminal of the first operational amplifier U1 is connected to the ground through the second capacitor C2 and is connected to a DAC interface of the fifth resistor R5.
When CTL1 is high, the PMOS tube Q5 is closed, and no current is output; when CTL1 is low, PMOS tube Q5 is turned on, and the circuit outputs normally. Assuming that the positive terminal of the first operational amplifier U1 is V4, the negative terminal is V5, the output terminal is V6, the controllable current flowing through the loop is I1, the base current of the second triode Q2 is Ib, the collector current is Ic, and ic=i1, ic=βib, β is the fixed amplification gain of the second triode Q2, so that the current of Ib is adjusted, i.e. the current of I1 can be adjusted. From the foregoing, since the voltage of V3 is stable, i1= (V3-V5)/R1, R1 is the loop current adjusting resistor, and the power thereof is larger than the power corresponding to the maximum current of the loop current. Since V3 and R1 are both fixed, the current I1 can be adjusted by adjusting the magnitude of V5. According to the characteristics of the first operational amplifier U1, v5=v4, v4=dac 1. The fifth resistor R5 and the second capacitor C2 form a low-pass filter circuit, so that the voltage of the DAC1 is more stable after low-pass filtering. Thus, the voltage of DAC1, i.e., the voltage of V5, is adjusted. When v5=v3, i1=0, no current is generated by the circuit, and when V5 is smaller than V3, i1= (V3-V5)/R1, a current is generated. For example v3=2.5v, r=10Ω, v5=2.4v, i1= (2.5-2.4)/10, i.e. 10mA, if v5=2.3V, i1=20ma. Thus, a change in V5 of 0.1V corresponds to a change in current of 10mA, i.e., 1mV corresponds to a change in current of 0.1 mA. If the DAC of the MCU is 12 bits, the reference voltage is 2.5V, namely the count value corresponding to the 12 bits is 4096, therefore, the minimum output unit is equal to 2.5/4096V, namely 0.61mV, and the corresponding current change is less than 0.1mA because of 0.61mV <1mV, namely the current regulation stepping mode of 0.1mA can be realized by the DAC of the 12 bits. The maximum adjustable current of the circuit depends on the gain of the second triode Q2, and the circuit can realize the current output function of about 150mA at maximum.
The current stabilization principle is as follows: when the load changes, if the I1 current decreases, the voltage across the first resistor R1 decreases, the voltage V5 of the V3 voltage reduced by the first resistor R1 increases, and the output terminal V6 decreases because the positive terminal V4 of the first operational amplifier U1 is unchanged and the negative terminal V5 increases. Assuming that the emitter voltage of the second transistor Q2 is V21, ib= (V5-V21-V6)/R4, V5 rises, V6 decreases, V21 does not change, R4 does not change, and therefore Ib will rise, ic rises, i.e. I1 rises. Similarly, when the current I1 increases, V5 decreases, V6 increases, ib decreases, and the I1 current decreases.
The output current of the linear current control unit is kept constant by a linear adjusting loop formed by the first operational amplifier U1 and the second triode Q2. For example, as shown in fig. 3, the PMOS transistors Q5, Q6, Q7 are controlled by CTLx (x is 1 or 2 or 3), when CTLx is low, the corresponding channels are open, and when CTLx is high, the corresponding channels are closed. The maximum current output of the linear current control unit circuit depends on the amplification gain of the transistor Qn (Q2, Q3, Q4 in the illustrated example) and the current setting resistance Rn (R1, R7, R14 in the illustrated example).
According to node current law, the current flowing into the node is equal to the current flowing out of the node, so i=i1+i2+i3 In the example shown In fig. 3, and i=i1+i2+ … +in extends to the n-route current control unit. Each linear current control cell circuit can obtain finer current subdivision settings by setting appropriate Rn (R1, R7, R14 in the figure). For example, when the load needs 300mA current, i1=100 mA, i2=100 mA and i3=100 mA can be set respectively, and at this time, dac1=dac2=dac3 can be used; i1=50ma, i2=125ma, i3=125ma can be set, and DAC 2=dac 3 can be set at this time, and DAC1 can be calculated according to actual parameters.
To verify the feasibility of the current combining mode of each routable current control unit (which can be understood as a channel), tests were performed based on the circuit shown in fig. 5, and the test results are shown in the following table:
It can be seen from the above table that the channel-merged current mode is feasible, conforming to node current law. Meanwhile, a certain error exists between the actual current and the calculated current, but the error can be corrected through current sampling feedback, so that the control precision can be ensured.
Since the unit circuits are integrated, the power consumption of the regulator circuit is allocated to each unit circuit, and it is not necessary to select Rn (R1, R7, R14 in the drawing) to be larger. If only one-way regulation is used, if the loop current needs 300mA, the power P of Rn needs P >300mA x Rn. According to the principle of u=i×r, if the value of Rn is reduced to reduce power consumption, the circuit current is subdivided insufficiently. For example, i= (V3-V5)/R1, let v3=2.5v, r1=10Ω, i=10ma when v5=2.4v, and i=20ma when v5=2.3v, i.e. 0.1V corresponds to a current change of 10 mA; if r1=5Ω, i=20ma when v5=2.4v, and i=40ma when v5=2.3v, i.e., 0.1V corresponds to a current change of 20 mA. It can be seen that if the first resistor R1 becomes smaller, the step subdivision of the current setting becomes larger, and the current subdivision setting requirement of the high-power laser is not satisfied. Therefore, the circuit scheme of the regulating circuit is formed by combining the multi-path linear current control unit circuits, so that the requirement of large current output is realized, and the requirements of low ripple and current subdivision are also ensured.
In the example shown in fig. 3, PMOS transistors are used to realize the connection of the circuits of the linear current control units, and other switching transistors, such as NMOS transistors, may be used.
As shown in fig. 4, as an example, the load-side current sampling unit includes a seventh resistor R17, a differential amplifier U5, a sixth resistor R13, and a third capacitor C11, the output end of the n-line linear current control unit (PMOS transistors Q5, Q6, Q7 in the example shown in fig. 3) is connected to the laser load LD1 through the seventh resistor R17, the seventh resistor R17 is connected in parallel to the positive and negative terminals of the differential amplifier U5, the output end of the differential amplifier U5 is connected to an ADC interface of the MCU through the sixth resistor R13, and the sixth resistor R13 and the third capacitor C11 form a low-pass filter circuit.
The current flowing through the laser load LD1 is equal to the voltage drop across the seventh resistor R17 divided by the resistance of the seventh resistor R17. I= (V13-V14)/R17, the differential amplifier U5 is used for detecting the voltages at two ends of the seventh resistor R17, that is, the MCU collects the voltage values of the ADC, so as to calculate the current of the current loop. The purpose of the load end current sampling unit circuit is to detect the actual current value of the current loop. Because of device errors and DAC deviation in the adjusting circuit, the current value output by the circuit setting may have deviation, and according to the actual current feedback value of the load end current sampling unit circuit, the MCU finely adjusts the setting value of each linear current control unit circuit in real time so as to realize current real-time compensation and reach the setting value.
The foregoing is merely illustrative of the present invention, and the present invention is not limited thereto, and any person skilled in the art will readily recognize that variations or substitutions are within the scope of the present invention.
Claims (7)
1. The driving circuit of the linear power supply of the laser is characterized by comprising an MCU, a direct current power supply unit, a load end current sampling unit and an adjusting circuit, wherein the adjusting circuit comprises n route current control units, n is an integer larger than 1, the direct current power supply unit is connected with each route current control unit, each route current control unit is connected with one DAC interface of the MCU and is connected with the load end current sampling unit, the load end current sampling unit is used for collecting real-time current of the laser load, the MCU respectively adjusts output current of each linear current control unit according to current data fed back by the load end current sampling unit, and the output current of each route current control unit is combined and output to the laser load;
The linear current control unit comprises a first resistor, a second triode, a first operational amplifier, a fourth resistor and a switch tube, wherein the first resistor is connected with an emitter of the first triode, the other end of the first resistor is connected with the emitter of the second triode, a collector of the second triode is connected with the switch tube, the switch tube is connected with the load end current sampling unit, a base of the second triode is connected with an output end of the first operational amplifier through the fourth resistor, a negative end of the first operational amplifier is connected with the emitter of the second triode through the second resistor, and a positive end of the first operational amplifier is connected with a DAC interface of the MCU;
The load end current sampling unit comprises a seventh resistor and a differential amplifier, the output end of the n-line linear current control unit is connected with the laser load through the seventh resistor, the seventh resistor is connected in parallel with the positive electrode end and the negative electrode end of the differential amplifier, and the output end of the differential amplifier is connected with an ADC interface of the MCU.
2. The driving circuit of a linear power supply of a laser according to claim 1, wherein the dc power supply unit comprises a first triode, a second operational amplifier, a third resistor, a variable resistor, an eighth resistor and a ninth resistor, the collector of the first triode is connected to the power supply, the base of the first triode is connected to the output end of the second operational amplifier through the third resistor, the positive end of the second operational amplifier is connected to the variable resistor, the negative end of the second operational amplifier is grounded through the ninth resistor, and is connected to the emitter of the first triode through the eighth resistor, and the emitter of the first triode is also connected to the linear current control unit.
3. The driving circuit of a linear power supply of a laser according to claim 2, wherein the dc power supply unit further comprises a first capacitor and a fourth capacitor, one end of the first capacitor is connected to the collector of the first triode, and the other end is grounded; one end of the fourth capacitor is connected with the positive end of the second operational amplifier, and the other end of the fourth capacitor is grounded.
4. The driving circuit of the linear power supply of the laser according to claim 1, wherein the switching tube is a PMOS tube, a source electrode of the PMOS tube is connected with a collector electrode of the second triode, a drain electrode of the PMOS tube is connected with the load end current sampling unit, a gate electrode of the PMOS tube is connected with a control signal, and a tenth resistor is connected between the gate electrode and the drain electrode of the PMOS tube.
5. The driving circuit of claim 1, wherein the linear current control unit further comprises a fifth resistor and a second capacitor, the fifth resistor and the second capacitor forming a low-pass filter circuit connected between the MCU and the positive terminal of the first operational amplifier.
6. The driving circuit of a linear power supply of claim 1, wherein the load current sampling unit further comprises a sixth resistor and a third capacitor, and the sixth resistor and the third capacitor form a low-pass filter circuit connected to the output terminal of the differential amplifier.
7. A laser comprising a drive circuit for a laser linear power supply according to any one of claims 1 to 6.
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