CN114900401A - DFMA-PONs-oriented channel interference elimination method and device - Google Patents
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Abstract
The invention discloses a DFMA-PONs-oriented channel interference elimination method and a DFMA-PONs-oriented channel interference elimination device, which comprise the following steps: in a transmission system, a sending end sends a known training sequence, and a receiving end carries out filtering training by using a system inverse identification adaptive channel estimation algorithm so as to obtain an optimal filtering solution of an inverse system of a system transmission channel; at the transmitting end, the determined inverse system impulse response and the digital orthogonal shaping filter are cascaded into a new digital filter on a subcarrier band. Compared with the traditional digital filtering multiple access passive optical network, the invention utilizes the digital orthogonal shaping filter and the inverse system cascade of the transmission channel to form a new digital shaping filter, thereby not only solving the problem of channel orthogonality damage caused by a non-flat system transfer function in an actual transmission system, but also having simple construction of a communication system and easy realization of hardware.
Description
Technical Field
The invention belongs to the technical field of optical communication, and particularly relates to a channel interference elimination method and device for a digital filtering multiple access passive optical network.
Background
In recent years, with the explosive growth of the internet of things industry, the bandwidth requirement is continuously increased, however, the former network tends to support the traffic mode mainly based on static state, but the static service providing mode cannot meet the dynamic, reconfigurable and flexible interconnection requirements of the emerging digital service network. In order to realize a highly dynamic service mode and significantly improve network reconfigurability, flexibility and elasticity, a Digital Filter Multiple Access (DFMA) technology is widely researched and applied to Passive Optical Networks (PONs).
The DFMA-PONs utilizes a centralized control of a Software Defined Network (SDN) and a dynamic Software reconfigurable Digital orthogonal filter bank based on Digital Signal Processing (DSP) to realize multiplexing and demultiplexing of channels. The DFMA-PONs not only have good backward compatibility, but also have great potential in supporting future cloud access networks.
However, the system performance of DFMA-PONs is highly dependent on the preservation of the spectrally overlapping channel orthogonality, which depends on the linear transmission of the optical signal, as well as the effects of device and channel frequency response. In practical transmission systems, a deterioration of the channel orthogonality based on digital filtering is inevitable due to non-linear effects that the signal may encounter during generation, transmission, routing, aggregation and detection etc.
To mitigate Cross Channel Interference (CCI) in modern communication systems, various DSP-based techniques have been proposed. These techniques fall broadly into two categories: indirect Interference Cancellation (IIC) and Direct Interference Cancellation (DIC) techniques. Maximum Likelihood (ML) detection is a representative one of the IIC techniques, but since the DSP complexity of most of the IIC techniques grows exponentially with the number of users, it is not feasible to use such techniques in DFMA-PONs that accommodate a large number of Optical Network Units (ONUs). Similarly, DIC techniques can produce relatively high delays and the number of iterations required to achieve acceptable performance accuracy is relatively large, and thus these drawbacks also greatly limit the applicability of such techniques to DFMA-PONs.
Disclosure of Invention
In view of this, the present invention provides a method and an apparatus for channel interference cancellation for DFMA-PONs, wherein a transmission system thereof can effectively alleviate CCI effect and has the characteristics of low DSP complexity, low time delay, low cost, etc.
In order to achieve the purpose, the technical scheme adopted by the invention is a DFMA-PONs-oriented channel interference elimination device, at a sending end, a modulation signal is subjected to K times of upsampling by an upsampling unit, then a digital orthogonal shaping filter is used for filtering the signal, channel aggregation is carried out in an electric domain, the aggregated signal passes through an inverse system and a digital-to-analog converter in sequence, and an output electric signal is modulated onto an optical carrier wave by an electro-optical conversion unit.
At a receiving end, the signal is converted into an electric signal in a photoelectric conversion unit, then the signal is digitized through an analog-to-digital converter, the digitized signal is input into a digital orthogonal matched filter, then K-time domain down-sampling is carried out in a down-sampling unit, and finally the signal is demodulated in a demodulation unit.
On the basis of the technical scheme, the inverse system comprises a digital-to-analog converter DAC, an analog-to-digital converter ADC, an electro-optical converter E/O, an electro-optical converter O/E and an optical fiber link, a known training sequence sequentially passes through the digital-to-analog converter DAC, the electro-optical converter E/O, a transmission channel, the electro-optical converter O/E and the analog-to-digital converter ADC, an output sequence passes through a self-adaptive channel estimation algorithm, and the coefficient of an iterative self-adaptive filter is continuously updated, so that the impulse response w of the inverse system can be obtained -1 (t) of (d). Utilizing a self-adaptive filtering estimation algorithm to perform inverse identification on a system transmission channel; the system takes the training sequence as an ideal signal, carries out self-adaptive filtering training on the signal passing through an unknown system, and the filtering coefficient is iterated rapidly, so as to finally obtain the optimal filtering solution of the inverse system.
On the basis of the technical scheme, the coefficients of the adaptive filter are continuously updated iteratively by using an error function e (n) between a training sequence d (n) and an output signal y (n) of the adaptive filter.
On the basis of the technical scheme, the numbers are orthogonalShaping filter and estimated inverse system impulse response w -1 (t) cascading to obtain a new digital shaping filter.
On the basis of the technical scheme, different channel estimation algorithms are selected according to different signal modulation formats: for an on-off keying OOK modulation format, a channel estimation algorithm based on minimum mean square error MMSE is utilized; for the quadrature amplitude modulation QAM modulation format, a channel estimation algorithm based on least mean square LMS is utilized; for the orthogonal frequency division multiplexing OFDM modulation format, a least mean square LMS-based channel estimation algorithm or a least square LS-based channel estimation algorithm is utilized. According to different signal modulation formats, the channel estimation can be independent from the digital filter, and flexible selection can be performed on the whole channel or the sub-channel.
On the basis of the technical scheme, a channel estimation module is designed for a QAM (quadrature amplitude modulation) modulation format of a single carrier by utilizing a channel estimation algorithm based on least mean square LMS (least mean square); the channel estimation module based on the least mean square LMS algorithm has flexibility in adjusting the step size factor, and ensures that the system has high convergence speed and small steady-state detuning in a stable environment.
The invention also provides a DFMA-PONs-oriented channel interference elimination method, which comprises the following steps:
step 1: estimating the inverse system impulse response w of a system transmission channel -1 (t), the sending end sends a known training sequence, the known training sequence passes through a digital-to-analog converter (DAC), and an electric signal output by the DAC is injected into an optical fiber link through light intensity modulation; at a receiving end, the electric signal after photoelectric conversion is digitized by an analog-to-digital converter (ADC), the output digital signal is subjected to a self-adaptive channel estimation algorithm, and then the coefficient of an iterative self-adaptive filter is continuously updated, so that the inverse system impulse response w of a system transmission channel can be obtained -1 (t)。
Step 2: obtaining the inverse system impulse response w according to the estimation -1 (t) at the transmitting end, the digital quadrature shaping filter and the estimated inverse system impulse response w are combined -1 (t) cascading to obtain a new digital shaping filter; different users select different new digital shaping filters to sample the K times of the signalsFiltering the signals, modulating the signals to optical carriers with the same central frequency through a digital-to-analog conversion DAC and an optical intensity modulation IM, and finally performing channel aggregation on the signals sent by all users through a passive optical coupler OC; at a receiving end, an electric signal after photoelectric conversion is digitized through an analog-to-digital converter (ADC), and then is input into a plurality of parallel digital orthogonal matched filters to realize channel separation, then a sent coded signal is obtained through time domain down-sampling, and finally signal demodulation is utilized to finish signal recovery.
On the basis of the technical scheme, the digital orthogonal shaping filter and the inverse system impulse response w obtained by estimation -1 (t) cascading to obtain a new digital shaping filter having an impulse response of:
h I (t)、h Q (t) denotes the I and Q filter impulse responses, g I (t)、g Q (t) denotes the I and Q filter impulse responses, respectively, based on a Hilbert-pair, w -1 (t) is the impulse response of the inverse system, p (t) is the root-mean-square raised cosine pulse, f c T represents time, which is the center frequency of the digital quadrature filter.
On the basis of the above technical scheme, at the receiving end, the final output through the in-phase matched filter is:
the final output through the quadrature matched filter is:
d I (t)、d Q (t) represents the inputs of the in-phase channel and the quadrature channel of the transmitting end, respectively, h I (t)、h Q (t) respectively representing the impulse response of the I path and the Q path of the digital filter at the sending end, w (t) is the impulse response of a system channel, m I (t)、m Q (t) is the impulse response of the digital quadrature filter at the receiving end;
h I (t)、h Q (t) is the impulse response w of the digital quadrature filter and inverse system -1 (t) results from the cascade, thus:
namely:
the invention has the following beneficial effects:
(1) compared with IIC type technology, the method can meet the requirement of relieving the CCI effect without repeated CCIC iteration; meanwhile, compared with the existing DIC class technology, the method has lower DSP complexity, and particularly has remarkable performance improvement on DFMA-PONs accommodating a large number of ONU.
(2) In the invention, the DSP operation of the system does not depend on the adopted signal modulation format; moreover, the system performance does not depend on the initial system operation condition, the compatibility of the invention and DFMA-PONs is ensured, and the reconfigurability, flexibility and elasticity of the DFMA-PONs are further improved.
Drawings
FIG. 1 is a schematic chain diagram of the present invention for estimating the impulse response of an inverse system;
FIG. 2 is a block diagram of an adaptive filtering iteration employed by the design channel estimation module of the present invention;
FIG. 3 is a block diagram of the data transmission steps for the in-phase and quadrature channels on the same subband in the system of the present invention;
fig. 4 is a block diagram of the sending end of the DFMA-PONs oriented channel interference cancellation system for estimating the channel to act on the sub-channels according to the present invention;
fig. 5 is a block diagram of the sending end of the DFMA-PONs-oriented channel interference cancellation system for channel estimation acting on the entire channel according to the present invention;
fig. 6 is a block diagram of a receiving end of a DFMA-PONs-oriented channel interference cancellation system according to the present invention.
Detailed Description
The invention is described in further detail below with reference to the figures and the detailed description.
The design idea of the invention is to provide a DFMA-PONs-oriented channel interference elimination method.
Wherein the inverse system impulse response w of the system transmission channel -1 (t) the determining link is shown in fig. 1, and includes sending a training sequence 110 at the sending end, and injecting the electrical signal output by the DAC into an optical fiber link 140 through an electro-optical conversion unit 130 via a digital-to-analog converter 120; at the receiving end, the optical signal is input into the photoelectric conversion unit 150 and converted into an electrical signal, the electrical signal is digitized by the analog-to-digital converter 160, the output digital signal is subjected to the adaptive filter I170, the adaptive filter coefficient is continuously updated and iterated, and the inverse system impulse response w of the system transmission channel can be obtained -1 (t)。
Further, the inverse system impulse response w -1 And (t) physical transmission characteristics such as a digital-to-analog converter (DAC), an analog-to-digital converter (ADC), an electro-optical converter (E/O), an electro-optical converter (O/E) and an optical fiber link are included.
Referring to fig. 2, which is a block diagram of an adaptive filtering iteration adopted in designing a channel estimation module, first, a training sequence d (n)210 sequentially passes through a system transmission channel w (t)220 and an adaptive filtering iterationIn the second stage 230, an adaptive filter output signal y (n) is obtained. Continuously iteratively updating the adaptive filter coefficient by using an error function e (n) between a training sequence d (n) and an output signal y (n) of the adaptive filter, and finally obtaining an inverse system impulse response w of a system transmission channel -1 (t)。
FIG. 3 is a block diagram of the data transmission steps of the in-phase and quadrature channels on the same subband in the system of the present invention, where the modulation signal of the in-phase channel is d at the transmitting end I (t)310, the modulation signal of the orthogonal channel is d Q (t)350, the two modulated signals are up-sampled by a factor of K in the up-sampling unit 320, respectively, after which the signal of the in-phase branch is passed through the in-phase filter g in the digital quadrature shaping filter unit 330 I (t), the signal of the quadrature branch is passed through a quadrature phase filter g in a digital quadrature shaping filter unit 360 Q (t) following the impulse response w of the two signals through the inverse system channel, respectively -1 (t)340 and system channels w (t) 370; at the receiving end, the signals after channel aggregation pass through the digital quadrature in-phase matched filter unit 380 and the digital quadrature phase matched filter unit 3110, and then the two signals are K-times down-sampled at the down-sampling unit 390 to obtain the in-phase branch received signal d' I (t)3100 and quadrature branch reception signal d' Q (t)3120。
The concrete expression of the scheme is as follows:
the final output of the receiving end through the in-phase matched filter meets the following requirements:
the final output through the quadrature matched filter satisfies:
d I (t)、d Q (t) represents the inputs of the in-phase channel and the quadrature channel of the transmitting end, respectively, h I (t)、h Q (t) is divided intoRespectively representing the impulse response of an I path and a Q path of a digital shaping filter at a sending end, w (t) representing the impulse response of a system channel, m I (t)、m Q And (t) respectively represent the impulse responses of the digital orthogonal matched filters at the receiving end.
h I (t)、h Q (t) is the impulse response w of the digital quadrature shaping filter and the inverse system -1 (t) results from the cascade, thus:
namely:
g I (t)、g Q (t) denotes the I and Q filter impulse responses, respectively, based on a hilbert pair.
As shown in fig. 4, which is a block diagram of the sending end of the DFMA-PONs-oriented channel interference cancellation system for applying channel estimation to sub-channels, modulated signals 410 of different users are up-sampled by K times by using an up-sampling unit 320, then the signals are filtered by using a digital filter 420, then the signals are sequentially passed through a digital-to-analog conversion unit 120 and an electro-optical conversion unit 130, the signals are modulated onto optical carriers of the same center frequency, and finally, the signals sent by all users are subjected to channel aggregation in an optical coupling unit 430.
Further, the digital quadrature shaping filter bandwidth is equal to the symbol rate R _ s of the modulated signal; the selection range of the center frequency F _ c of the digital orthogonal filter depends on the symbol rate R _ s and the DAC sampling rate F s_DAC Is that is[R_s/2,(F s_DAC -R_s)/2]。
Further, the impulse response w of the system is formed by using a digital quadrature shaping filter and an inverse system -1 (t) cascading to obtain a new digital filter, the impulse response of which is:
h I (t)、h Q (t) denotes the I and Q filter impulse responses, w, respectively -1 (t) the impulse response of the inverse system, g I (t)、g Q (t) respectively representing the impulse responses of the I and Q filters based on Hilbert pairs, p (t) being the root-mean-square raised cosine pulse, f c T represents time, which is the center frequency of the digital quadrature filter.
As shown in fig. 5, which is a block diagram of the sending end of the DFMA-PONs-oriented channel interference cancellation system for estimating the channel to act on the entire channel, different users 510 perform K times up-sampling by using an up-sampling unit 320, then filter the signal by using a digital orthogonal shaping filter 520, then perform channel aggregation in the electrical domain, the aggregated signal passes through an inverse system 530 and a digital-to-analog converter 120 in sequence, and the output electrical signal is modulated onto an optical carrier by an electro-optical conversion unit 130.
As shown in fig. 6, a receiving end step diagram of a DFMA-PONs-oriented channel interference cancellation system is shown, at the receiving end, a signal is converted into an electrical signal in an optical-to-electrical conversion unit 150, then the signal is digitized by an analog-to-digital converter 160, the digitized signal is input into a digital orthogonal matched filter bank 610, then K-time domain down-sampling is performed in a down-sampling unit 390, and finally a demodulated signal 630 is obtained by a demodulation unit 620.
Further, at the receiving end, the impulse response of the digital orthogonal matched filter is the time domain inversion of the impulse response of the digital orthogonal shaping filter at the sending end, that is, the following conditions are satisfied:
m I (t)＝g I (-t)
m Q (t)＝g Q (-t)
g I (t)、g Q (t) denotes the I and Q filter impulse responses, respectively, based on a hilbert pair.
The above description is only a preferred embodiment of the present invention, and it should be noted that several modifications and variations can be made in the actual implementation without departing from the spirit of the method and the core device of the present invention.
Those not described in detail in this specification are within the knowledge of those skilled in the art.
Claims (8)
1. A DFMA-PONs-oriented channel interference cancellation apparatus, characterized by: at a sending end, modulating signals are subjected to K times of upsampling by an upsampling unit, then the signals are filtered by a digital orthogonal shaping filter, then channel aggregation is carried out in an electric domain, the aggregated signals sequentially pass through an inverse system and a digital-to-analog converter, and output electric signals are modulated onto optical carriers through an electro-optical conversion unit;
at a receiving end, the signal is converted into an electric signal in a photoelectric conversion unit, then the signal is digitized through an analog-to-digital converter, the digitized signal is input into a digital orthogonal matched filter, then K-time domain down-sampling is carried out in a down-sampling unit, and finally the signal is demodulated in a demodulation unit.
2. The apparatus of claim 1, wherein the DFMA-PONs-oriented channel interference cancellation apparatus comprises: the inverse system comprises a digital-to-analog converter DAC, an analog-to-digital converter ADC, an electro-optical converter E/O, an electro-optical converter O/E and an optical fiber link, a known training sequence sequentially passes through the digital-to-analog converter DAC, the electro-optical converter E/O, a transmission channel, the electro-optical converter O/E and the analog-to-digital converter ADC, an output sequence passes through an adaptive channel estimation algorithm, and the coefficient of an iterative adaptive filter is continuously updated, so that the impulse response w of the inverse system can be obtained -1 (t)。
3. The apparatus of claim 2, wherein the DFMA-PONs-oriented channel interference cancellation apparatus comprises: the adaptive filter coefficients are updated iteratively over time using an error function e (n) between the training sequence d (n) and the adaptive filter output signal y (n).
4. The apparatus for eliminating channel interference towards DFMA-PONs of claim 2 or 3, wherein: the digital orthogonal shaping filter and the estimated inverse system impulse response w are used -1 (t) cascading to obtain a new digital shaping filter.
5. The apparatus of claim 4, wherein the DFMA-PONs-oriented channel interference cancellation apparatus comprises: selecting different channel estimation algorithms according to different signal modulation formats: for an on-off keying OOK modulation format, a channel estimation algorithm based on minimum mean square error MMSE is utilized; for the quadrature amplitude modulation QAM modulation format, a channel estimation algorithm based on least mean square LMS is utilized; for the orthogonal frequency division multiplexing OFDM modulation format, a least mean square LMS-based channel estimation algorithm or a least square LS-based channel estimation algorithm is utilized.
6. A DFMA-PONs-oriented channel interference elimination method is characterized by comprising the following steps:
step 1: estimating the inverse system impulse response w of a system transmission channel -1 (t), the sending end sends a known training sequence, the known training sequence passes through a digital-to-analog converter (DAC), and an electric signal output by the DAC is injected into an optical fiber link through light intensity modulation; at a receiving end, the electric signal after photoelectric conversion is digitized by an analog-to-digital converter (ADC), the output digital signal is subjected to a self-adaptive channel estimation algorithm, and then the coefficient of an iterative self-adaptive filter is continuously updated, so that the inverse system impulse response w of a system transmission channel can be obtained -1 (t)；
Step 2: obtaining the inverse system impulse response w according to the estimation -1 (t) at the transmitting end, applying a digital quadrature shaping filter to the estimateThe obtained pulse response w of the inverse system -1 (t) cascading to obtain a new digital shaping filter; different users select different new digital forming filters to filter the signals sampled by the K times, then the signals are modulated to optical carriers with the same central frequency through digital-to-analog conversion DAC and light intensity modulation IM, and finally the signals sent by all the users are subjected to channel aggregation through a passive optical coupler OC; at a receiving end, an electric signal after photoelectric conversion is digitized through an analog-to-digital converter (ADC), and then is input into a plurality of parallel digital orthogonal matched filters to realize channel separation, then a sent coded signal is obtained through time domain down-sampling, and finally signal demodulation is utilized to finish signal recovery.
7. The method of claim 6, wherein the DFMA-PONs-oriented channel interference cancellation method comprises: the digital quadrature shaping filter and the estimated inverse system impulse response w -1 (t) cascading to obtain a new digital shaping filter, wherein the impulse response of the filter is as follows:
h I (t)、h Q (t) denotes the I and Q filter impulse responses, g I (t)、g Q (t) denotes the I and Q filter impulse responses, respectively, based on Hilbert-pairs, w -1 (t) is the impulse response of the inverse system, p (t) is the root-mean-square raised cosine pulse, f c T represents time, which is the center frequency of the digital quadrature filter.
8. The method of claim 6, wherein the DFMA-PONs-oriented channel interference cancellation method comprises: at the receiving end, the final output through the in-phase matched filter is:
the final output through the quadrature matched filter is:
d I (t)、d Q (t) represents the inputs of the in-phase channel and the quadrature channel of the transmitting end, respectively, h I (t)、h Q (t) respectively representing the impulse response of the I path and the Q path of the digital filter at the sending end, w (t) is the impulse response of a system channel, m I (t)、m Q (t) is the impulse response of the digital quadrature filter at the receiving end;
h I (t)、h Q (t) is the impulse response w of the digital quadrature filter and inverse system -1 (t) results from the cascade, thus:
namely:
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