CN114759796A - Controller of active clamping flyback conversion circuit, power supply module and electronic equipment - Google Patents

Controller of active clamping flyback conversion circuit, power supply module and electronic equipment Download PDF

Info

Publication number
CN114759796A
CN114759796A CN202210374393.7A CN202210374393A CN114759796A CN 114759796 A CN114759796 A CN 114759796A CN 202210374393 A CN202210374393 A CN 202210374393A CN 114759796 A CN114759796 A CN 114759796A
Authority
CN
China
Prior art keywords
circuit
controller
voltage
output voltage
capacitor
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
CN202210374393.7A
Other languages
Chinese (zh)
Inventor
孙程豪
伍梁
戴宝磊
单浩仁
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
Shanghai Huawei Digital Energy Technology Co ltd
Original Assignee
Shanghai Huawei Digital Energy Technology Co ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Shanghai Huawei Digital Energy Technology Co ltd filed Critical Shanghai Huawei Digital Energy Technology Co ltd
Priority to CN202210374393.7A priority Critical patent/CN114759796A/en
Publication of CN114759796A publication Critical patent/CN114759796A/en
Priority to PCT/CN2022/140116 priority patent/WO2023197660A1/en
Pending legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/32—Means for protecting converters other than automatic disconnection
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters

Abstract

The application provides a controller, power module and electronic equipment of active clamper flyback conversion circuit, the controller can be after active clamper flyback conversion circuit operates in pause operating condition, through the resonance capacitor discharge of control active clamper flyback conversion circuit, make the voltage value of power circuit's output voltage be higher than the low voltage protection's of controller preset voltage value to avoid the controller to restart because of low voltage protection, and improved the stability of the power module and the electronic equipment that active clamper flyback conversion circuit belongs to. And the controller can not increase the ripple of the output voltage of the active clamping flyback conversion circuit when controlling the discharge of the resonant capacitor, and can not introduce noise from an input power supply.

Description

Controller of active clamping flyback conversion circuit, power supply module and electronic equipment
Technical Field
The present application relates to power supply technologies, and in particular, to a controller for Active Clamp Flyback (ACF), and a power module and an electronic device using the same.
Background
Conventional electronic devices or power modules generally include asymmetric half-bridge (AHB) dc conversion circuits and controllers, such as Active Clamp Flyback (ACF) dc conversion circuits. The dc conversion circuit generally includes a half-bridge circuit, a transformer, and a rectifier circuit. A primary winding circuit of the transformer receives input voltage of an input power supply through a half-bridge circuit, and a secondary winding circuit is used for providing output voltage to supply power to a load. The transformer further comprises an auxiliary winding circuit for supplying power to the power circuit of the controller. When the power module is activated, the power circuit of the controller is generally powered by the input voltage of the input power source. When the power supply module operates, the auxiliary winding circuit of the transformer supplies power to the power supply circuit of the controller. Therefore, the operating state of the dc conversion circuit may affect the power supply stability of the power circuit of the controller, and further affect the stability of the power module and the electronic device where the controller is located.
Disclosure of Invention
The application provides a controller of an active clamp flyback conversion circuit, a power supply module and electronic equipment, which are used for solving the technical problem that the stability of the power supply circuit of the controller, the power supply module where the controller is located and the electronic equipment is influenced by the operation state of direct current conversion circuits such as the active clamp flyback conversion circuit.
Taking a dc conversion circuit as an active clamp flyback conversion circuit as an example, a first aspect of the present application provides a controller for an active clamp flyback conversion circuit, which can be used to control an operating state of the active clamp flyback conversion circuit. When the controller controls the active clamping flyback conversion circuit to operate in a continuous working state, the output voltage of the active clamping flyback conversion circuit is the rated output voltage. When the controller judges that the output voltage of the active clamping flyback conversion circuit is higher than a first preset value, the active clamping flyback conversion circuit is controlled to operate in a work pause state. And then, after the active clamp flyback conversion circuit operates in a suspended working state, when the controller judges that the output voltage of the auxiliary winding circuit in the active clamp flyback conversion circuit is less than or equal to a second preset value, the clamp capacitor of the active clamp flyback conversion circuit is controlled to discharge. Or after the active clamp flyback conversion circuit operates in a suspended working state, when the controller judges that the output voltage of the power supply circuit in the active clamp flyback conversion circuit is smaller than or equal to a third preset value, the clamp capacitor of the active clamp flyback conversion circuit is controlled to discharge. Therefore, after the active clamp flyback conversion circuit operates in the suspended working state, the controller provided by the embodiment can control the clamp capacitor of the active clamp flyback conversion circuit to discharge, so that the voltage value of the output voltage of the power supply circuit is higher than the preset voltage value of the low voltage protection of the controller, thereby preventing the controller from restarting due to the low voltage protection, and improving the stability of the power supply module and the electronic equipment where the active clamp flyback conversion circuit is located. In addition, the controller provided by the embodiment can not increase the ripple of the output voltage of the active clamp flyback conversion circuit when controlling the discharge of the clamp capacitor, and can not introduce noise from an input power supply.
In an embodiment of the first aspect of the present application, when the controller determines that the output voltage of the active clamp flyback conversion circuit is less than or equal to the rated output voltage, the controller controls the active clamp flyback conversion circuit to switch from the suspended operation state to the continuous operation state. Therefore, the controller provided by the embodiment can timely control the active clamp flyback conversion circuit to recover the continuous working state after the output voltage of the active clamp flyback conversion circuit recovers to be normal, and the stability of the power supply module and the electronic equipment where the active clamp flyback conversion circuit is located is further improved.
In an embodiment of the first aspect of the present application, the controller specifically controls the active clamp flyback converter circuit to operate in a suspended operating state by controlling both the auxiliary power transistor and the main power transistor of the half-bridge converter circuit in the active clamp flyback converter circuit to be turned off. Therefore, after the load level of the power module where the controller is located falls, the controller provided by the embodiment can control the active clamp flyback conversion circuit not to process the received input voltage and provide the output voltage, so that the load is prevented from being damaged due to overhigh output voltage of the power module.
In an embodiment of the first aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback converter circuit to be turned on, so as to discharge the clamp capacitor in the half-bridge circuit. The output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be quickly improved, the output voltage of the power supply module can be quickly reduced, the output voltage of the power supply module to a load is reduced to be larger than a first preset value as far as possible, and the load is effectively protected.
In an embodiment of the first aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback converter circuit to be periodically turned on, so as to discharge the clamp capacitor in the half-bridge circuit. Because the clamp capacitors in the half-bridge circuit discharge periodically, the output voltage of the auxiliary winding circuit and the output voltage of the power circuit can be increased in a stepped manner, and the circuit devices are prevented from being damaged due to too fast voltage increase, so that the stability of the power module and the electronic equipment where the active clamp flyback conversion circuit is located is improved.
In an embodiment of the first aspect of the present application, the controller controls the auxiliary power tube and the main power tube in the half-bridge circuit of the active clamp flyback converter circuit to be periodically and alternately turned on, so as to discharge the clamp capacitor in the half-bridge circuit. When the controller controls the auxiliary power tube to be switched on and the main power tube to be switched off, the clamping capacitor discharges, and the voltage value of the output voltage of the power supply circuit of the controller is increased; when the controller controls the auxiliary power tube to be cut off and the main power tube to be conducted, the input voltage generates primary winding voltage on two sides of the primary winding. The primary winding voltage is coupled through a transformer to produce an auxiliary winding voltage on the auxiliary winding. Accordingly, the voltage value of the output voltage of the auxiliary winding circuit is raised, and the voltage value of the output voltage of the power supply circuit of the controller is raised. The output voltage of the auxiliary winding circuit and the output voltage of the power circuit are increased in a stepped mode, and the phenomenon that circuit devices are damaged due to too fast increasing is avoided, so that the stability of a power module and electronic equipment where the active clamping flyback conversion circuit is located is improved.
In the above embodiments, in a scenario where the load level of the power module drops, the controller may control the clamping capacitor to start discharging. And when the controller controls the clamping capacitor to discharge, only the main power tube and the auxiliary power tube in the active clamping flyback conversion circuit need to be controlled to be switched on or switched off, so that the configuration is simple, and the active clamping flyback conversion circuit is more suitable for various products.
In an embodiment of the first aspect of the present application, the controller determines that the capacitor voltage of the clamping capacitor decreases to be less than or equal to a predetermined capacitor voltage value, and then controls the clamping capacitor to stop discharging. Therefore, the controller in the embodiment can prevent the situation that the restoration of the active clamp flyback conversion circuit to the continuous working state is influenced due to the fact that the capacitor voltage of the clamp capacitor is too low, and the stability of the power module and the electronic device where the active clamp flyback conversion circuit is located is further improved.
In an embodiment of the first aspect of the present application, the controller controls the clamp capacitor to stop discharging when the voltage value of the output voltage of the auxiliary winding circuit is increased to be greater than or equal to a fourth preset value. Therefore, the controller in this embodiment can prevent the power supply circuit and the controller from being damaged due to the excessively high voltage of the output voltage of the auxiliary winding circuit, and further improve the stability of the power supply module and the electronic device where the active clamping flyback conversion circuit is located.
In an embodiment of the first aspect of the present application, the controller may control the clamping capacitor to stop discharging when it is determined that the voltage value of the output voltage of the power circuit is increased to be greater than or equal to the fifth preset value. Therefore, the controller in this embodiment can prevent the controller from being damaged due to the overhigh voltage of the output voltage of the power circuit, and further improve the stability of the power module and the electronic device where the active clamping flyback conversion circuit is located.
In an embodiment of the first aspect of the present application, the controller controls the auxiliary power tube and the main power tube in the half-bridge circuit of the active clamp flyback converter circuit to be turned off, so that the clamp capacitor stops discharging. Therefore, in a scene that the load level of the power module drops, the controller in this embodiment controls the clamp capacitor to stop discharging only by controlling the conduction or the cut-off of the main power tube and the auxiliary power tube in the active clamp flyback conversion circuit, so that the configuration is simple, and the controller is more suitable for various products.
A second aspect of the present application provides a power supply module, which includes an active clamping flyback converter circuit, an auxiliary winding circuit, a power supply circuit, and a controller. Wherein, active clamp flyback conversion circuit includes: half-bridge circuit, transformer and rectifier circuit. The half-bridge circuit comprises a main power tube, an auxiliary power tube and a clamping capacitor.
The active clamping flyback conversion circuit is used for receiving input voltage, performing voltage conversion processing on the input voltage and then providing output voltage for a load. The auxiliary winding circuit is used for supplying power to the power supply circuit. The power supply circuit is used for supplying power to the controller. The controller may be used to control an active clamp flyback conversion circuit.
When the controller controls the active clamping flyback conversion circuit to operate in a continuous working state, the output voltage of the active clamping flyback conversion circuit is the rated output voltage. When the controller judges that the output voltage of the symmetrical half-bridge conversion circuit is higher than a first preset value, the active clamping flyback conversion circuit is controlled to operate in a work pause state. And then, after the active clamp flyback conversion circuit operates in a suspended working state, when the controller judges that the output voltage of the auxiliary winding circuit in the active clamp flyback conversion circuit is less than or equal to a second preset value, the clamp capacitor of the active clamp flyback conversion circuit is controlled to discharge. Or after the active clamp flyback conversion circuit operates in a suspended working state, when the controller judges that the output voltage of the power supply circuit in the active clamp flyback conversion circuit is smaller than or equal to a third preset value, the clamp capacitor of the active clamp flyback conversion circuit is controlled to discharge.
Therefore, in the power module provided by this embodiment, the controller can control the clamp capacitor of the active clamp flyback conversion circuit to discharge after the active clamp flyback conversion circuit operates in the suspended operating state, so that the voltage value of the output voltage of the power circuit is higher than the preset voltage value of the low-voltage protection of the controller, thereby preventing the controller from being restarted due to the low-voltage protection, and improving the stability of the power module and the electronic device where the power module is located. In addition, the controller provided by the embodiment can not increase the ripple of the output voltage of the active clamp flyback conversion circuit when controlling the discharge of the clamp capacitor, and can not introduce noise from an input power supply.
In an embodiment of the second aspect of the present application, when the controller determines that the output voltage of the active clamp flyback conversion circuit is less than or equal to the rated output voltage, the controller controls the active clamp flyback conversion circuit to switch from the suspended operation state to the continuous operation state. Therefore, in the power module provided by this embodiment, the controller can timely control the active clamp flyback conversion circuit to recover the continuous working state after the output voltage of the active clamp flyback conversion circuit recovers to normal, so as to further improve the stability of the power module and the electronic device where the power module is located.
In an embodiment of the second aspect of the present application, the controller specifically controls the active clamp flyback converter circuit to operate in a suspended operating state by controlling both the auxiliary power transistor and the main power transistor of the half-bridge converter circuit in the active clamp flyback converter circuit to be turned off. Therefore, in the power supply module provided by this embodiment, after the load level of the power supply module where the controller is located falls, the controller controls the active clamp flyback conversion circuit to stop processing the received input voltage and provide the output voltage, so as to avoid the load damage caused by the overhigh output voltage of the power supply module.
In an embodiment of the second aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback converter circuit to be turned on, so as to discharge the clamp capacitor in the half-bridge circuit. The output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit can be improved quickly, the output voltage of the power supply module can be reduced quickly, the output voltage of the power supply module to the load is reduced as far as possible, and the load is protected more effectively.
In an embodiment of the second aspect of the present application, the controller controls the auxiliary power transistor in the half-bridge circuit of the active clamp flyback converter circuit to be periodically turned on, so as to discharge the clamp capacitor in the half-bridge circuit. Because the clamping capacitor in the half-bridge circuit discharges periodically, the output voltage of the auxiliary winding circuit and the output voltage of the power circuit can be increased in a stepped manner, and the circuit device is prevented from being damaged due to too fast voltage increase, so that the stability of the power module and the electronic equipment where the power module is located is improved.
In an embodiment of the second aspect of the present application, the controller controls the auxiliary power tube and the main power tube in the half-bridge circuit of the active clamp flyback conversion circuit to be periodically and alternately turned on, so as to discharge the clamp capacitor in the half-bridge circuit. When the controller controls the auxiliary power tube to be switched on and the main power tube to be switched off, the clamping capacitor discharges, and the voltage value of the output voltage of the power supply circuit of the controller is increased; when the controller controls the auxiliary power tube to be cut off and the main power tube to be conducted, the input voltage generates primary winding voltage on two sides of the primary winding. The primary winding voltage is coupled through a transformer to produce an auxiliary winding voltage on the auxiliary winding. Accordingly, the voltage value of the output voltage of the auxiliary winding circuit is raised, and the voltage value of the output voltage of the power supply circuit of the controller is raised. The output voltage of the auxiliary winding circuit and the output voltage of the power supply circuit are boosted in a stepped manner, so that the circuit devices are prevented from being damaged due to too fast boosting, and the stability of the power supply module and the electronic equipment where the power supply module is located is improved.
In the foregoing embodiments, in a scenario where the load level of the power module drops, the controller in the power module may control the clamping capacitor to start discharging. And when the controller controls the clamp capacitor to discharge, only the main power tube and the auxiliary power tube in the active clamp flyback conversion circuit need to be controlled to be switched on or switched off, so that the configuration is simple, and the active clamp flyback conversion circuit is more suitable for various products.
In an embodiment of the second aspect of the present application, the controller determines that the capacitor voltage of the clamping capacitor decreases to be less than or equal to the predetermined capacitor voltage value, and controls the clamping capacitor to stop discharging. Therefore, the controller in the embodiment can prevent the situation that the capacitor voltage of the clamp capacitor is too low to affect the recovery of the active clamp flyback conversion circuit to the continuous working state, and further improves the stability of the power module and the electronic device in which the power module is located.
In an embodiment of the second aspect of the present application, the controller controls the clamping capacitor to stop discharging when the voltage value of the output voltage of the auxiliary winding circuit is increased to be greater than or equal to the fourth preset value. Therefore, the controller in this embodiment can prevent the power supply circuit and the controller from being damaged due to the overhigh voltage of the output voltage of the auxiliary winding circuit, and further improve the stability of the power supply module and the electronic device in which the power supply module is located.
In an embodiment of the second aspect of the present disclosure, the controller may control the clamping capacitor to stop discharging when the voltage value of the output voltage of the power circuit is increased to be greater than or equal to the fifth preset value. Therefore, the controller in this embodiment can prevent the controller from being damaged due to the excessively high voltage of the output voltage of the power circuit, and further improve the stability of the power module and the electronic device in which the power module is located.
In an embodiment of the second aspect of the present application, the controller controls the auxiliary power tube and the main power tube in the half-bridge circuit of the active clamp flyback conversion circuit to be turned off, so that the clamp capacitor stops discharging. Therefore, in the scenario that the load level of the power supply module drops, the controller of the power supply module controls the clamp capacitor to stop discharging, and only the main power tube and the auxiliary power tube in the active clamp flyback conversion circuit need to be controlled to be turned on or off, so that the configuration of the power supply module is simple, and the power supply module is more suitable for various products.
In the above embodiments, the dc converter circuit is taken as an example of an active clamp flyback converter circuit, and the dc converter circuit may be an asymmetric half-bridge converter circuit.
A third aspect of the application provides an electronic device comprising a controller of an active-clamp flyback converter circuit as claimed in any of the first aspects of the application.
A fourth aspect of the present application provides an electronic device, including the power module according to any one of the second aspects of the present application.
Drawings
Fig. 1 is a schematic diagram of an electronic device provided in the present application;
fig. 2 is another schematic diagram of an electronic device provided in the present application;
Fig. 3 is a schematic diagram of a power module according to an embodiment of the disclosure;
FIG. 4 is a schematic diagram of a power module;
FIG. 5 is a schematic voltage waveform diagram of the power module of FIG. 4 in a situation where a drop occurs in the load level;
FIG. 6 is a schematic diagram of another conventional controller and a power module thereof;
fig. 7 is a schematic diagram of a power module according to an embodiment of the disclosure;
fig. 8 is a schematic voltage waveform diagram of a controller and a power module thereof provided in the present application in a situation where a load level drops;
FIG. 9 is a schematic diagram of an embodiment of a power module provided in the present application;
FIG. 10 is a schematic diagram of an embodiment of a power module provided in the present application;
fig. 11 is a schematic voltage waveform diagram of a controller and a power module thereof provided in the present application in a situation where a load level drops;
FIG. 12 is a schematic diagram of an embodiment of a power module provided in the present application;
fig. 13 is a schematic diagram of a control signal of the controller provided in the present application in a scenario where a load level of a power module is dropped;
FIG. 14 is a schematic diagram of control signals of a controller according to an embodiment of the present disclosure;
FIG. 15 is a schematic diagram of an embodiment of a controller controlling the discharge of the resonant capacitor of the AHB conversion circuit;
Fig. 16 is a schematic diagram illustrating a variation of a capacitance voltage of a resonant capacitor of the AHB conversion circuit provided in the present application;
FIG. 17 is a schematic diagram of another embodiment of a controller controlling the discharge of the resonant capacitor of the AHB conversion circuit provided in the present application;
FIG. 18 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided in the present application;
FIG. 19 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided in the present application;
FIG. 20 is a schematic view of an embodiment of a power module according to the present application;
FIG. 21 is a schematic view of an embodiment of a power module provided herein;
fig. 22 is a schematic voltage waveform diagram of a controller and a power module thereof provided in the present application in a situation where a load level drops;
FIG. 23 is a schematic diagram of an embodiment of a power module provided in the present application;
fig. 24 is a schematic diagram of a control signal of the controller provided in the present application in a situation where a load level of a power module is dropped;
FIG. 25 is a schematic diagram of control signals of a controller according to an embodiment of the present disclosure;
FIG. 26 is a schematic diagram of an embodiment of a controller controlling discharge of clamp capacitors of an ACF conversion circuit;
fig. 27 is a schematic diagram illustrating a variation of a capacitance voltage of a clamp capacitor of an ACF conversion circuit provided in the present application;
Fig. 28 is a schematic diagram of another embodiment of a controller for controlling discharge of clamp capacitors of an ACF conversion circuit according to the present application.
Detailed Description
Fig. 1 is a schematic view of an electronic device provided in the present application. As shown in fig. 1, the electronic device 10 includes a power module 11 and a load 12. Wherein, the power module 11 receives an input voltage V provided by an input power 131And providing an output voltage V2To power the load 12. In one embodiment, the electronic device 10 may include a plurality of power modules 11, wherein the plurality of power modules 11 provide a plurality of output voltages V2To power the load 12. In one embodiment, the electronic device 10 may include a plurality of loads 12, and the power module 11 provides a plurality of output voltages V2A plurality of loads 12 are powered individually. In one embodiment, the electronic device 10 may include a plurality of loads 12 and a plurality of power modules 11, and the plurality of power modules 11 may respectively supply power to the plurality of loads 12. In one embodiment, the electronic device 10 may receive the output of multiple input power sources 13Voltage V1. In one embodiment, the electronic device 10 may include one or more input power sources 13. In one embodiment, the electronic device 10 may be a mobile phone, a computer, a tablet, or a home appliance. In one embodiment, load 12 comprises internal circuitry of electronic device 10 or external electronics of electronic device 10.
Fig. 2 is another schematic view of an electronic device provided in the present application. As shown in fig. 2, the electronic device 10 includes a power module 11. The power module 11 receives an input voltage V provided by an input power 131And providing an output voltage V2To power the load 12. In one embodiment, the electronic device 10 includes a plurality of power modules 11, and the plurality of power modules 11 can provide a plurality of output voltages V2To power the load 12. In one embodiment, the power module 11 of the electronic device 10 can provide a plurality of output voltages V2A plurality of loads 12 are powered individually. In one embodiment, the electronic device 10 may include a plurality of power modules 11, and the plurality of power modules 11 respectively provide the output voltages V for the plurality of loads 122. In one embodiment, the electronic device 10 may receive a plurality of input power sources 13. In one embodiment, the electronic device 10 may include an input power source 13. In one embodiment, the electronic device 10 may be an adapter, a charging post, or the like. In general, an adapter (adapter) may also be referred to as a charger (charger), a charging head, a switch power supply (switch power supply), a power converter (power converter), or the like. In one embodiment, the load 12 may be an electronic device such as a mobile phone, a computer, a tablet, or a home appliance. In one embodiment, load 12 may be other internal circuitry of electronic device 10.
Fig. 3 is a schematic diagram of a power module according to an embodiment of the disclosure. As shown in fig. 3, the power module 11 includes a Direct Current (DC) conversion circuit 111, an auxiliary winding circuit 112, a power circuit 113, and a controller 114. The DC conversion circuit 111 is used for receiving an input voltage V provided by an input power supply 131And provides an output voltage V to load 122. The dc converter circuit 111 supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112. WhereinAn auxiliary winding circuit 112 is coupled to the dc converter circuit 111 for generating an auxiliary winding voltage V at the auxiliary winding3. The auxiliary winding circuit 112 converts the auxiliary winding voltage V3Is converted into an output voltage V4And supplies an output voltage V to the power supply circuit 1134. The power supply circuit 113 supplies the output voltage V of the auxiliary winding circuit 1124Is converted into an output voltage V5And provides an output voltage V to the control circuit 1145. The controller 114 is configured to control the dc conversion circuit 111. In the embodiment of the present application, the dc conversion circuit 111 may include an asymmetric half-bridge (AHB) conversion circuit or an Active Clamp Flyback (ACF) conversion circuit.
Fig. 4 is a schematic diagram of a power module. As shown in fig. 4, the power module 11 includes a dc conversion circuit 111, an auxiliary winding circuit 112, a power circuit 113, and a controller 114. The dc conversion circuit 111 may include a half-bridge circuit 1110, a transformer 1112, and a rectifying circuit 1114. The transformer 1112 includes a primary winding 1111 and a secondary winding 1113. In addition, the transformer 1112 further includes an auxiliary winding 1121 in the auxiliary winding circuit 112. Secondary winding 1113 is coupled to primary winding 1111 and auxiliary winding 1121 is coupled to primary winding 1111.
Half-bridge circuit 1110 for receiving input voltage V provided by input power supply 131And provides an output voltage V according to a control signal of the controller 11410. Input voltage V1And an output voltage V10May be a range of voltages. Half-bridge circuit 1110 typically includes a main power transistor, an auxiliary power transistor, and a capacitor. The dc conversion circuit 111 includes an AHB conversion circuit and an ACF conversion circuit according to the connection relationship between the main power transistor, the auxiliary power transistor, and the capacitor. The capacitor in the half-bridge circuit 1110 of the AHB conversion circuit is a resonant capacitor Cr. The capacitor in half-bridge 1110 of ACF conversion circuit is clamping capacitor Cc。
Primary winding 1111 of transformer 1112 is adapted to receive the output voltage V of half-bridge circuit 111010And generates a primary winding voltage V on the primary winding 111111. Through a secondary winding 1113 of the transformer 1112 and a primary winding of the transformer 1112Group 1111 is coupled to generate a secondary winding voltage V on secondary winding 111312. Winding voltage V11And secondary winding voltage V12May be a range of voltages.
The rectifying circuit 1114 is used for receiving the secondary winding voltage V generated on the secondary winding 111312And converted into an output voltage V2. Output voltage V2May be a range of voltages.
The auxiliary winding circuit 112 is used to power a power supply circuit 113. An auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111 of the transformer 1112. Primary winding voltage V on primary winding 1112 11Coupled to produce an auxiliary winding voltage V across auxiliary winding 11213. Auxiliary winding voltage V3After being processed by the auxiliary winding circuit 112, the output voltage V is provided to the power circuit 1134. The auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifying module 1122. Auxiliary winding voltage V3And an output voltage V4May be a range of voltages.
The power supply circuit 113 is used to supply power to the controller 114. The power supply circuit 113 receives the output voltage V of the auxiliary winding circuit 1124And provides an output voltage V to the controller 1145. The power circuit 113 may include a voltage stabilizing circuit. Output voltage V5May be a range of voltages.
The controller 114 is used to control the operation state of the dc conversion circuit 111. The controller 114 may send a control signal G to the half-bridge circuit 1110 of the dc converter circuit 111, thereby controlling the operation state of the dc converter circuit 111. The operation state of the dc link circuit 111 generally includes a continuous operation state and a pause operation state. The continuous operation state may also be referred to as a normal operation state, a controller normal wave generation state, and the like. The pause state may also be referred to as an intermittent operation state, a BURST operation state, a controller intermittent wave state, or the like.
When the load level of the load 12 of the power module 11 drops, the primary winding voltage V of the primary winding 1111 in the dc conversion circuit 11111No change will result in the output of the DC-to-DC converter 111Voltage V2The voltage value of (2) is rapidly increased. Accordingly, the controller 114 needs to adjust the operation state of the dc conversion circuit 111 so as to lower the output voltage V of the dc conversion circuit 1112To avoid the output voltage V of the power module 112Too high to damage load 12.
Fig. 5 is a voltage waveform diagram of the power module of fig. 4 in a load level droop scenario. The following describes the effect of the load level L of the load 12 falling on the conventional controller 114 and the power module 11 in which the controller is located in detail with reference to the power module 11 shown in fig. 4.
At t1Before the moment, the load level L of the load 12 is the normal load L1. The controller 114 controls the DC conversion circuit 111 to be in a continuous operation state, and the output voltage V of the DC conversion circuit 1112The voltage value of (A) is rated output voltage V20. Rated output voltage V20The rated output voltage of the dc converter circuit 111 in the continuous operation state. Rated output voltage V20May be a range of voltages. Accordingly, the output voltage V of the auxiliary winding circuit 112 4Has a voltage value of V40. Voltage value V40Is the nominal input voltage of the auxiliary winding circuit 112. Voltage value V40May be the output voltage V of a voltage range power supply circuit 1135Has a voltage value of V50. Voltage value V50Is the nominal input voltage of the controller 114. Voltage value V50May be a range of voltages.
At t1At that moment, the load level L of the load 12 is changed from the normal load L1Drop to light load L2。
At t1After the time, the output voltage V of the dc conversion circuit 1112Will rise to a voltage value greater than the rated output voltage V20. In one embodiment, the controller 114 controls the dc conversion circuit 111 to operate in a continuous operation state. In addition, the controller 114 reduces the conduction frequency or the conduction time of the main power tube and the auxiliary power tube in the half-bridge circuit 1111, so that the primary winding voltage V of the primary winding 1111 is reduced11The voltage value of (2) decreases. Accordingly, the secondary winding voltage V13The voltage value of (3) is decreased, the output voltage V of the DC conversion circuit 111 can be decreased2The voltage value of (2). Since the auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111, the voltage V of the auxiliary winding3The voltage value of (2) decreases. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases 5The voltage value of (2) decreases.
However, the load level of the load 12 has a large drop effect, and the controller 114 cannot usually effectively reduce the output voltage V of the dc-dc converter circuit 111 by only reducing the conduction frequency or the conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 11112The voltage value of (2). Result in at t1After the time point, the output voltage V of the dc conversion circuit 1112Will continue to rise.
At t1T after the moment of time2At that time, the output voltage V of the DC conversion circuit 1112The voltage value of the voltage is increased to be more than or equal to a first preset value V21. Output voltage V of conversion circuit 1112Will damage the load 12. To prevent the output voltage V of the DC conversion circuit 1112The voltage value of the dc converter circuit 111 is continuously increased, and the controller 114 needs to control the dc converter circuit 111 to operate in the pause state. Wherein the voltage value V is adjusted21Record as a first preset value, voltage value V21Is the maximum output voltage of the dc conversion circuit 111. Voltage value V21Less than the rated output voltage V of the DC conversion circuit 11120And is smaller than the overvoltage protection voltage of the dc conversion circuit 111.
At t2After the moment, the dc conversion circuit 111 is in a suspended state, so that the primary winding voltage V of the primary winding circuit 1111 in the dc conversion circuit 111 11And (4) descending. Accordingly, the output voltage V of the dc conversion circuit 1112The voltage value of (2) decreases. Since the auxiliary winding 1121 is coupled to the primary winding 1111, the primary winding voltage V of the primary winding 111111Drop, which results in an auxiliary winding voltage V of the auxiliary winding 11213The voltage value of (2) decreases. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, and the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
If the output voltage V of the power supply circuit 113 is5Is less than the under-voltage protection voltage V of the controller 11451The controller 114 will restart because of the low voltage protection. Voltage value V51Is the under-voltage protection voltage of the controller 114. The controller 114 needs a period of time to complete the restart process, so that the controller 14 cannot control the operating state of the dc transformer circuit 111 during the period of time, thereby affecting the stability of the power module 11 and the electronic device 10 where the controller 114 is located.
At t2T after time3At that time, the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V52. Third preset value V52Greater than the undervoltage protection voltage V of the controller 11451And is less than the rated input voltage V of the controller 11450. When the output voltage V of the power circuit 113 is 5Is less than or equal to a third predetermined value V52The controller 114 controls the dc conversion circuit 111 to operate in a continuous operation state. Accordingly, the primary winding voltage V11The voltage value of (2) is raised. Primary winding voltage V11Can lead to an auxiliary winding voltage V3The voltage value of (2) is raised. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (2) is raised. Output voltage V of power supply circuit 1135The voltage value of (2) is raised. However, the primary winding voltage V11The voltage value of (2) is increased, and the secondary winding voltage V is also caused12So that the output voltage V of the dc conversion circuit 111 is raised2The voltage value of (2) is raised.
At t3T after the moment4At that time, the output voltage V of the DC conversion circuit 1112Is raised to be greater than or equal to a second predetermined value V21. At this time, the controller 114 needs to control the dc converter circuit 111 to operate in the suspended state. The DC conversion circuit 111 operates in a pause state to make the primary winding voltage V11The voltage value of (2) decreases. Accordingly, direct currentOutput voltage V of conversion circuit 1112The voltage value of (2) decreases. However, the primary winding voltage V11Will also result in the output voltage V of the auxiliary winding circuit 112 4The voltage value of (2) decreases. Accordingly, the output voltage V of the power supply circuit 1135The voltage value of (2) decreases.
At t4T after the moment of time5At that time, the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a fifth predetermined value V52. At this time, the controller 114 needs to control the dc converter circuit 111 to operate in a continuous operation state. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (2) is raised. Output voltage V of power supply circuit 1135The voltage value of (2) is raised. However, the dc conversion circuit 111 operates in a continuous operation state, which causes the output voltage V of the dc conversion circuit 111 to be increased2The voltage value of (2) is raised.
Therefore, although the controller 114 in the conventional power module 11 can avoid the restart due to the under-voltage protection, the controller also causes the output voltage V of the dc converter circuit 1112The corrugation of (2) is large. Therefore, the conventional controller 114 and the power module 11 thereof will cause the output voltage V of the dc conversion circuit 1112The ripple of (2) is large, thereby affecting the stability of the power module 11.
Fig. 6 is a schematic diagram of another conventional controller and a power module thereof. As shown in fig. 6, the auxiliary winding circuit 112 of the power module 11 is connected to the input power 13 through the switch K. The change in the load level L of the load 12 causes the output voltage V of the dc conversion circuit 111 2After the voltage value is raised, the controller 114 controls the dc conversion circuit 111 to operate in the suspended state, and the controller 114 controls the switch K to be turned on. The input power 13 supplies power to the power circuit 113 through the switch K and the auxiliary winding circuit 112, thereby preventing the controller 114 from restarting due to undervoltage protection. However, noise of the input power 13 is also transmitted to the inside of the power module 11 through the switch K, and affects electromagnetic compatibility (EMC) of the power module 11.
The application provides a controller of a direct current conversion circuit, a power module and electronic equipment where the controller is located, and the controller can overcome the defects that in the prior art, the stability problem, the electromagnetic compatibility problem, the output voltage ripple increase and the like of the controller, the power module and the electronic equipment where the controller is located are overcome. The following examples are given in detail. The following embodiments may be combined, and details of the same or similar concepts or processes may not be repeated in some embodiments.
Fig. 7 is a schematic diagram of a power module according to an embodiment of the disclosure. The power module 11 shown in fig. 7 can be applied to the electronic device 10 shown in fig. 1 or fig. 2. As shown in fig. 7, the power module 11 includes a dc conversion circuit 111, an auxiliary winding circuit 112, a power circuit 113, and a controller 114. The dc conversion circuit 111 may include a half-bridge circuit 1110, a transformer 1112, and a rectifying circuit 1114. The transformer 1112 includes a primary winding 1111 and a secondary winding 1113. In addition, the transformer 1112 further includes an auxiliary winding 1121 in the auxiliary winding circuit 112. Secondary winding 1113 is coupled to primary winding 1111 and auxiliary winding 1121 is coupled to primary winding 1111.
Half-bridge circuit 1110 is arranged to receive an input voltage V provided by an input power supply 131And provides an output voltage V to the primary winding 1111 according to a control signal of the controller 11410. Half-bridge circuit 1110 typically includes a main power transistor, an auxiliary power transistor, and a capacitor. According to the connection relationship between the main power transistor, the auxiliary power transistor and the capacitor, the dc converter 111 in the embodiment of the present application includes an AHB converter and an ACF converter. In one embodiment, the dc-dc converter 111 comprises an AHB converter, and the capacitor in the half-bridge 1110 is a resonant capacitor Cr. In one embodiment, DC converter 111 comprises an ACF converter, and half-bridge 1110 has a clamp capacitor Cc. In one embodiment, the main power Transistor and the auxiliary power Transistor are Metal-Oxide-Semiconductor Field-Effect transistors (MOS). In other embodiments, the main power Transistor and the auxiliary power Transistor may also be transistors or other types of transistors such as an Insulated Gate Bipolar Transistor (IGBT).
Primary winding 1111 of transformer 1112 is adapted to receive the output voltage V of half-bridge circuit 111010And generates a primary winding voltage V 11. A secondary winding 1113 of the transformer 1112 is coupled to a primary winding 1111 of the transformer 1112 such that a secondary winding voltage V is generated across the secondary winding 11133。
The rectifying circuit 1114 is used for receiving the secondary winding voltage V on the secondary winding 11133And converted into an output voltage V2。
The auxiliary winding circuit 112 is used to supply power to the power supply circuit 113. An auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111 of the transformer 1112. Primary winding voltage V on primary winding 111211Coupled to produce an auxiliary winding voltage V across auxiliary winding 11213. Auxiliary winding voltage V3After being processed by the auxiliary winding circuit 112, the output voltage V is provided to the power circuit 1134. In one embodiment, the auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectification module 1122.
The power supply circuit 113 is used to supply power to the controller 114. The power supply circuit 113 receives the output voltage V of the auxiliary winding circuit 1124And provides an output voltage V to the controller 1145. That is, the dc converter circuit 111 supplies power to the power circuit 113 of the controller 114 via the auxiliary winding circuit 112 coupled to the primary winding 1111 of the transformer 1112. In some embodiments, the power circuit 113 includes a voltage regulation circuit.
The controller 114 is used to control the operation state of the dc conversion circuit 111. The controller 114 is also used for detecting the output voltage V of the DC conversion circuit 111 2Output voltage V of winding circuit 1124And an output voltage V of the power supply circuit 1135Or the capacitor voltage V of the capacitor in half-bridge circuit 1110cVariations in the plurality of voltage values. The controller 114 is further configured to control an operation state of the dc conversion circuit 111 according to the change of the one or more voltage values.
In one embodiment, the controller 114 controls the operation state of the dc converter circuit 111 by controlling the operation state of the half-bridge circuit 1110 in the dc converter circuit 111. For example, the controller 114 may controlThe main power transistor and the auxiliary power transistor of the bridge circuit 1110 are turned on and off, so as to control the operation state of the half-bridge circuit 1110. The controller 114 can adjust the turn-on frequency or the turn-on duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110, and accordingly adjust the output voltage V of the half-bridge circuit 111010. Accordingly, the output voltage V of half-bridge circuit 111010Will result in a primary winding voltage V11And (4) changing. Accordingly, the primary winding voltage V11Can result in a secondary winding voltage V12And an auxiliary winding voltage V3And (4) changing. Accordingly, the secondary winding voltage V12May result in the output voltage V of the dc conversion circuit 1112And (4) changing. Accordingly, the auxiliary winding voltage V 3May result in an output voltage V of the auxiliary winding circuit 1124And (4) changing. Accordingly, the output voltage V of the auxiliary winding circuit 1124Can result in an output voltage V of the power supply 1135A change in (c).
The DC converter circuit 111 may provide an output voltage V as shown in the direction of F1 in FIG. 72To power the load 12. Wherein the input voltage V1Converted into an output voltage V by a half-bridge circuit 1110, a primary winding 1111, a secondary winding 1113 and a rectifying circuit 1114 of the DC conversion circuit 1112。
As shown in the direction of F2 in fig. 7, the dc converter circuit 111 may supply power to the power circuit 113 of the controller 114 through the auxiliary winding circuit 112. Wherein the input voltage V1After being processed by the half-bridge circuit 1110 of the dc conversion circuit 111, a primary winding voltage V can be generated at the primary winding 111111. Accordingly, the primary winding voltage V11An auxiliary winding voltage V can be generated across an auxiliary winding 1121 of the transformer 11123. Auxiliary winding voltage V3Processed by an auxiliary winding circuit 1121 to provide an output voltage V4And supplies power to the power supply circuit 113 of the controller 114.
Fig. 8 is a schematic voltage waveform diagram of a controller and a power module in which the controller is located in a scene where a load level drops. The following describes an operation process of the controller 114 and the power module 11 thereof provided in the present application in a scenario where the load level L of the load 12 falls down, with reference to fig. 7 and 8.
At t1Before the moment, the load level L of the load 12 is the normal load L1The controller 114 controls the dc conversion circuit 111 to operate in a continuous operation state, and the controller 114 controls the output voltage V of the dc conversion circuit 1112Is a rated output voltage V20. Output voltage V of auxiliary winding circuit 1124Has a voltage value of V40. Output voltage V of power supply circuit 1135Has a voltage value of V50. Capacitor voltage V of capacitor in half-bridge circuit 1111cHas a voltage value of VC1。VC1The capacitor voltage of the capacitor when the dc conversion circuit 111 operates in the continuous operation state.
At t1At that moment, the load level L of the load 12 is changed from the normal load L1Drop to light load L2. Accordingly, at t1After the time, the output voltage V of the dc conversion circuit 1112Will rise to a voltage value greater than the rated output voltage V20。
In one embodiment, the output voltage V of the DC conversion circuit 111 is set2Has a voltage value greater than the rated output voltage V20The controller 114 may control the dc conversion circuit 111 to operate in a continuous operation state. The controller 114 controls the dc conversion circuit 111 to lower the output voltage V2The voltage value of (2). That is, the controller 114 is controlled according to the output voltage V of the DC conversion circuit 1112Voltage value of and rated output voltage V 20As a result of the comparison, the controller 114 controls the dc converting circuit 111 to operate in a continuous operation state, and the controller 114 controls the dc converting circuit 111 to decrease the output voltage V2The voltage value of (2). Specifically, controller 114 sends control signal G to control the operating states of the main power tube and the auxiliary power tube in half-bridge circuit 1110, so that the primary winding voltage V is applied11The voltage value of (2) decreases. In one embodiment, the controller 114 may decrease the transmission frequency of the control signal G, thereby decreasing the conduction frequency of the main power transistor and the auxiliary power transistor. In one embodiment, the controller 114 may decrease the duty cycle of the control signal G, thereby decreasing the duty cycle of the control signal GThe conduction duration of the main power tube and the auxiliary power tube is reduced. In another embodiment, the output voltage V of the DC conversion circuit 111 is set2Has a voltage value greater than the rated output voltage V20The controller 114 can control the dc converting circuit 111 to operate in the suspended state, and can also reduce the output voltage V2The voltage value of (2). However, both of the above embodiments may not enable the output voltage V of the dc conversion circuit 1112Is effectively reduced, at t1Output voltage V of dc conversion circuit 111 after the time2Will continue to rise.
At the same time, at t1After the time, the drop of the load level L causes the output voltage V of the dc conversion circuit 1112Is higher than the rated output voltage V20. Primary winding voltage V11Charging the capacitor in half-bridge circuit 1110, the voltage V of the capacitor in half-bridge circuit 1110cVoltage value of from VC1Is lifted to VC2。VC2Is the maximum charging voltage of the capacitor in half bridge circuit 1110.
At t1T after the moment2At that time, the output voltage V of the DC conversion circuit 1112The voltage value of the transformer is increased to a first preset value V21. The controller 114 determines the output voltage V of the dc conversion circuit 1112Is greater than or equal to a first preset value V21The controller 114 controls the dc conversion circuit 111 to suspend operation. That is, the controller 114 is controlled according to the output voltage V of the DC conversion circuit 1112Voltage value of (d) and a first predetermined value V21As a result of the comparison, the controller 114 controls the dc conversion circuit 111 to operate in the suspended state. Specifically, the controller 114 controls the main power transistor and the auxiliary power transistor of the half-bridge circuit 1110 to be turned off. In the embodiment of the present application, the first preset value V21May be the peak voltage of the dc conversion circuit 111. The peak voltage of the DC conversion circuit 111 is greater than the rated output voltage V20And is smaller than the overvoltage protection voltage of the dc conversion circuit 111.
At t2After the time, the controller 114 controls the dc conversion circuit 111 to operate in the pause state. Accordingly, theOutput voltage V of half-bridge circuit 111010So that the voltage value of the primary winding 1111 is decreased, the voltage of the primary winding V is applied to the primary winding 111111The voltage value of (2) decreases. Primary winding voltage V on primary winding 111111Will result in a secondary winding voltage V across the secondary winding 111312And (4) descending. Accordingly, the output voltage V of the dc conversion circuit 1112The voltage value of (2) decreases. In addition, the primary winding voltage V on the primary winding 111111Will result in an auxiliary winding voltage V3The voltage value of (2) decreases. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
At t2T after time3At that moment, the output voltage V of the auxiliary winding circuit 1124Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V52. Wherein the voltage value V is adjusted41Is recorded as a second preset value, voltage value V41Is greater than the lowest input voltage of the power circuit 113 and is less than the rated input voltage V of the power circuit 113 40. Voltage value V52Record as the third preset value, voltage value V52Greater than the undervoltage protection voltage V of the controller 11451And is less than the rated input voltage V of the controller 11450
In one embodiment, the controller 114 determines the output voltage V of the auxiliary winding circuit 1124Is less than or equal to a second preset value V41Controller 114 controls the discharge of the capacitor in half-bridge circuit 1110. That is, the controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a second predetermined value V41Controls the discharge of the capacitor in half bridge circuit 1110.
In one embodiment, the controller 114 determines the output voltage V of the power circuit 1135Is less than or equal to a third predetermined value V52Controller 114 controls the discharge of the capacitor in half-bridge circuit 1110. That is, the controller 114 is powered according to the power supplyOutput voltage V of path 1135Voltage value of (d) and a third predetermined value V52As a result of the comparison, controller 114 controls the discharge of the capacitor in half-bridge circuit 1110.
In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110 to be turned on, so that the capacitor of the half-bridge circuit 1110 is discharged. When the auxiliary power tube in the half-bridge circuit 1110 is turned on, the primary winding 1111, the capacitor of the half-bridge circuit 1110, and the auxiliary power tube may form a discharge loop. Accordingly, the capacitor in half-bridge circuit 1110 discharges, producing a primary winding voltage V across primary winding 1111 11。
In one embodiment, controller 114 controls the auxiliary power transistor in half-bridge circuit 1110 to be turned on periodically, so that the capacitor of half-bridge circuit 1110 is discharged. When the auxiliary power in half-bridge circuit 1110 is turned on, primary winding 1111, the capacitor of half-bridge circuit 1110, and the auxiliary power tube of half-bridge circuit 1110 may form a discharge loop. Accordingly, the auxiliary power transistor is periodically turned on, which may cause the capacitor in half-bridge circuit 1110 to be periodically discharged.
In one embodiment, the dc-dc converter circuit 111 includes an AHB converter circuit, and the controller 114 controls the resonance capacitor in the half-bridge circuit 1110 of the AHB converter circuit to discharge. In one embodiment, the dc conversion circuit 111 includes an ACF conversion circuit, and the controller 114 controls the clamp capacitors in the half bridge circuit 1110 of the ACF conversion circuit to discharge. In one embodiment, a plurality of capacitors may be included in half-bridge circuit 1110 of dc converter circuit 111, and controller 114 controls the plurality of capacitors in half-bridge circuit 1110 to discharge.
At t3After the moment, the capacitor voltage V of the capacitor in half-bridge circuit 1110cThe voltage value of (2) decreases. The capacitor in half-bridge circuit 1110 discharges, causing a primary winding voltage V on primary winding 111111The voltage value of (2) is raised. Accordingly, the primary winding voltage V 11The voltage value of (2) is increased, which results in an auxiliary winding voltage V3The voltage value of (2) is raised. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased5The voltage value of (2) is raised. Thus, the load level of the load 12 occursIn a changing scenario, the output voltage V of the power supply circuit 1135Does not drop below the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection.
The controller 114 provided in this embodiment of the application can control the capacitor in the primary winding circuit 1111 of the dc conversion circuit 111 to discharge, so that the output voltage V of the power supply circuit 113 is obtained5Is higher than the preset voltage value V of the low voltage protection of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
Because of the limited energy stored by the capacitor in half-bridge circuit 1110, the primary winding voltage V is generated across primary winding 1111 after discharge11The voltage value of (2) is small. The voltage V of the primary winding generated at the primary winding 1111 at this time11Is less than the secondary winding voltage V on the secondary winding 1113 12Without causing the output voltage V of the DC transformer circuit 1112And (5) lifting. Therefore, the controller 114 controls the primary winding voltage V generated on the primary winding 1111 after the capacitor in the half-bridge circuit 1110 is discharged11For boosting the output voltage V of the auxiliary winding circuit 112 only4And the output voltage V of the power supply circuit 1135As shown in the direction of F2 in fig. 7. Therefore, the controller 114 and the power module 111 thereof provided in the embodiment of the present application can not only prevent the controller 114 from being restarted due to under-voltage protection, but also prevent the output voltage V of the dc conversion circuit 111 from being increased2The ripple of (2) can improve the stability of the power module 11 and the electronic device 10 in which the controller 114 is located.
In addition, the controller 114 provided in the embodiment of the present application controls the capacitor in the dc conversion circuit 111 to discharge, so that noise from the input power supply 13 is not introduced, and the noise can be prevented from affecting the electromagnetic compatibility of the dc conversion circuit 111 and the power module 11 and the electronic device 10 in which the dc conversion circuit is located. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
In an embodiment of the present application, after the capacitor in the half-bridge circuit 1110 of the dc conversion circuit 111 starts to discharge, the controller 114 may further determine the capacitor voltage V according to the capacitor in the half-bridge circuit 1110 cVoltage value of (d), output voltage V of auxiliary winding circuit 1124Or the output voltage V of the power supply circuit 1135Controls the capacitor in half-bridge circuit 1110 to stop discharging.
In one embodiment, the controller 114 controls the auxiliary power tube of the half-bridge circuit 1110 to be turned off, and the discharge circuit formed by the primary winding 1111 and the capacitor and the auxiliary power tube of the half-bridge circuit 1110 is disconnected. Accordingly, the capacitor in half-bridge circuit 1110 stops discharging.
In one embodiment, the dc converter circuit 111 comprises an AHB converter circuit, and the controller 114 controls the resonant capacitor C in the half-bridge circuit 1110rThe discharge is stopped. In one embodiment, the dc conversion circuit 111 comprises an ACF conversion circuit, and the controller 114 controls the clamping capacitor C in the half-bridge circuit 1110cThe discharge is stopped. In one embodiment, the half-bridge circuit 1110 of the dc converter circuit 111 further includes a plurality of capacitors, and the controller 114 controls the plurality of capacitors in the half-bridge circuit 1110 to stop discharging.
In a first embodiment, at t3T after the moment4At time, the capacitor voltage V of the capacitor in half-bridge circuit 1110cIs reduced to be less than or equal to the preset capacitance voltage value VC3. In one embodiment, controller 114 determines the capacitor voltage V of the capacitor in half-bridge circuit 1110 cIs reduced to be less than or equal to the preset capacitor voltage value VC3Controller 114 controls the capacitor in half-bridge circuit 1110 to stop discharging. In one embodiment, the preset capacitor voltage value VC3Can be greater than or equal to the voltage value V of the capacitor voltage of the capacitor in half-bridge circuit 1110 when DC-DC converter circuit 111 is in continuous operationC1. That is, controller 114 depends on the capacitance voltage V of the capacitor in half-bridge circuit 1110cAnd a predetermined capacitor voltage value VC3As a result of the comparison, the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging. Thus, controller 114 may control half-bridge circuit 1110The capacitor stops discharging, so that the direct current conversion circuit 111 is prevented from being influenced by too low capacitor voltage to recover a continuous working state, and the stability of the power module 11 and the electronic device 10 where the power module is located is further improved.
In a second embodiment, at t3T after the moment4At that moment, the output voltage V of the auxiliary winding circuit 1124The voltage value of the voltage is increased to be more than or equal to a fourth preset value V42. In one embodiment, the controller 114 determines the output voltage V of the auxiliary winding circuit 1124Is greater than or equal to a fourth preset value V42The controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging. Wherein the voltage value V is adjusted 42Is recorded as a fourth preset value, voltage value V42May be the highest input voltage of the power supply circuit 113. Voltage value V42Greater than the rated input voltage V of the power circuit 11340And is less than the over-voltage protection voltage of the power supply circuit 113. That is, the controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a fourth preset value V42As a result of the comparison, controller 114 controls the capacitor in half-bridge circuit 1110 to stop discharging. Therefore, the controller 114 can prevent the output voltage V of the auxiliary winding circuit 112 by controlling the capacitor in the half-bridge circuit 1110 to stop discharging4The voltage of the power supply circuit 113 and the controller 114 is too high, which further improves the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located.
In a third embodiment, at t3T after the moment4At that time, the output voltage V of the power supply circuit 1135The voltage value of the voltage is increased to be more than or equal to a fifth preset value V53Then (c) is performed. In one embodiment, the controller 114 determines the output voltage V of the power circuit 1135Is greater than or equal to a fifth preset value V53The controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging. Wherein the voltage value V is adjusted53Is recorded as a fifth preset value, voltage value V 53Greater than the rated input voltage V of the controller 11450And less than the overvoltage protection voltage of the controller 114. That is, the controller 114 is based on the output voltage V of the power supply circuit 1135Electricity (D) fromPressure value and fifth preset value V53As a result of the comparison, the controller 114 controls the capacitor in the half-bridge circuit 1110 to stop discharging. Therefore, the controller 114 can prevent the output voltage V of the power circuit 113 from being discharged by controlling the capacitor in the half-bridge circuit 1110 to stop discharging4The voltage of the power supply is too high to damage the controller 114, so that the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located is further improved.
At t4After the time, the capacitor in half-bridge circuit 1110 stops discharging, and the capacitor voltage VcStops decreasing in voltage value. Accordingly, the primary winding voltage V11Resulting in a drop in the voltage value of the auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
In one embodiment of the present application, at t4After the moment when the output voltage V of the auxiliary winding circuit 112 is reached4Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V 52Controller 114 may then control the capacitance of half-bridge circuit 1110 to discharge again. The specific process is as described in the above examples, and will not be repeated. That is, the controller 114 may be based on the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a second preset value V41Controls the capacitor of half-bridge circuit 1110 to discharge again as a result of the comparison. Alternatively, the controller 114 may be based on the output voltage V of the power supply circuit 1135Voltage value of (d) and a third preset value V52Controls the capacitor of half-bridge circuit 1110 to discharge again as a result of the comparison.
In an embodiment of the present application, the controller 114 further outputs the output voltage V of the dc conversion circuit 111 after the capacitor in the half-bridge circuit 1110 starts or stops discharging2The voltage value of (3) controls the operation state of the dc conversion circuit 111 to be switched from the suspended operation state to the continuous operation state. At t2After the time, the controller 114 controls the dc conversion circuit 111 to operate in the suspended state,accordingly, the output voltage V of the DC conversion circuit 1112The voltage value of (2) decreases. In one embodiment, the output voltage V of the dc converter circuit 111 is obtained after the capacitor in the half-bridge circuit 1110 starts to discharge and before the capacitor stops discharging2To a voltage value less than or equal to a rated voltage V 20The controller 114 controls the operation state of the dc conversion circuit 111 to be switched from the pause operation state to the continuous operation state. In one embodiment, the output voltage V of the DC-to-DC converter 111 is obtained after the capacitor in the half-bridge circuit 1110 stops discharging2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the dc conversion circuit 111 to be switched from the pause operation state to the continuous operation state.
At t3T after the moment of time5At that time, the output voltage V of the dc conversion circuit 1112To a voltage value less than or equal to the rated output voltage V20. The controller 114 determines the output voltage V of the dc conversion circuit 1112To a voltage value less than or equal to the rated output voltage V20The controller 114 controls the operation state of the dc conversion circuit 111 to be switched from the pause operation state to the continuous operation state. That is, the controller 114 is controlled according to the output voltage V of the DC conversion circuit 1112Voltage value of and rated output voltage V20As a result of the comparison, the controller 114 controls the operation state of the dc conversion circuit 111 to be switched from the pause operation state to the continuous operation state. That is, at t2After time t5Before the time, the controller 114 controls the dc conversion circuit 111 to operate in the pause state. At t 5After the time, the controller 114 controls the dc conversion circuit 111 to operate in the continuous operation state. At t5After the time point, the output voltage V of the dc conversion circuit 1112Is increased to a rated output voltage V20The output voltage V of the auxiliary winding circuit 1124Is raised to V40Output voltage V of power supply circuit 1135Is raised to V50。
In some embodiments of the present application, controller 114 may control the capacitance of capacitor in half-bridge circuit 1110The voltage value of the capacitor voltage is reduced to be less than VC1The discharge is stopped before, so that the operating state of the dc conversion circuit 111 can be switched from the suspended operating state to the continuous operating state more quickly, and therefore, the control 114 provided by the embodiment of the present application can improve the performance of the power module 11 and the electronic device 10 where the dc conversion circuit is located.
Fig. 9 is a schematic diagram of an embodiment of a power module provided in the present application. The power module 11 shown in fig. 9 can be applied to the electronic device 10 shown in fig. 1 or fig. 2. The power supply module 11 shown in fig. 9 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power supply circuit 113, and a controller 114. The AHB conversion circuit 111a is used for receiving the input voltage V of the input power supply 131And providing an output voltage V 2To power the load 12. In addition, the AHB conversion circuit 111a supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112. The auxiliary winding circuit 112 is coupled to the AHB conversion circuit 111a, and an auxiliary winding voltage V is generated on the auxiliary winding 11213. The auxiliary winding circuit 112 converts the auxiliary winding voltage V3Is converted into an output voltage V4And supplies power to the power supply circuit 113. The power supply circuit 113 supplies power to the control circuit 114. The controller 114 is used to control the operation state of the AHB conversion circuit 111 a.
Fig. 10 is a schematic diagram of an embodiment of a power module provided in the present application. As shown in fig. 10, the power module 11 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power supply circuit 113, and a controller 114. The AHB conversion circuit 111a in the power module 11 includes a half-bridge circuit 1110a, a transformer 1112a, and a rectifying circuit 1114 a. The transformer 1112a includes a primary winding 1111a and a secondary winding 1113 a. In addition, the transformer 1112a also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. Secondary winding 1113a is coupled to primary winding 1111a, and auxiliary winding 1121 is coupled to primary winding 1111 a.
Half-bridge circuit 1110a for receiving input voltage V provided by input power supply 13 1And provides an output voltage V to the primary winding 1111a according to a control signal of the controller 11410. Half-bridge circuit 1110a generally includes a main power transistor, an auxiliary power transistor, and a resonant capacitor.
Primary winding 1111a of transformer 1112a is configured to receive output voltage V of half-bridge circuit 1110a10And generates a primary winding voltage V11. A secondary winding 1113a of transformer 1112a is coupled to a primary winding 1111a of transformer 1112a, and a secondary winding voltage V is generated across secondary winding 1113a3。
The rectifying circuit 1114a is used for receiving the secondary winding voltage V on the secondary winding 1113a3And converted into an output voltage V2。
The auxiliary winding circuit 112 is used to power a power supply circuit 113. The auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111a of the transformer 1112 a. Primary winding voltage V on primary winding 1112a11Coupled to produce an auxiliary winding voltage V across auxiliary winding 11213. Auxiliary winding voltage V3Processed by the auxiliary winding circuit 112, provides an output voltage V to the power circuit 1134. The auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifying module 1122.
The power supply circuit 113 is used to supply power to the controller 114. The power supply circuit 113 receives the output voltage V of the auxiliary winding circuit 112 4And provides an output voltage V to the controller 1145. That is, the AHB converter circuit 111a supplies power to the power circuit 113 of the controller 114 via the auxiliary winding circuit 112 coupled to the primary winding 1111 of its transformer 1112 a. In some embodiments, the power circuit 113 includes a voltage regulation circuit.
The controller 114 is used to control the operation state of the AHB conversion circuit 111 a. The controller 114 is also used for detecting the output voltage V of the AHB conversion circuit 111a2The output voltage V of the auxiliary winding circuit 1124And the output voltage V of the power supply circuit 1135Or resonant capacitor C in half-bridge circuit 1110arVoltage of capacitor VCrThe voltage value of (d) and the like. The controller 114 is further configured to control the operation state of the AHB conversion circuit 111a according to the change of the one or more voltage values.
In one embodiment, the controller 114 sends a control signal G to control the operation state of the half-bridge 1110a in the AHB converter circuit 111a, thereby controlling the operation state of the AHB converter circuit 111 a. For example, the operation state of the AHB conversion circuit 111a generally includes a continuous operation state and a suspended operation state. The continuous operation state may also be referred to as a normal operation state, a controller normal wave generation state, and the like. The pause state may also be referred to as an intermittent operation state, a BURST operation state, a controller intermittent wave state, or the like.
In the embodiment of the present application, the controller 114 can send the control signal G to control the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a to turn on and off. The controller 114 adjusts the frequency or duty ratio of the control signal G to control the conduction frequency or conduction duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110a, so as to adjust the output voltage V of the half-bridge circuit 1110a accordingly10. Output voltage V of half-bridge circuit 1110a10Will result in a primary winding voltage V11And (4) changing. Accordingly, the primary winding voltage V11The variation may result in a secondary winding voltage V12And an auxiliary winding voltage V3And (4) changing. Accordingly, the secondary winding voltage V12Can result in the output voltage V of the AHB conversion circuit 111a2And (4) changing. Accordingly, the auxiliary winding voltage V3May result in the output voltage V of the auxiliary winding circuit 1124And (4) changing. Accordingly, the output voltage V of the auxiliary winding circuit 1124Can result in an output voltage V of the power supply 1135A change in (c).
As shown in the direction of F1 in FIG. 10, the AHB conversion circuit 111a may provide an output voltage V2To power the load 12. Wherein the input voltage V1The voltage is converted into an output voltage V through a half-bridge circuit 1110a, a primary winding 1111a, a secondary winding 1113a and a rectifying circuit 1114a in the AHB conversion circuit 111a 2。
As shown in the direction of F2 in fig. 10, the AHB conversion circuit 111a can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112. Wherein the input voltage V1After being processed by the half-bridge circuit 1110a in the AHB conversion circuit 111a, the primary winding 1111a can generate a primary winding voltage V11. Accordingly, the primary winding voltage V11An auxiliary winding may be generated on auxiliary winding 1121 of transformer 1112aGroup voltage V3. Auxiliary winding voltage V3Processed by an auxiliary winding circuit 1121 to provide an output voltage V4And supplies power to the power supply circuit 113 of the controller 114.
Fig. 11 is a schematic voltage waveform diagram of a controller and a power module in which the controller is provided in the present application in a situation where a load level falls. The following describes in detail the operation process of the controller 114 and the power module 11 thereof in a scenario where the load level L of the load 12 falls, with reference to fig. 10 and fig. 11.
At t1Before the moment, the load level L of the load 12 is the normal load L1The controller 114 controls the AHB conversion circuit 111a to operate in a continuous operation state, and the controller 114 controls the output voltage V of the AHB conversion circuit 111a2The voltage value of (A) is rated output voltage V20. Output voltage V of auxiliary winding circuit 112 4Has a voltage value of V40. Output voltage V of power supply circuit 1135Has a voltage value of V50. Resonant capacitor C in half-bridge circuit 1111arVoltage of capacitor VCrHas a voltage value of VCr1。VCr1Resonant capacitor C for AHB conversion circuit 111a to operate in continuous working staterThe capacitor voltage of (c).
At t1At that moment, the load level of the load 12 is changed from the normal load L1Drop to light load L2. Accordingly, at t1After the time, the output voltage V of the AHB conversion circuit 111a2The voltage value of the voltage is increased to be larger than the rated output voltage V20。
In one embodiment, the output voltage V of the AHB conversion circuit 111a is set as2Has a voltage value greater than the rated output voltage V20The controller 114 can control the AHB conversion circuit 111a to operate in a continuous operation state. The controller controls the AHB conversion circuit 111a to lower the output voltage V2The voltage value of (2). That is, the controller 114 converts the output voltage V of the circuit 111a according to AHB2Voltage value of and rated output voltage V20As a result of the comparison, the controller 114 controls the AHB conversion circuit 111a to operate in a continuous operation state, and the controller 114 controls the AHB conversion circuit 111a to reduce the outputVoltage V2The voltage value of (2). Specifically, the controller 114 sends a control signal G to control the operation states of the main power tube and the auxiliary power tube in the half-bridge circuit 1110a, so that the primary winding voltage V is obtained 11The voltage value of (2) decreases. In one embodiment, the controller 114 may decrease the transmission frequency of the control signal G, thereby decreasing the conduction frequency of the main power transistor and the auxiliary power transistor. In one embodiment, the controller 114 may decrease the duty cycle of the control signal G, thereby decreasing the conduction time of the main power transistor and the auxiliary power transistor. In another embodiment, when the output voltage V of the AHB conversion circuit 111a is being converted to the voltage V2Is greater than the rated voltage V20The controller 114 can control the AHB conversion circuit 111a to operate in a suspended state, and can also reduce the output voltage V2The voltage value of (2). However, both of the above embodiments may not enable the output voltage V of the AHB conversion circuit 111a2Is effectively reduced at t1Output voltage V of AHB conversion circuit 111a after the time2Will continue to rise.
At the same time, at t1After the time, the drop in the load level L causes the output voltage V of the AHB conversion circuit 111a2Has a voltage value higher than the rated voltage V20. Primary winding voltage V11For resonant capacitor C in half-bridge circuit 1110arCharging, resonant capacitor C in half-bridge circuit 1110arVoltage of capacitor VCrVoltage value of from VCr1Is lifted to VCr2。VCr2Is a resonant capacitor C in half-bridge circuit 1110a rThe maximum charging voltage of.
At t1T after the moment of time2At this time, the output voltage V of the AHB conversion circuit 111a2The voltage value is increased to a first preset value V21. The controller 114 determines the output voltage V of the AHB conversion circuit 111a2Is greater than or equal to a first preset value V21The controller 114 controls the AHB conversion circuit 111a to suspend operation. That is, the controller 114 converts the output voltage V of the circuit 111a according to AHB2Voltage value of (d) and a first predetermined value V21As a result of the comparison, the controller 114 controls the AHB conversion circuit 111a to operate in the suspended state. In particularThe controller 114 controls the main power transistor and the auxiliary power transistor of the half-bridge circuit 1110a to be turned off. In the embodiment of the present application, the first preset value V21May be the peak voltage of the AHB conversion circuit 111 a. The peak voltage of the AHB conversion circuit 111a is greater than the rated voltage V20And is smaller than the overvoltage protection voltage of the AHB conversion circuit 111 a.
At t2After that time, the controller 114 controls the AHB conversion circuit 111a to operate in the suspended state. Accordingly, the primary winding voltage V on the primary winding 1111a in the AHB conversion circuit 111a11Resulting in a secondary winding voltage V12Drop and result in an auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the AHB conversion circuit 111a 2The voltage value of (2) decreases, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
At t2T after time3At that moment, the output voltage V of the auxiliary winding circuit 1124Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V52. At this time, the controller 114 controls the resonant capacitor C in the half-bridge circuit 1110arAnd (4) discharging.
In one embodiment, the controller 114 determines the output voltage V of the auxiliary winding circuit 1124Is less than or equal to a second preset value V41Controller 114 controls resonant capacitor C in half-bridge circuit 1110arAnd (4) discharging. That is, the controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a second predetermined value V41Controls the resonant capacitor C in half-bridge circuit 1110a as a result of the comparisonrAnd (4) discharging.
In one embodiment, the controller 114 determines the output voltage V of the power circuit 1135Is less than or equal to a third predetermined value V52Controller 114 controls resonant capacitor C in half-bridge circuit 1110arAnd (4) discharging. That is, the controller 114 is based on the output voltage V of the power supply circuit 1135Voltage value of (d) and a third predetermined value V 52As a result of the comparison, controller 114 controls resonant capacitor C in half-bridge circuit 1110arAnd (4) discharging.
In one embodiment, controller 114 controls the conduction of the auxiliary power transistor in half-bridge circuit 1110a, so that the resonant capacitor C in half-bridge circuit 1110arAnd (4) discharging. Resonant capacitor C of primary winding 1111a and half-bridge circuit 1110arThe auxiliary power transistor of half bridge 1110a may form a discharge loop. Accordingly, resonant capacitor C of half-bridge circuit 1110arDischarge, producing a primary winding voltage V on the primary winding 1111a11。
In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110a to be periodically turned on, so that the resonant capacitor C in the half-bridge circuit 1110arAnd (4) discharging. When the auxiliary power tube of the half-bridge circuit 1110a is turned on, the primary winding 1111a and the resonant capacitor C of the half-bridge circuit 1110arThe auxiliary power transistor of half-bridge circuit 1110a may form a discharge circuit. Accordingly, the auxiliary power transistor of half-bridge circuit 1110a is periodically turned on, so that the resonant capacitor C in half-bridge circuit 1110arIs discharged periodically.
At t3After time, resonant capacitor C in half-bridge circuit 1110arVoltage of capacitor VCrThe voltage value of (2) decreases. Resonant capacitor C in half-bridge circuit 1110a rDischarge so that the primary winding voltage V on the primary winding 1111a11The voltage value of (2) is raised. Accordingly, the primary winding voltage V11The voltage value of (2) is increased, which results in an auxiliary winding voltage V3The voltage value of (2) is raised. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased5The voltage value of (2) is raised. Therefore, in a scene where the load level of the load 12 changes, the output voltage V of the power supply circuit 1135Does not drop below the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection.
The controller 114 provided in the embodiment of the present application controls the half-bridge circuit of the AHB conversion circuit 111a1110a resonant capacitor CrDischarge, the output voltage V of the power supply circuit 113 can be made5Is higher than the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
Due to the resonant capacitor C in the half-bridge circuit 1110a of the AHB conversion circuit 111arLimited energy stored, primary winding voltage V generated on primary winding 1111a after discharge 11The voltage value of (2) is small. At this time, a primary winding voltage V is generated at the primary winding 1111a11Is less than the secondary winding voltage V on the secondary winding 111312Without causing the output voltage V of the AHB conversion circuit 111a2And (5) lifting. Thus, controller 114 controls resonant capacitor C in half-bridge circuit 1110arAfter discharge, the voltage V of the primary winding generated on the primary winding 1111a11For boosting the output voltage V of the auxiliary winding circuit 112 only4And the output voltage V of the power supply circuit 1135As shown in the direction of F2 in fig. 10. Therefore, the controller 114 and the power module 111 thereof provided in the embodiment of the present application can not only prevent the controller 114 from being restarted due to under-voltage protection, but also prevent the output voltage V of the AHB conversion circuit 111a from being increased2The ripple of (2) can improve the stability of the power module 11 and the electronic device 10 in which the controller 114 is located.
Furthermore, the controller 114 provided in the embodiment of the present application controls the resonant capacitor C in the half-bridge circuit 1110a of the AHB conversion circuit 111arNoise from the input power supply 13 is not introduced, and the influence of noise on the electromagnetic compatibility of the AHB conversion circuit 111a, the power supply module 11 in which the AHB conversion circuit is located, and the electronic device 10 can be avoided. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
In one embodiment of the present application, the resonant capacitor C is disposed in the half-bridge circuit 1110a of the AHB conversion circuit 111arAfter the discharge is initiated, the controller 114 can also adjust the resonant capacitance C of the half-bridge circuit 1110arVoltage of capacitor VCrElectricity (D) fromVoltage value, output voltage V of auxiliary winding circuit 1124Or the output voltage V of the power supply circuit 1135Controls the resonant capacitor C in half-bridge circuit 1110arThe discharge is stopped. In one embodiment, the controller 114 controls the auxiliary power tube in the half-bridge circuit 1110a to be turned off, and the primary winding 1111a and the resonant capacitor C of the half-bridge circuit 1110arThe discharge circuit formed by the auxiliary power tube of half-bridge circuit 1110a is open. Accordingly, resonant capacitor C of half-bridge circuit 1110arThe discharge is stopped.
In a first embodiment, at t3T after the moment4At time, resonant capacitor C of half-bridge circuit 1110arVoltage of capacitor VCrIs reduced to be less than or equal to the preset capacitance voltage value VCr3. In one embodiment, controller 114 determines resonant capacitance C of half-bridge circuit 1110arVoltage of capacitor VCrIs reduced to be less than or equal to the preset capacitance voltage value VCr3Controller 114 controls resonant capacitor C of half-bridge circuit 1110arThe discharge is stopped. In one embodiment, the preset capacitor voltage value V Cr3The resonant capacitance C of the half-bridge circuit 1110a can be greater than or equal to that of the AHB conversion circuit 111a when the AHB conversion circuit is operated in the continuous operation staterVoltage value V of the capacitor voltageCr1. That is, controller 114 depends on resonant capacitance C of half-bridge circuit 1110arVoltage of capacitor VCrAnd a predetermined capacitor voltage value VCr3As a result of the comparison, the controller 114 controls the resonant capacitor C of the half-bridge circuit 1110arThe discharge is stopped. Thus, controller 114 may pass through resonant capacitor C of half-bridge circuit 1110arStopping discharge to avoid the resonance capacitor CrVoltage of capacitor VCrThe continuous operation of the AHB conversion circuit 111a is affected by too low voltage, which further improves the stability of the power module 11 and the electronic device 10 in which the power module is located.
In a second embodiment, at t3T after the moment4At that moment, the output voltage V of the auxiliary winding circuit 1124The voltage value of the voltage is increased to be more than or equal to a fourth preset value V42. In one embodiment, the controller 114 determines the auxiliary winding circuit 112Output voltage V4Is greater than or equal to a fourth preset value V42Controller 114 controls resonant capacitor C of half-bridge circuit 1110arThe discharge is stopped. That is, the controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a fourth preset value V 42As a result of the comparison, controller 114 controls resonant capacitor C of half-bridge circuit 1110arThe discharge is stopped. Thus, controller 114 may pass through resonant capacitance C of half-bridge circuit 1110arStopping the discharge can prevent the output voltage V of the auxiliary winding circuit 1124The power circuit 113 and the controller 114 are damaged due to the excessive voltage, and the stability of the controller 114, the power module 11 and the electronic device 10 in which the controller is located is further improved.
In a third embodiment, at t3T after the moment of time4At that time, the output voltage V of the power supply circuit 1135Is increased to be greater than or equal to a fifth preset value V53When the user wants to use the device. In one embodiment, the controller 114 determines the output voltage V of the power circuit 1135Is greater than or equal to a fifth preset value V53Controller 114 controls resonant capacitor C of half-bridge circuit 1110arThe discharge is stopped. That is, the controller 114 is based on the output voltage V of the power supply circuit 1135Voltage value of (d) and a fifth predetermined value V53As a result of the comparison, the controller 114 controls the resonant capacitor C of the half-bridge circuit 1110arThe discharge is stopped. Thus, controller 114 may control resonant capacitance C of half-bridge circuit 1110a by controllingrStopping discharge to avoid the output voltage V of the power circuit 1134The voltage of the power supply is too high to damage the controller 114, so that the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located is further improved.
At t4After the time, the resonant capacitor Cr of the half-bridge circuit 1110a stops discharging, and the resonant capacitor CrVoltage of capacitor VCrStops decreasing in voltage value. Accordingly, the primary winding voltage V11Resulting in a drop in the voltage value of the auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
In one embodiment of the present application, at t4After the moment when the output voltage V of the auxiliary winding circuit 112 is reached4Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V52When desired, controller 114 may control resonant capacitor C of half-bridge circuit 1110arAnd discharging again. The specific process is as described in the above examples, and will not be repeated. That is, the controller 114 may be based on the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a second predetermined value V41Controls the resonant capacitance C of half-bridge circuit 1110arAnd discharging again. Alternatively, the controller 114 may be based on the output voltage V of the power supply circuit 1135Voltage value of (d) and a third predetermined value V52Controls the resonant capacitance C of half-bridge circuit 1110a rAnd discharging again.
In one embodiment of the present application, the resonant capacitor C of half-bridge circuit 1110arAfter the discharge is started or stopped, the controller 114 also converts the output voltage V of the AHB conversion circuit 111a according to the voltage2The voltage value of (3) controls the operation state of the AHB conversion circuit 111a to be switched from the suspended operation state to the continuous operation state. At t2After the moment, the controller 114 controls the AHB conversion circuit 111a to operate in the suspended state, and accordingly the output voltage V of the AHB conversion circuit 111a2The voltage value of (2) decreases. In one embodiment, resonant capacitor C in half-bridge circuit 1110arAfter the start of discharge and before the stop of discharge, the output voltage V of the AHB conversion circuit 111a2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the AHB conversion circuit 111a to be switched from the suspended operation state to the continuous operation state. In one embodiment, resonant capacitor C in half-bridge circuit 1110arAfter stopping discharging, the output voltage V of the AHB conversion circuit 111a2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the AHB conversion circuit 111a to be switched from the suspended operation state to the continuous operation state.
At t3T after the moment5At that time, the output voltage V of the AHB conversion circuit 111a 2To a voltage value less than or equal to a rated voltage V20. The controller 114 determines the output voltage V of the AHB conversion circuit 111a2To a voltage value less than or equal to a rated voltage V20The operation state of the AHB conversion circuit 111a is controlled to be switched from the suspended operation state to the continuous operation state. That is, the controller 114 converts the output voltage V of the AHB conversion circuit 111a into the output voltage V2Voltage value of (d) and rated voltage V20Controls the AHB conversion circuit 111a to switch the operation state from the suspended operation state to the continuous operation state. At t5After the time, the output voltage V of the AHB conversion circuit 111a2Is restored to the rated voltage V20The output voltage V of the auxiliary winding circuit 1124Is restored to V40Output voltage V of power supply circuit 1135Is restored to V50。
Fig. 12 is a schematic diagram of an embodiment of a power module provided in the present application. Fig. 12 is a schematic diagram showing a part of the circuit in the power module 11 shown in fig. 10. As shown in fig. 12, the power module 11 includes an AHB conversion circuit 111a, an auxiliary winding circuit 112, a power supply circuit 113, and a controller 114. The AHB converter circuit 111a includes a half-bridge circuit 1110a, a transformer 1112a, and a rectifier circuit 1114 a. The transformer 1112a includes a primary winding 1111a and a secondary winding 1113 a. In addition, the transformer 1112a also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. Secondary winding 1113a is coupled to primary winding 1111a, and auxiliary winding 1121 is coupled to primary winding 1111 a.
Half-bridge circuit 1110a includes main power transistor QLAnd an auxiliary power tube QHAnd a resonant capacitor Cr. Main power tube QLAnd an auxiliary power tube QHAnd a resonant capacitor CrAn asymmetric half-bridge topology is formed. In particular, a resonant capacitance CrIs connected with the different name end of the primary winding 1111a, and a resonant capacitor CrIs connected with an auxiliary power tube QHOf the substrate. Auxiliary power tube QHSource electrode ofDotted terminal of winding 1111a and main power tube QLOf the substrate. Main power tube QLIs grounded. In one embodiment, the main power transistor QLIs used for receiving a second control signal G of the controller 114H. Auxiliary power tube QHIs used for receiving a first control signal G of the controller 114L。
The rectifying circuit 1114a includes a capacitor C1And a diode D2. Diode D2Is connected to the dotted terminal of the secondary winding 1113 a. Capacitor C1Are respectively connected with a diode D2And the opposite terminal of the secondary winding 1113 a.
The auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectification module 1122. The rectification module 1122 may include a diode D1. Wherein, the diode D1Is connected to the dotted terminal of auxiliary winding 1121, diode D1And the opposite end of the auxiliary winding 1121 is connected to the power supply circuit 113.
The power circuit 113 may include a BOOST (BOOST) circuit. In one embodiment, the power circuit 113 may also be a BUCK (BUCK) circuit, a BUCK-BOOST (BUCK-BOOST) circuit, or the like. In one embodiment, the power circuit 113 may also be a low dropout regulator (LDO) or other voltage regulator.
The controller 114 includes a detection unit 1141 and a driving unit 1142. In some embodiments, when the driving unit 1142 is a chip, the power circuit 113 may be connected to a power supply pin of the driving unit 1142. For example, the supply pin may be the reference "V" shown in FIG. 12dd"of the substrate.
The detecting unit 1141 is used for detecting the output voltage V of the AHB converting circuit 111a2 Auxiliary winding circuit 1124Voltage value of (d), output voltage V of power supply circuit 1135Voltage value of or a resonant capacitor C in a half-bridge circuit 1110a of the AHB conversion circuit 111arVoltage of capacitor VCrA variation of a plurality of voltage values. The driving circuit 1142 is used for controlling the operation state of the AHB converting circuit 111a according to the change of the one or more voltage values.
For example, the detection unit 1141 may detect the output voltage V of the AHB conversion circuit 111a through a point a connected to the output terminal of the secondary winding circuit 1114a in fig. 12 2The voltage value of (2). The detection unit 1141 may detect the output voltage V of the auxiliary winding circuit 112 via the point B connected to the output terminal of the auxiliary winding circuit 112 in fig. 124The voltage value of (2). The detection unit 1141 may detect the output voltage V of the power circuit 113 through a point C connected to the output terminal of the power circuit 113 in fig. 125The voltage value of (2). The detecting unit 1141 may be connected to the resonant capacitor C in FIG. 12rDetecting a resonant capacitance C at a point D on either siderVoltage of capacitor VCrThe voltage value of (2).
The driving unit 1142 is used to control the operation state of the AHB conversion circuit 111 a. Wherein, the driving unit 1142 sends out a control signal GL/GHControlling the main power transistor QLAnd an auxiliary power tube QHThereby controlling the operation state of the AHB conversion circuit 111 a. In some embodiments, when the driving unit 1142 is a chip, the driving unit 1142 shown in fig. 12 may be denoted by its reference numeral "GH' the pin sends out a control signal GHMay be given by its reference numeral "GL' the pin sends out a control signal GL. The reference numbers of the pins in fig. 12 are only examples, and the pins of other reference numbers of the driving unit 1142 may be used to realize the functions of the pins shown in fig. 12 in practical applications.
The driving unit 1142 supplies power to the main power tube Q LSending a first control signal GLControl the main power tube QLOn or off. The driving unit 1142 drives the auxiliary power tube QHSending a second control signal GHControl the auxiliary power tube QHOn or off. In the embodiment of the present application, the first control signal G sent by the controller 114LA second control signal GHAnd may include high level signals or low level signals, etc. In one embodiment, the main power transistor QLAccording to the first control signal GLConducting auxiliary power tube QHAccording to the second control signal GHAnd conducting. In a kind of implementationIn the example, the main power tube QLAccording to the first control signal GLTurn-off, auxiliary power tube QHAccording to the second control signal GHAnd (6) turning off.
Fig. 13 is a schematic diagram of a control signal of the controller provided in the present application in a situation where a load level of the power module is dropped. The following describes, with reference to fig. 11, 12 and 13, an operation process of the controller 114 and the power module 11 thereof provided in the present application in a scenario where the load level L of the load 12 falls.
Before time t1, the load level of load 12 is normal load L1. The controller 114 controls the AHB conversion circuit 111a to operate in a continuous operation state, and controls the output voltage V of the AHB conversion circuit 111a 2Has a voltage value of rated voltage V20. At this time, the output voltage V of the auxiliary winding circuit 1124Has a voltage value of V40. Output voltage V of power supply circuit 1135Has a voltage value of V50. Resonant capacitor C in half-bridge circuit 1111arVoltage of capacitor VCrHas a voltage value of VCr1。
Fig. 14 is a schematic diagram of a control signal of a controller according to an embodiment of the present application. As shown in FIG. 14, the control signal G sent by the controller 1141、G2、G3… each includes a main power transistor QLThe transmitted first control signal GLOr to the auxiliary power tube QHSecond control signal G sentH. The controller 114 controls the main power transistor QLAnd an auxiliary power tube QHPeriodically and alternately turned on and off, the half-bridge circuit 1110a can generate a primary winding voltage V at the primary winding 1111a11. Primary winding voltage V on primary winding 1111a11Coupled, a secondary winding voltage V can be generated across secondary winding 1113a12And may generate an auxiliary winding voltage V across auxiliary winding 11213. Accordingly, the rectifying circuit 1114a supplies the output voltage V to the load 122The auxiliary winding circuit 112 supplies the output voltage V to the power supply circuit 1134The output voltage V of the power supply circuit 113 to the controller 1155Is a V50. Due to AHB conversion circuit111a to load 12 2Is stabilized at a rated voltage V20Resonant capacitor C in half-bridge circuit 1110arVoltage value V ofCrStabilized at VCr1。
At time t1, the load level of load 12 is changed from normal load L1Drop to light load L2. After time t1, the output voltage V of the AHB conversion circuit 111a2Is increased to be larger than the rated voltage V20。
In one embodiment, the controller 114 converts the output voltage V of the AHB conversion circuit 111a according to2Voltage value of (d) and rated voltage V20The comparison result of (1) controls the AHB conversion circuit 111a to operate in a continuous working state, and the controller 114 controls the AHB conversion circuit 111a to reduce the output voltage V2The voltage value of (2).
Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the AHB conversion circuit 111a2And determines the output voltage V of the AHB conversion circuit 111a2Greater than rated voltage V20. Accordingly, the controller 114 controls the AHB conversion circuit 111a to operate in the continuous operation state, and the controller 114 decreases the first control signal GLAnd a second control signal GHOr reducing the first control signal GLAnd a second control signal GHThe duty cycle of (c). As shown in fig. 13, at t1Control signal G sent by controller 114 after a time4、G5、G6Is less than t1Control signal G periodically transmitted before time 1、G2、G3Of the frequency of (c). Accordingly, the main power tube QLAnd an auxiliary power tube QHThe frequency of on and off is reduced so that the output voltage V of the AHB conversion circuit 111a is reduced2The voltage value of (2) decreases. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases. However, the above-mentioned method may not enable the output voltage V of the AHB conversion circuit 111a2The voltage value of (a) is effectively reduced, and the output voltage V of the AHB conversion circuit 111a2Will continue to rise.
At t1After the time, the output voltage V of the AHB conversion circuit 111a2Has a voltage value higher than the rated voltage V20. At this time, the primary winding voltage V11For resonant capacitor C in half-bridge circuit 1110arCharging, resonant capacitor C in half-bridge circuit 1110arVoltage of capacitor VCrVoltage value of from VCr1Is lifted to VCr2。
At t1T after the moment2At that time, the output voltage V of the AHB conversion circuit 111a2The voltage value of the voltage is increased to be more than or equal to a first preset value V21. The controller 114 converts the output voltage V of the circuit 111a according to AHB2Voltage value of (d) and a first predetermined value V21As a result of the comparison, the controller 114 controls the AHB conversion circuit 111a to operate in the suspended state. Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the AHB conversion circuit 111a 2And determines the output voltage V of the AHB conversion circuit 111a2Is greater than or equal to a first preset value V21. Accordingly, the driving unit 1142 of the controller 114 stops transmitting the first control signal GLAnd a second control signal GHThereby controlling the AHB conversion circuit 111a to operate in the suspended operation state. Accordingly, the input voltage V that the AHB conversion circuit 111a does not receive to it1Processed, the output voltage V of the AHB conversion circuit 111a2And (4) reducing.
At t2After that time, the controller 114 controls the AHB conversion circuit 111a to operate in the suspended state. Accordingly, the primary winding voltage V on the primary winding 1111a in the AHB conversion circuit 111a11Resulting in a secondary winding voltage V12Drop and result in an auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the AHB conversion circuit 111a2The voltage value of (2) decreases, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
At t2T after time3At that moment, the output voltage V of the auxiliary winding circuit 1124To a voltage value lower thanSecond preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be lower than a third preset value V 52. At this time, controller 114 controls resonant capacitor C in half-bridge circuit 1110arAnd (4) discharging.
In one embodiment, the detection unit 1141 of the controller 114 detects the output voltage V of the auxiliary winding circuit 1124And determines the output voltage V of the auxiliary winding circuit 1124Is less than or equal to a second preset value V41. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd conducting. At this time, the resonant capacitor C of half-bridge circuit 1110arPower tube Q of primary winding 1111a and half-bridge circuit 1110aHResonant capacitor C forming a discharge circuit, half-bridge circuit 1110arThe discharge is started.
In one embodiment, the detection unit 1141 of the controller 114 detects the output voltage V of the power circuit 1135And determines the output voltage V of the power supply circuit 1135Is less than or equal to a third predetermined value V52. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd conducting. At this time, resonant capacitor C of half-bridge circuit 1110arPower tube Q of primary winding 1111a and half-bridge circuit 1110aHResonant capacitor C forming a discharge circuit, half-bridge circuit 1110arThe discharge is started.
At t3After time, resonant capacitor C in half-bridge circuit 1110a rVoltage of capacitor VCrThe voltage value of (2) decreases. Resonant capacitor C in half-bridge circuit 1110arDischarge so that the primary winding voltage V on the primary winding 1111a11The voltage value of (2) is raised. Accordingly, the auxiliary winding voltage V3The voltage value of (2) is raised, and the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased5The voltage value of (2) is raised. Therefore, in a scene where the load level of the load 12 changes, the output voltage V of the power supply circuit 1135Does not drop below the under-voltage protection of the controller 114Voltage V51Thereby avoiding the controller 114 from restarting due to low voltage protection.
The controller 114 provided in the embodiment of the present application controls the resonant capacitor C in the half-bridge circuit 1110a of the AHB conversion circuit 111arDischarge, the output voltage V of the power supply circuit 113 can be made5Is higher than the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
Due to the resonant capacitor C in the half-bridge circuit 1110a of the AHB conversion circuit 111arLimited energy stored, primary winding voltage V generated on primary winding 1111a after discharge 11The voltage value of (2) is small. At this time, a primary winding voltage V is generated at the primary winding 1111a11Is less than the secondary winding voltage V on the secondary winding 111312Without causing the output voltage V of the AHB conversion circuit 111a2And (5) lifting. Thus, controller 114 controls resonant capacitor C in half-bridge circuit 1110arAfter discharge, a primary winding voltage V is generated on the primary winding 1111a11For boosting the output voltage V of the auxiliary winding circuit 112 only4And the output voltage V of the power supply circuit 1135. Therefore, the controller 114 and the power module 111 thereof provided in the embodiment of the present application can not only prevent the controller 114 from being restarted due to under-voltage protection, but also prevent the output voltage V of the AHB conversion circuit 111a from being increased2The ripple of (2) can improve the stability of the power module 11 and the electronic device 10 in which the controller 114 is located.
Furthermore, the controller 114 provided in the embodiment of the present application controls the resonant capacitor C in the half-bridge circuit 1110a of the AHB conversion circuit 111arNoise from the input power supply 13 is not introduced, and the influence on the electromagnetic compatibility of the AHB conversion circuit 111a, the power supply module 11 in which the AHB conversion circuit is located, and the electronic device 10 can be avoided. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
In one embodiment of the present application, the controller 114 may also controlResonant capacitor C in half-bridge circuit 1110a of AHB conversion circuit 111arThe discharge is stopped.
In a first embodiment, at t3T after the moment of time4At time, resonant capacitor C of half-bridge circuit 1110arVoltage of capacitor VCrIs reduced to be less than or equal to the preset capacitance voltage value VCr3. In one embodiment, the preset capacitor voltage value VCr3The resonant capacitance C of the half-bridge circuit 1110a can be greater than or equal to that of the AHB conversion circuit 111a when the AHB conversion circuit is operated in the continuous operation staterVoltage value V of the capacitor voltageCr1. Controller 114 depends on resonant capacitance C of half-bridge circuit 1110arVoltage of capacitor VCrAnd a predetermined capacitor voltage value VCr3As a result of the comparison, the controller 114 controls the resonant capacitor C of the half-bridge circuit 1110arThe discharge is stopped. Specifically, the detection unit 1141 of the controller 114 detects the resonant capacitance C of the half-bridge circuit 1110arVoltage of capacitor VCrAnd determines the resonant capacitance C of half-bridge circuit 1110arVoltage of capacitor VCrLess than or equal to the preset capacitor voltage value VCr3. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd (6) turning off. At this time, resonant capacitor C of half-bridge circuit 1110arPower tube Q of primary winding 1111a and half-bridge circuit 1110a HThe formed discharge circuit is opened, and the resonant capacitor C of the half-bridge circuit 1110arThe discharge is stopped.
Thus, controller 114 may pass through resonant capacitor C of half-bridge circuit 1110arStopping discharge to avoid the resonance capacitor CrVoltage of capacitor VCrThe continuous operation of the AHB conversion circuit 111a is affected by too low voltage, which further improves the stability of the power module 11 and the electronic device 10 in which the power module is located.
In a second embodiment, at t3T after the moment4At that moment, the output voltage V of the auxiliary winding circuit 1124The voltage value of the voltage is increased to be more than or equal to a fourth preset value V42. The controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a fourth preset value V42Comparison ofAs a result, controller 114 controls resonant capacitor C of half-bridge circuit 1110arThe discharge is stopped. Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the auxiliary winding circuit 1124And determines the output voltage V of the auxiliary winding circuit 1124Is less than or equal to the preset capacitor voltage value VCr3. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd (6) turning off. At this time, resonant capacitor C of half-bridge circuit 1110arPower tube Q of primary winding 1111a and half-bridge circuit 1110a HThe resulting discharge circuit is open and resonant capacitor C of half-bridge circuit 1110a is closedrThe discharge is stopped.
Thus, controller 114 may pass through resonant capacitance C of half-bridge circuit 1110arStopping the discharge can prevent the output voltage V of the auxiliary winding circuit 1124The voltage of the power supply circuit 113 and the controller 114 is too high, which further improves the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located.
In a third embodiment, at t3T after the moment of time4At that time, the output voltage V of the power supply circuit 1135The voltage value of the voltage is increased to be more than or equal to a fifth preset value V53. The controller 114 is controlled according to the output voltage V of the power circuit 1135Voltage value of (d) and a fifth predetermined value V53As a result of the comparison, the controller 114 controls the resonant capacitor C of the half-bridge circuit 1110arThe discharge is stopped. Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the power supply circuit 1135And determines the output voltage V of the power supply circuit 1135Is greater than or equal to a fifth preset value V53. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd (6) turning off. At this time, resonant capacitor C of half-bridge circuit 1110arPower tube Q of primary winding 1111a and half-bridge circuit 1110a HThe resulting discharge circuit is open and resonant capacitor C of half-bridge circuit 1110a is closedrThe discharge is stopped.
Thus, controller 114 may control the resonant capacitance of half-bridge circuit 1110a by controllingCrStop discharging to avoid the output voltage V of the power circuit 1134The voltage of the power supply is too high to damage the controller 114, so that the stability of the controller 114 and the power module 11 and the electronic device 10 in which the controller is located is further improved.
At t4After a moment, resonant capacitor C of half-bridge circuit 1110arAfter stopping discharging, the resonant capacitor CrVoltage of capacitor VCrThe voltage value of (2) stops decreasing. Accordingly, the primary winding voltage V11Resulting in a drop in the voltage value of the auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
In one embodiment of the present application, at t4After the moment when the output voltage V of the auxiliary winding circuit 112 is reached4Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V52When desired, controller 114 may control resonant capacitor C of half-bridge circuit 1110arAnd discharging again. The specific process is as described in the above examples, and will not be repeated.
In one embodiment of the present application, resonant capacitor C in half-bridge circuit 1110arAfter the discharge is started or stopped, the controller 114 also converts the output voltage V of the AHB conversion circuit 111a according to the voltage2The voltage value of (3) controls the operation state of the AHB conversion circuit 111a to be switched from the suspended operation state to the continuous operation state. At t2After the moment, the controller 114 controls the AHB conversion circuit 111a to operate in the suspended state, and accordingly the output voltage V of the AHB conversion circuit 111a2The voltage value of (2) decreases. In one embodiment, resonant capacitor C in half-bridge circuit 1110arAfter the start of discharge and before the stop of discharge, the output voltage V of the AHB conversion circuit 111a2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the AHB conversion circuit 111a to be switched from the suspended operation state to the continuous operation state. In one embodiment, resonant capacitor C in half-bridge circuit 1110arAfter stopping discharging, the output voltage V of the AHB conversion circuit 111a2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the AHB conversion circuit 111a to be switched from the suspended operation state to the continuous operation state.
At t3T after the moment5At that time, the output voltage V of the AHB conversion circuit 111a 2To a voltage value less than or equal to the rated output voltage V20. The controller 114 converts the output voltage V of the circuit 111a according to AHB2Voltage value of and rated output voltage V20Controls the AHB conversion circuit 111a to switch the operation state from the suspended operation state to the continuous operation state. Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the AHB conversion circuit 111a2And determines the output voltage V of the AHB conversion circuit 111a2Is less than or equal to the rated output voltage V20. The driving unit 1142 of the controller 114 periodically transmits the first control signal GLAnd a second control signal GHControlling the main power tube QLAnd an auxiliary power tube QHAnd is periodically turned on and off, so that the AHB conversion circuit 111a is restored to the continuous operation state. At this time, the controller 114 sends a first control signal GLAnd a second control signal GHIs marked as G7、G8、G9… are provided. Each control signal G7、G8、G9… are the same as those shown in FIG. 14 and will not be described in detail. Also for example, the control signal G7、G8、G9… may also be synchronized with the control signal G1、G2、G3… …, or with the same period as G4、G5、G6… … are equal in period. At t5After the time, the output voltage V of the AHB conversion circuit 111a2Is restored to the rated output voltage V 20The output voltage V of the auxiliary winding circuit 1124Is restored to V40Output voltage V of power supply circuit 1135Is restored to V50。
FIG. 15 shows the present applicationA schematic diagram of an embodiment of a controller for controlling the discharge of a resonant capacitor of an AHB converter circuit is provided. Fig. 15 differs from fig. 13 in that the controller 114 controls the resonant capacitor C of the primary winding circuit 1111a in the AHB conversion circuit 111arIs discharged periodically. The following description will be made with reference to fig. 11 and 15.
At t3At this time, the controller 114 controls the auxiliary power transistor Q in the half-bridge circuit 1110aHIs periodically turned on to make the resonant capacitor C in the half-bridge circuit 1110arAnd (4) discharging. Specifically, the controller 114 does not supply the main power transistor Q with powerLSending a first control signal GLSo that the main power tube QLAnd (6) turning off. And, the controller 114 periodically supplies the auxiliary power transistor Q with the electric powerHSending a second control signal GHSo that the auxiliary power tube QHIs periodically turned on. Auxiliary power tube Q of half-bridge circuit 1110aHWhen conducting, the primary winding 1111a and the resonant capacitor C of the half-bridge circuit 1110arAuxiliary power tube Q of half-bridge circuit 1110aHA discharge loop may be formed. Accordingly, auxiliary power tube Q of half-bridge circuit 1110aHPeriodically conducting can cause the resonant capacitor C in half-bridge circuit 1110a rAnd is discharged periodically.
In the embodiment of the present application, the controller 114 controls the auxiliary power transistor QHThe period T1, which is periodically conducted, may be pre-configured, or the controller 114 may be based on the current resonant capacitance CrVoltage of capacitor VCrOr stored electric energy is calculated. In one embodiment, the resonant capacitor CrVoltage of capacitor VCrThe period T1 may be set smaller when the voltage value of (a) is higher or the stored electric energy is larger. In one embodiment, the period T1 may also be related to the control signal G1、G2、G3… … or G4、G5、G6… … are identical. In the embodiment of the present application, the controller 114 controls and controls the auxiliary power tube Q in each periodHThe duration of the on or off may be the same or different.
Fig. 16 is a schematic diagram illustrating a change in capacitance voltage of a resonant capacitor of the AHB conversion circuit provided in the present application. As shown in the figure16, resonant capacitance CrPeriodically discharged, resonant capacitor CrVoltage of capacitor VCrFrom VCr2Descending stepwise. At t3Time t4Between moments, resonant capacitance CrVoltage of capacitor VCrWith auxiliary power tube QHThe periodic conduction exhibits a stepwise decrease. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of the power supply circuit 113 also shows a step-like increase, and the output voltage V of the power supply circuit 5Also exhibits a step-like increase in voltage value.
Therefore, the controller 114 controls the resonant capacitor C in the AHB conversion circuit 111arDischarge periodically to make resonant capacitor CrVoltage of capacitor VCrThe stepped descending avoids the influence on the operation of the AHB conversion circuit 111a caused by the excessively fast descending, thereby improving the stability of the power module 11. Furthermore, the controller 114 controls the resonant capacitor C in the AHB conversion circuit 111arThe periodic discharge can cause the output voltage V of the auxiliary winding circuit 112 to be4And an output voltage V of the power supply circuit 1135The step-type ground lifting avoids the damage of circuit devices caused by the too fast voltage lifting, thereby improving the stability of the power module 11.
Fig. 17 is a schematic diagram of another embodiment of a controller controlling the discharge of the resonant capacitor of the AHB converter circuit according to the present application. Fig. 17 differs from fig. 15 in that the controller 114 controls the auxiliary power transistor Q in the primary winding circuit 1111a in the AHB conversion circuit 111aHAnd a main power tube QLPeriodically and alternately conducting to make the resonant capacitor CrIs discharged periodically.
At t3At that time, the controller 114 periodically controls the main power transistor QLAnd an auxiliary power tube QHAlternately conducted and controls the auxiliary power tube QHAnd a main power tube Q LNot simultaneously conducting. Specifically, the controller 114 periodically and sequentially supplies the auxiliary power transistor Q with the electric powerHSending a second control signal GHTo the main power tube QLThe transmitted first control signal GLSo that the auxiliary power tube QHAnd a main power tube QLAre sequentially conducted and assistedPower-assisted tube QHAnd a main power tube QLNot conducting at the same time. Auxiliary power tube Q of half-bridge circuit 1110aHWhen conducting, the primary winding 1111a and the resonant capacitor C of the half-bridge circuit 1110arAuxiliary power tube Q of half-bridge circuit 1110aHA discharge loop may be formed. Resonant capacitor CrVoltage of capacitor VCrReference may be made to fig. 16 for a variation of (2).
In one embodiment, the controller 114 controls the auxiliary power transistor Q every cycleHFirst-conducting main power tube QLThen conducting.
First, the controller 114 controls the auxiliary power transistor QHConducting and main power tube QLAnd (6) cutting off. Specifically, the controller 114 supplies the auxiliary power transistor Q with the electric currentHSending a second control signal GHAnd does not supply the main power tube QLSending a first control signal GL. Accordingly, the resonant capacitor CrPrimary winding a and auxiliary power tube QHForming a current loop, a resonant capacitor CrAnd (4) discharging. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased 5The voltage value of (2) is raised.
The controller 114 then controls the auxiliary power transistor QHCut-off and main power tube QLAnd conducting. Specifically, the controller 114 does not supply the auxiliary power transistor QHSending a second control signal GHAnd to the main power tube QLSending a first control signal GL. At this time, the input voltage V1A primary winding a and a main power tube QLA loop is formed. Accordingly, the input voltage V1Generating a primary winding voltage V on both sides of a primary winding a11. Primary winding voltage V11Coupled via a transformer 1112a, an auxiliary winding voltage V is generated across the auxiliary winding c3. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased5The voltage value of (2) is raised.
Therefore, the controller 114 controls the resonant capacitor C of the primary winding circuit 1111a in the AHB conversion circuit 111arIs periodically discharged, canSo that the resonant capacitance CrVoltage of capacitor VCrThe stepped decline prevents the decline from influencing the operation of the AHB conversion circuit 111a due to too fast decline, thereby improving the stability of the power module 111. Further, the controller 114 controls the resonant capacitor C of the primary winding circuit 1111a in the AHB conversion circuit 111arThe periodic discharge can cause the output voltage V of the auxiliary winding circuit 112 to be 4And an output voltage V of the power supply circuit 1135The step-type lifting avoids that circuit devices are damaged due to too fast lifting, so that the stability of the power module 111 is improved.
In one embodiment, the controller 114 may control the main power transistor Q each cycleLFirst-conducting auxiliary power tube QHThen conducting. In the embodiment of the present application, the controller 114 controls the main power transistor QLAnd an auxiliary power tube QHThe period T2 for periodically conducting alternately can be pre-configured, or the controller 114 can be based on the current resonant capacitance CrVoltage of capacitor VCrOr the stored electric energy is calculated. In one embodiment, the resonant capacitor CrVoltage of capacitor VCrThe period T2 may be set smaller when the voltage value of (a) is higher or the stored electric energy is larger. In one embodiment, the period T2 may be related to the control signal G1、G2、G3… … period or G4、G5、G6… … are identical. In the embodiment of the present application, the controller 114 controls the main power transistor Q in each periodLDuration of conduction, control auxiliary power tube QHThe duration of the conduction may be the same or different. In the embodiment of the present application, the first control signal G sent by the controller 114LAnd a second control signal GHMay be the same or different.
Fig. 18 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided in the present application. As shown in fig. 18, half-bridge circuit 1110a1 includes main power transistor Q LAnd an auxiliary power tube QHAnd a resonant capacitor Cr. Main power tube QLThe source electrode of the primary winding 1111a is connected with the synonym terminal of the primary winding and the auxiliary power tube QHOf the substrate. Auxiliary power tube QHSource electrode ofConnected with a resonance capacitor CrAnd to ground. Resonant capacitor CrIs connected to the same-name terminal of the primary winding 1111 a. Half-bridge circuit 1110a1 shown in fig. 18 may be substituted for half-bridge circuit 1110a in fig. 12, with the function and control logic of half-bridge circuit 1110a1 being the same as half-bridge circuit 1110 a.
Fig. 19 is a schematic diagram of a half-bridge circuit in another AHB conversion circuit provided in the present application. As shown in fig. 19, half-bridge circuit 1110a2 includes main power transistor QLAuxiliary power tube QHAnd a resonant capacitor Cr. The same name end of the primary winding 1111a is connected with a main power tube QLDrain electrode and resonant capacitor CrThe first end of (a). Resonant capacitor CrIs connected with an auxiliary power tube QHOf the substrate. Main power tube QLIs grounded. Auxiliary power tube QHIs grounded. Half-bridge circuit 1110a2 shown in fig. 19 may be substituted for half-bridge circuit 1110a in fig. 12, with the function and control logic of half-bridge circuit 1110a2 being the same as that of half-bridge circuit 1110 a.
In the scenario that the load level L of the power module 11 drops, the controller 114 provided in the embodiment of the present application only needs to control the main power transistor Q in the AHB conversion circuit 111a LAnd an auxiliary power tube QHOn or off. Therefore, the controller 114 provided in the embodiment of the present application can not only improve the stability of the AHB conversion circuit 111a, the power module 11, and the electronic device 10 where the controller 114 is located, but also simplify the configuration of the controller 114, so that the controller is more suitable for various products.
Fig. 20 is a schematic diagram of an embodiment of a power module provided in the present application, and the power module 11 shown in fig. 20 may be applied to the electronic device 10 shown in fig. 1 or fig. 2. As shown in fig. 20, the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113, and a controller 114.
The ACF conversion circuit 111b is used for receiving the input voltage V of the input power supply 131And providing an output voltage V2To power the load 12. In addition, the ACF conversion circuit 111b supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112. Wherein the content of the first and second substances,the auxiliary winding circuit 112 is coupled to the ACF conversion circuit 111b, and generates an auxiliary winding voltage V on the auxiliary winding 11213. The auxiliary winding circuit 112 converts the auxiliary winding voltage V3Is converted into an output voltage V4And supplies power to the power supply circuit 113. The power supply circuit 113 supplies power to the control circuit 114. The controller 114 is used to control the operation state of the ACF conversion circuit 111 b.
Fig. 21 is a schematic diagram of an embodiment of a power module according to the present application. As shown in fig. 21, the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113, and a controller 114. The ACF conversion circuit 111b in the power module 11 includes a half-bridge circuit 1110b, a transformer 1112b, and a rectifier circuit 1114 b. The transformer 1112b includes a primary winding 1111b and a secondary winding 1113 b. In addition, the transformer 1112b also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. Secondary winding 1113b is coupled to primary winding 1111b, and auxiliary winding 1121 is coupled to primary winding 1111 b.
Half-bridge circuit 1110b for receiving an input voltage V provided by an input power supply 131And provides an output voltage V to the primary winding 1111b according to a control signal of the controller 11410. Half-bridge circuit 1110b typically includes a main power transistor, an auxiliary power transistor, and a clamp capacitor.
Primary winding 1111b of transformer 1112b is adapted to receive the output voltage V of half-bridge 1110b10And generates a primary winding voltage V11. A secondary winding 1113b of transformer 1112b is coupled to a primary winding 1111b of transformer 1112b, and a secondary winding voltage V is generated across secondary winding 1113b3。
The rectifying circuit 1114b is used for receiving the secondary winding voltage V on the secondary winding 1113b 3And converted into an output voltage V2。
The auxiliary winding circuit 112 is used to supply power to the power supply circuit 113. An auxiliary winding 1121 of the auxiliary winding circuit 112 is coupled to the primary winding 1111b of the transformer 1112 b. Primary winding voltage V across primary winding 1112b11Coupled to produce an auxiliary winding voltage V across auxiliary winding 11213. Auxiliary winding voltage V3After being processed by the auxiliary winding circuit 112, the magnetic field generator outputsThe power circuit 113 provides an output voltage V4. The auxiliary winding circuit 112 may include an auxiliary winding 1121 and a rectifying module 1122.
The power supply circuit 113 is used to supply power to the controller 114. The power supply circuit 113 receives the output voltage V of the auxiliary winding circuit 1124And provides an output voltage V to the controller 1145. That is, the ACF conversion circuit 111b supplies power to the power supply circuit 113 of the controller 114 via the auxiliary winding circuit 112 coupled to the primary winding 1111 of its transformer 1112 b. In some embodiments, the power circuit 113 includes a voltage regulation circuit.
The controller 114 is used to control the operation state of the ACF conversion circuit 111 b. The controller 114 is also used for detecting the output voltage V of the ACF conversion circuit 111b2The output voltage V of the auxiliary winding circuit 1124And the output voltage V of the power supply circuit 1135Or clamp capacitor C in half-bridge circuit 1110b cVoltage of capacitor VCcThe voltage value of (c), etc. of the plurality of voltage values. The controller 114 is also configured to control the operation state of the ACF conversion circuit 111b according to the change in the one or more voltage values.
In one embodiment, the controller 114 sends the control signal G to control the operation state of the half-bridge circuit 1110b in the ACF conversion circuit 111b, thereby controlling the operation state of the ACF conversion circuit 111 b. For example, the operation state of the ACF conversion circuit 111b generally includes a continuous operation state and a suspended operation state. The continuous operation state may also be referred to as a normal operation state, a controller normal wave generation state, and the like. The pause state may also be referred to as an intermittent operation state, a BURST operation state, a controller intermittent wave state, or the like.
In the embodiment of the present application, the controller 114 can send a control signal G to control the on and off of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110 b. The controller 114 adjusts the frequency or duty ratio of the control signal G to control the turn-on frequency or turn-on duration of the main power transistor and the auxiliary power transistor in the half-bridge circuit 1110b, so as to adjust the output voltage V of the half-bridge circuit 1110b accordingly10. Output voltage V of half-bridge circuit 1110b10Will result in a primary winding voltage V 11And (4) changing. Accordingly, the primary winding is electrically connectedPressure V11The variation may result in a secondary winding voltage V12And an auxiliary winding voltage V3And (4) changing. Accordingly, the secondary winding voltage V12May result in the output voltage V of the ACF conversion circuit 111b2And (4) changing. Accordingly, the auxiliary winding voltage V3May result in the output voltage V of the auxiliary winding circuit 1124And (4) changing. Accordingly, the output voltage V of the auxiliary winding circuit 1124Can result in an output voltage V of the power supply 1135A change in (c).
The ACF conversion circuit 111b may supply the output voltage V as indicated by the direction F1 in FIG. 212To power the load 12. Wherein the input voltage V1Converted into an output voltage V by a half-bridge circuit 1110b, a primary winding 1111b, a secondary winding 1113b, and a rectifier circuit 1114b in the ACF conversion circuit 111b2。
As shown in the direction of F2 in fig. 21, the ACF conversion circuit 111b can supply power to the power supply circuit 113 of the controller 114 through the auxiliary winding circuit 112. Wherein the input voltage V1After being processed by the half-bridge circuit 1110b in the ACF conversion circuit 111b, the primary winding voltage V can be generated at the primary winding 1111b11. Accordingly, the primary winding voltage V11An auxiliary winding voltage V can be generated across an auxiliary winding 1121 of transformer 1112b3. Auxiliary winding voltage V 3Processed by an auxiliary winding circuit 1121 to provide an output voltage V4And supplies power to the power supply circuit 113 of the controller 114.
Fig. 22 is a schematic voltage waveform diagram of a controller and a power module in which the controller is located in a scene where a load level drops. The following describes in detail the operation process of the controller 114 and the power module 11 thereof in a scenario where the load level L of the load 12 falls, with reference to fig. 22 and 21.
At t1Before the moment, the load level L of the load 12 is the normal load L1The controller 114 controls the ACF conversion circuit 111b to operate in a continuous operation state, and the controller 114 controls the output voltage V of the ACF conversion circuit 111b2Is a rated output voltage V20. Output power of auxiliary winding circuit 112Pressure V4Has a voltage value of V40. Output voltage V of power supply circuit 1135Has a voltage value of V50. Clamping capacitor C in half-bridge circuit 1111bcVoltage of capacitor VCcHas a voltage value of VCc1。VCc1Clamping capacitor C for ACF conversion circuit 111b operating in continuous operation statecThe capacitor voltage of (c).
At t1At that moment, the load level of the load 12 is changed from the normal load L1Drop to light load L2. Accordingly, at t1After the time point, the output voltage V of the ACF conversion circuit 111b 2Is increased to be larger than the rated output voltage V20。
In one embodiment, when the output voltage V of the ACF conversion circuit 111b is detected2Has a voltage value greater than the rated output voltage V20The controller 114 may control the ACF conversion circuit 111b to operate in the continuous operation state. The controller controls the ACF conversion circuit 111b to lower the output voltage V2The voltage value of (2). That is, the controller 114 outputs the voltage V according to the ACF conversion circuit 111b2Voltage value of and rated output voltage V20As a result of the comparison, the controller 114 controls the ACF conversion circuit 111b to operate in a continuous operation state, and the controller 114 controls the ACF conversion circuit 111b to lower the output voltage V2The voltage value of (2). Specifically, the controller 114 sends a control signal G to control the operation states of the main power tube and the auxiliary power tube in the half-bridge circuit 1110b, so that the primary winding voltage V is obtained11The voltage value of (2) decreases. In one embodiment, the controller 114 may decrease the transmission frequency of the control signal G, thereby decreasing the conduction frequency of the main power transistor and the auxiliary power transistor. In one embodiment, the controller 114 may decrease the duty cycle of the control signal G, thereby decreasing the conduction time of the main power transistor and the auxiliary power transistor. In another embodiment, when the output voltage V of the ACF conversion circuit 111b 2Is greater than the rated voltage V20The controller 114 can control the ACF conversion circuit 111b to operate in a suspended state and can also reduce the output voltage V2The voltage value of (2). However, both of the above embodiments may fail to make the output voltage V of the ACF conversion circuit 111b2Is effectively reduced at t1Output voltage V of ACF conversion circuit 111b after time2Will continue to rise.
At the same time, at t1After the time, the drop of the load level L causes the output voltage V of the ACF conversion circuit 111b2Has a voltage value higher than the rated voltage V20. Primary winding voltage V11Clamping capacitor C for half-bridge circuit 1110bcCharging, clamping capacitor C in half-bridge circuit 1110bcVoltage of capacitor VCcVoltage value of from VCc1Is lifted to VCc2。VCc2Clamping capacitor C in half-bridge circuit 1110bcThe maximum charging voltage of.
At t1T after the moment2At that time, the output voltage V of the ACF conversion circuit 111b2The voltage value of the transformer is increased to a first preset value V21. The controller 114 determines the output voltage V of the ACF conversion circuit 111b2Is greater than or equal to a first preset value V21The controller 114 controls the ACF conversion circuit 111b to suspend operation. That is, the controller 114 outputs the voltage V according to the ACF conversion circuit 111b2Voltage value of (d) and a first predetermined value V 21As a result of the comparison, the controller 114 controls the ACF conversion circuit 111b to operate in a pause state. Specifically, controller 114 controls both the main power transistor and the auxiliary power transistor of half-bridge circuit 1110b to be turned off. In the embodiment of the present application, the first preset value V21May be the peak voltage of the ACF conversion circuit 111 b. The peak voltage of the ACF conversion circuit 111b is larger than the rated voltage V20And is smaller than the overvoltage protection voltage of the ACF conversion circuit 111 b.
At t2After the time, the controller 114 controls the ACF conversion circuit 111b to operate in the suspended state. Accordingly, the primary winding voltage V on the primary winding 1111b in the ACF conversion circuit 111b11Resulting in a secondary winding voltage V12Drop and result in an auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the ACF conversion circuit 111b2The voltage value of (2) decreases, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage of the power supply circuit 113 decreasesV5The voltage value of (2) decreases.
At t2T after time3At that moment, the output voltage V of the auxiliary winding circuit 1124Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V 52. At this time, controller 114 controls clamp capacitor C in half-bridge circuit 1110bcAnd (4) discharging.
In one embodiment, the controller 114 determines the output voltage V of the auxiliary winding circuit 1124Is less than or equal to a second preset value V41Controller 114 controls clamp capacitor C in half-bridge circuit 1110bcAnd (4) discharging. That is, the controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a second predetermined value V41Controls the clamp capacitor C in half-bridge circuit 1110bcAnd (4) discharging.
In one embodiment, the controller 114 determines the output voltage V of the power circuit 1135Is less than or equal to a third predetermined value V52Controller 114 controls clamp capacitor C in half-bridge circuit 1110bcAnd (4) discharging. That is, the controller 114 is based on the output voltage V of the power supply circuit 1135Voltage value of (d) and a third predetermined value V52As a result of the comparison, the controller 114 controls the clamp capacitor C in the half-bridge circuit 1110bcAnd (4) discharging.
In one embodiment, controller 114 controls the conduction of the auxiliary power transistor in half-bridge circuit 1110b, so that clamping capacitor C in half-bridge circuit 1110bcAnd (4) discharging. Clamping capacitor C of primary winding 1111b and half-bridge circuit 1110bcThe auxiliary power transistor of half-bridge circuit 1110b may form a discharge circuit. Accordingly, clamp capacitor C of half-bridge circuit 1110b cDischarging to generate a primary winding voltage V on the primary winding 1111b11。
In one embodiment, controller 114 controls the auxiliary power transistor in half-bridge circuit 1110b to be periodically turned on, so that the clamp capacitor C in half-bridge circuit 1110bcAnd (4) discharging. When the auxiliary power transistor of half-bridge 1110b is on,clamping capacitor C of primary winding 1111b and half-bridge circuit 1110bcThe auxiliary power transistor of half bridge 1110b may form a discharge loop. Accordingly, the auxiliary power transistor of half-bridge circuit 1110b is periodically turned on, so that the clamp capacitor C in half-bridge circuit 1110bcAnd is discharged periodically.
At t3After time, clamp capacitor C in half-bridge circuit 1110bcVoltage of capacitor VCcThe voltage value of (2) decreases. Clamping capacitor C in half-bridge circuit 1110bcDischarge so that the primary winding voltage V on the primary winding 1111b11The voltage value of (2) is raised. Accordingly, the primary winding voltage V11The voltage value of (2) is increased, which results in an auxiliary winding voltage V3The voltage value of (2) is raised. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased5The voltage value of (2) is raised. Therefore, in a scene where the load level of the load 12 changes, the output voltage V of the power supply circuit 113 5Does not fall below the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection.
The controller 114 provided by the embodiment of the present application controls the clamp capacitor C in the half-bridge circuit 1110b of the ACF conversion circuit 111bcDischarge, the output voltage V of the power supply circuit 113 can be made5Is higher than the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
Clamping capacitor C in half-bridge circuit 1110b of ACF conversion circuit 111bcLimited energy stored, primary winding voltage V generated on primary winding 1111b after discharge11The voltage value of (2) is small. The voltage V of the primary winding generated at the primary winding 1111b at this time11Is less than the secondary winding voltage V on the secondary winding 111312Without causing the output voltage V of the ACF conversion circuit 111b2And (5) lifting. Thus, controller 114 controls clamp capacitor C in half-bridge circuit 1110bcAfter discharge, the voltage V of the primary winding generated on the primary winding 1111b11For boosting the output voltage V of the auxiliary winding circuit 112 only 4And the output voltage V of the power supply circuit 1135As shown in the direction of F2 in fig. 21. Therefore, the controller 114 and the power module 111 thereof provided in the embodiment of the present application can not only prevent the controller 114 from being restarted due to under-voltage protection, but also prevent the output voltage V of the ACF conversion circuit 111b from being increased2The ripple of the controller can improve the stability of the power module 11 and the electronic device 10 in which the controller 114 is located.
Furthermore, the controller 114 provided in the embodiment of the present application controls the clamp capacitor C in the half-bridge circuit 1110b of the ACF conversion circuit 111bcNoise from the input power supply 13 is not introduced, and the noise can be prevented from affecting the electromagnetic compatibility of the ACF conversion circuit 111b, the power supply module 11 in which the ACF conversion circuit is installed, and the electronic device 10. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
In one embodiment of the present application, clamp capacitor C is placed in half-bridge circuit 1110b of ACF conversion circuit 111bcAfter the discharge is initiated, the controller 114 can also clamp the capacitor C in the half-bridge circuit 1110bcVoltage of capacitor VCcVoltage value of (3), output voltage V of auxiliary winding circuit 1124Or the output voltage V of the power supply circuit 113 5To control clamp capacitor C in half-bridge circuit 1110bcThe discharge is stopped. In one embodiment, the controller 114 controls the auxiliary power transistor in the half-bridge circuit 1110b to turn off, the primary winding 1111b, and the clamp capacitor C of the half-bridge circuit 1110bcThe discharge circuit formed by the auxiliary power tube of half-bridge circuit 1110b is open. Accordingly, clamp capacitor C of half-bridge circuit 1110bcThe discharge is stopped.
In a first embodiment, at t3T after the moment4At time, clamp capacitor C of half-bridge 1110bcVoltage of capacitor VCcIs reduced to be less than or equal to the preset capacitance voltage value VCc3. In one embodiment, controller 114 determines the clamping capacitance C of half-bridge circuit 1110bcVoltage of capacitor VCcIs reduced to be less than or equal to the preset capacitance voltage value VCc3Controller 114 controls clamp capacitor C of half-bridge circuit 1110bcThe discharge is stopped. In one embodiment, the preset capacitor voltage value VCc3May be greater than or equal to the clamping capacitance C of the half-bridge circuit 1110b when the ACF conversion circuit 111b is operated in the continuous operation statecVoltage value V of the capacitor voltageCc1. That is, controller 114 depends on the clamping capacitance C of half-bridge circuit 1110bcVoltage of capacitor VCcAnd a predetermined capacitor voltage value VCc3As a result of the comparison, the controller 114 controls the clamp capacitor C of the half-bridge circuit 1110b cThe discharge is stopped. Thus, controller 114 may pass through clamp capacitor C of half-bridge circuit 1110bcStopping discharging to avoid clamping capacitor CcVoltage of capacitor VCcThe ACF conversion circuit 111b is influenced to recover the continuous working state due to too low temperature, so that the stability of the power module 11 and the electronic device 10 in which the power module is arranged is further improved.
In a second embodiment, at t3T after the moment4At that moment, the output voltage V of the auxiliary winding circuit 1124The voltage value of the voltage is increased to be more than or equal to a fourth preset value V42. In one embodiment, the controller 114 determines the output voltage V of the auxiliary winding circuit 1124Is greater than or equal to a fourth preset value V42Controller 114 controls clamp capacitor C of half-bridge circuit 1110bcThe discharge is stopped. That is, the controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a fourth preset value V42As a result of the comparison, the controller 114 controls the clamp capacitor C of the half-bridge circuit 1110bcThe discharge is stopped. Thus, controller 114 may pass through clamp capacitor C of half-bridge circuit 1110bcStopping the discharge can prevent the output voltage V of the auxiliary winding circuit 1124The voltage of the power supply circuit 113 and the controller 114 is too high, which further improves the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located.
In a third embodiment, at t3T after the moment of time4At that time, the output voltage V of the power supply circuit 1135The voltage value of the voltage is increased to be more than or equal to a fifth preset value V53When the user wants to use the device. In one embodiment, the controller 114 determines the output voltage V of the power circuit 1135Is greater than or equal to a fifth preset value V53Controller 114 controls clamp capacitor C of half-bridge circuit 1110bcThe discharge is stopped. That is, the controller 114 is based on the output voltage V of the power supply circuit 1135Voltage value of (d) and a fifth predetermined value V53As a result of the comparison, the controller 114 controls the clamp capacitor C of the half-bridge circuit 1110bcThe discharge is stopped. Thus, controller 114 may control clamp capacitance C of half-bridge circuit 1110bcStopping discharge to avoid the output voltage V of the power circuit 1134The voltage of the power supply is too high to damage the controller 114, so that the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located is further improved.
At t4After time, clamp capacitor C of half-bridge circuit 1110bcAfter stopping discharging, the clamping capacitor CcVoltage of capacitor VCcStops decreasing in voltage value. Accordingly, the primary winding voltage V11Resulting in a drop in the voltage value of the auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the auxiliary winding circuit 112 4The voltage value of (3) decreases, and the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
In one embodiment of the present application, at t4After the moment, when the output voltage V of the auxiliary winding circuit 1124Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V52When desired, controller 114 may control clamp capacitance C of half-bridge circuit 1110bcAnd discharging again. The specific process is as described in the above examples, and will not be repeated. That is, the controller 114 may be based on the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a second predetermined value V41Controls the clamp capacitance C of half-bridge 1110b as a result of the comparisoncAnd discharging again. Alternatively, the controller 114 may be based on the output voltage V of the power supply circuit 1135Voltage value of and the third voltageSet value V52Controls the clamp capacitance C of half-bridge 1110b as a result of the comparisoncAnd discharging again.
In one embodiment of the present application, the clamping capacitor C of half-bridge circuit 1110bcAfter the discharge is started or stopped, the controller 114 also outputs the voltage V according to the ACF conversion circuit 111b2Controls the operation state of the ACF conversion circuit 111b to be switched from the pause operation state to the continuous operation state. At t 2After the time, the controller 114 controls the ACF conversion circuit 111b to operate in the suspended state, and accordingly the output voltage V of the ACF conversion circuit 111b2The voltage value of (2) decreases. In one embodiment, clamp capacitor C at half-bridge circuit 1110bcAfter the start of discharge and before the stop of discharge, the output voltage V of the ACF conversion circuit 111b2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the ACF conversion circuit 111b to be switched from the pause operation state to the continuous operation state. In one embodiment, clamp capacitor C at half-bridge circuit 1110bcAfter the discharge is stopped, the output voltage V of the ACF conversion circuit 111b2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the ACF conversion circuit 111b to be switched from the pause operation state to the continuous operation state.
At t3T after the moment5At that time, the output voltage V of the ACF conversion circuit 111b2To a voltage value less than or equal to a rated voltage V20. The controller 114 determines the output voltage V of the ACF conversion circuit 111b2To a voltage value less than or equal to a rated voltage V20The operation state of the ACF conversion circuit 111b is controlled to be switched from the pause operation state to the continuous operation state. That is, the controller 114 outputs the voltage V according to the ACF conversion circuit 111b 2Voltage value of (d) and rated voltage V20Controls the operation state of the ACF conversion circuit 111b to switch from the pause operation state to the continuous operation state. At t5After the time point, the output voltage V of the ACF conversion circuit 111b2Is restored to the rated voltage V20The output voltage V of the auxiliary winding circuit 1124Is restored to V40Output voltage V of power supply circuit 1135Is restored to V50。
Fig. 23 is a schematic diagram of an embodiment of a power module provided in the present application. Fig. 23 is a schematic diagram showing a part of the circuit in the power module 11 shown in fig. 21. As shown in fig. 23, the power module 11 includes an ACF conversion circuit 111b, an auxiliary winding circuit 112, a power circuit 113, and a controller 114. The ACF conversion circuit 111b includes a half-bridge circuit 1110b, a transformer 1112b, and a rectifier circuit 1114 b. The transformer 1112b includes a primary winding 1111b and a secondary winding 1113 b. In addition, the transformer 1112b also includes an auxiliary winding 1121 in the auxiliary winding circuit 112. The secondary winding 1113b is coupled to the primary winding 1111b, and the auxiliary winding 1121 is coupled to the primary winding 1111 b.
Half-bridge circuit 1110b includes main power transistor QLAuxiliary power tube QHAnd a clamp capacitor Cc. Main power tube Q LAnd an auxiliary power tube QHAnd a clamp capacitor CcAn active clamped flyback half-bridge topology is formed. Specifically, a clamping capacitor CcHas a first end connected to the different name end of the primary winding 1111b, and a clamping capacitor CcIs connected with an auxiliary power tube QHOf the substrate. Auxiliary power tube QHThe source electrode of the primary winding 1111b is connected with the same-name end of the primary winding 1111b and the main power tube QLOf the substrate. Main power tube QLIs grounded. In one embodiment, the main power transistor QLIs used for receiving a second control signal G of the controller 114H. Auxiliary power tube QHIs used for receiving a first control signal G of the controller 114L。
The rectifying circuit 1114b includes a capacitor C1And a diode D2. Diode D2Is connected to the end of the secondary winding 1113b having the same name. Capacitor C1Are respectively connected with a diode D2And the opposite terminal of the secondary winding 1113 b.
The auxiliary winding circuit 112 includes an auxiliary winding 1121 and a rectification module 1122. The rectification module 1122 may include a diode D1. Wherein, the diode D1And an anode ofDotted terminal connection of auxiliary winding 1121, diode D1And the opposite end of the auxiliary winding 1121 is connected to the power supply circuit 113.
The power circuit 113 may include a BOOST (BOOST) circuit. In one embodiment, the power circuit 113 may also be a BUCK (BUCK) circuit, a BUCK-BOOST (BUCK-BOOST) circuit, or the like. In one embodiment, the power circuit 113 may also be a low dropout regulator (LDO) or other regulator.
The controller 114 includes a detection unit 1141 and a driving unit 1142. In some embodiments, when the driving unit 1142 is a chip, the power circuit 113 may be connected to a power supply pin of the driving unit 1142. For example, the supply pin may be the reference numeral "V" shown in FIG. 23dd"of the substrate.
The detection unit 1141 is used for detecting the output voltage V of the ACF conversion circuit 111b2 Auxiliary winding circuit 1124Voltage value of (d), output voltage V of power supply circuit 1135Voltage value of or clamp capacitance C in half-bridge circuit 1110b of ACF conversion circuit 111bcVoltage of capacitor VCcOf the voltage values of (a). The driving circuit 1142 is used to control the operation state of the ACF conversion circuit 111b according to the change of the one or more voltage values.
For example, the detection unit 1141 may detect the output voltage V of the ACF conversion circuit 111b by connecting the point a of the output terminal of the secondary winding circuit 1114b in fig. 232The voltage value of (2). The detection unit 1141 may detect the output voltage V of the auxiliary winding circuit 112 through the point B connected to the output terminal of the auxiliary winding circuit 112 in fig. 234The voltage value of (2). The detection unit 1141 may detect the output voltage V of the power circuit 113 through the point C connected to the output terminal of the power circuit 113 in fig. 23 5The voltage value of (2). The detecting unit 1141 can be connected to the clamp capacitor C in FIG. 23cAt any point D, a clamp capacitor C is detectedcVoltage of capacitor VCcThe voltage value of (2).
The driving unit 1142 is used to control the operation state of the ACF conversion circuit 111 b. Wherein, the driving unit 1142 sends out a control signal GL/GHControlling the main power transistor QLAnd an auxiliary power tube QHThereby controlling the operation state of the ACF conversion circuit 111 b. In some embodiments, when the driving unit 1142 is a chip, the driving unit 1142 shown in fig. 23 may be denoted by its reference numeral "GH' the pin sends out a control signal GHMay be given by its reference numeral "GL' the pin sends out a control signal GL. It should be noted that the reference numbers of the pins in fig. 23 are only examples, and in practical applications, the pins of other reference numbers of the driving unit 1142 may also be used to implement the functions of the pins shown in fig. 23.
The driving unit 1142 supplies power to the main power tube QLSending a first control signal GLControl the main power tube QLOn or off. The driving unit 1142 drives the auxiliary power tube QHSending a second control signal GHControl the auxiliary power tube QHOn or off. In the embodiment of the present application, the first control signal G sent by the controller 114 LA second control signal GHImplementations may include a high level signal or a low level signal. In one embodiment, the main power tube QLAccording to a first control signal GLConducting auxiliary power tube QHAccording to the second control signal GHAnd conducting. In one embodiment, the main power transistor QLAccording to the first control signal GLTurn-off, auxiliary power tube QHAccording to the second control signal GHAnd (6) turning off.
Fig. 24 is a schematic diagram of control signals of the controller provided in the present application in a scenario where a load level of a power module is dropped. The following describes, with reference to fig. 22, 23 and 24, an operation process of the controller 114 and the power module 11 thereof provided in the present application in a scenario where the load level L of the load 12 falls.
Before time t1, the load level of load 12 is normal load L1. The controller 114 controls the ACF conversion circuit 111b to operate in a continuous operation state, and controls the output voltage V of the ACF conversion circuit 111b2Has a voltage value of rated voltage V20. At this time, the auxiliary winding circuit 112 output voltage V4Has a voltage value of V40. Output voltage V of power supply circuit 1135Has a voltage value of V50. Clamping capacitor C in half-bridge circuit 1111bcVoltage of capacitor VCcHas a voltage value of VCc1。
Fig. 25 is a schematic diagram of a control signal of a controller according to an embodiment of the present application. As shown in FIG. 25, the control signal G sent by the controller 114 1、G2、G3… each includes a primary power transistor QLThe transmitted first control signal GLOr to auxiliary power tube QHThe second control signal G transmittedH. The controller 114 controls the main power transistor QLAnd an auxiliary power tube QHPeriodically and alternately turned on and off, the half-bridge circuit 1110b can generate a primary winding voltage V at the primary winding 1111b11. Primary winding voltage V on primary winding 1111b11Coupled, a secondary winding voltage V can be generated across secondary winding 1113b12And may generate an auxiliary winding voltage V across auxiliary winding 11213. Accordingly, the rectifying circuit 1114b supplies the output voltage V to the load 122The auxiliary winding circuit 112 supplies the output voltage V to the power supply circuit 1134The output voltage V of the power supply circuit 113 to the controller 1155Is a V50. Since the ACF conversion circuit 111b outputs the voltage V to the load 122Is stabilized at a rated voltage V20Clamping capacitor C in half-bridge circuit 1110bcVoltage value V ofCcStabilized at VCc1。
At time t1, the load level of load 12 is changed from normal load L1Drop to light load L2. After time t1, the output voltage V of the ACF conversion circuit 111b2Is increased to be larger than the rated voltage V20。
In one embodiment, the controller 114 outputs the voltage V according to the ACF conversion circuit 111b 2Voltage value of (d) and rated voltage V20Controls the ACF conversion circuit 111b to operate in a continuous operation state, and the controller 114 controls the ACF conversion circuit 111b to lower the output voltage V2The voltage value of (2).
Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the ACF conversion circuit 111b2And determines the output voltage V of the ACF conversion circuit 111b2Greater than rated voltage V20. Accordingly, the controller 114 controls the ACF conversion circuit 111b to operate in the continuous operation state, and the controller 114 decreases the first control signal GLAnd a second control signal GHOr reducing the first control signal GLAnd a second control signal GHThe duty cycle of (c). As shown in fig. 24, at t1Control signal G sent by controller 114 after a time4、G5、G6Is less than t1Control signal G periodically transmitted before time1、G2、G3Of (c) is detected. Accordingly, the main power tube QLAnd an auxiliary power tube QHThe frequency of on and off is reduced so that the output voltage V of the ACF conversion circuit 111b is reduced2The voltage value of (2) decreases. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases. However, the above-described method may not allow the output voltage V of the ACF conversion circuit 111b to be set 2The voltage value of ACF conversion circuit 111b is effectively decreased, and the output voltage V of the ACF conversion circuit2Will continue to rise.
At t1After the time point, the output voltage V of the ACF conversion circuit 111b2Is higher than the rated voltage V20. At this time, the primary winding voltage V11Clamping capacitor C for half-bridge circuit 1110bcCharging, clamping capacitor C in half-bridge circuit 1110bcVoltage of capacitor VCcVoltage value of from VCc1Is lifted to VCc2。
At t1T after the moment2At that time, the output voltage V of the ACF conversion circuit 111b2The voltage value of the voltage is increased to be more than or equal to a first preset value V21. The controller 114 outputs the voltage V according to the ACF conversion circuit 111b2Voltage value of (d) and a first predetermined value V21As a result of the comparison, the controller 114 controls the ACF conversion circuit 111b to operate in the suspended state. In particular, the amount of the solvent to be used,the detection unit 1141 of the controller 114 detects the output voltage V of the ACF conversion circuit 111b2And determines the output voltage V of the ACF conversion circuit 111b2Is greater than or equal to a first preset value V21. Accordingly, the driving unit 1142 of the controller 114 stops transmitting the first control signal GLAnd a second control signal GHThereby controlling the ACF conversion circuit 111b to operate in the suspended state. Accordingly, the input voltage V that the ACF conversion circuit 111b does not receive for is 1The output voltage V of the ACF conversion circuit 111b is processed2And (4) reducing.
At t2After that time, the controller 114 controls the ACF conversion circuit 111b to operate in a pause state. Accordingly, the primary winding voltage V at the primary winding 1111b in the ACF conversion circuit 111b11Thereby causing a secondary winding voltage V12Drop and result in an auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the ACF conversion circuit 111b2The voltage value of (2) decreases, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
At t2T after time3At that moment, the output voltage V of the auxiliary winding circuit 1124Is reduced to be lower than a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be lower than a third preset value V52. At this time, the controller 114 controls the clamp capacitor C in the half-bridge circuit 1110bcAnd (4) discharging.
In one embodiment, the detection unit 1141 of the controller 114 detects the output voltage V of the auxiliary winding circuit 1124And determines the output voltage V of the auxiliary winding circuit 1124Is less than or equal to a second preset value V41. The driving unit 1142 of the controller 114 transmits a first control signal G LSo that the auxiliary power tube QHAnd conducting. At this time, clamp capacitor C of half-bridge 1110bcPower tube Q of primary winding 1111b and half-bridge circuit 1110bHClamping of half-bridge circuit 1110b forming a discharge loopContainer CcThe discharge is started.
In one embodiment, the detection unit 1141 of the controller 114 detects the output voltage V of the power circuit 1135And determines the output voltage V of the power supply circuit 1135Is less than or equal to a third preset value V52. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd conducting. At this time, clamp capacitor C of half-bridge circuit 1110bcPower tube Q of primary winding 1111b and half-bridge circuit 1110bHClamping capacitor C forming a discharge circuit, half-bridge circuit 1110bcThe discharge is started.
At t3After time, clamp capacitor C in half-bridge circuit 1110bcVoltage of capacitor VCcThe voltage value of (2) decreases. Clamping capacitor C in half-bridge circuit 1110bcDischarge so that the primary winding voltage V on the primary winding 1111b11The voltage value of (2) is raised. Accordingly, the auxiliary winding voltage V3The voltage value of (2) is raised, and the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased5The voltage value of (2) is raised. Therefore, in a scene where the load level of the load 12 changes, the output voltage V of the power supply circuit 113 5Does not fall below the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection.
The controller 114 provided by the embodiment of the present application controls the clamp capacitor C in the half-bridge circuit 1110b of the ACF conversion circuit 111bcDischarge, the output voltage V of the power supply circuit 113 can be made5Is higher than the under-voltage protection voltage V of the controller 11451Thereby avoiding the controller 114 from restarting due to low voltage protection. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
Clamping capacitor C in half-bridge circuit 1110b of ACF conversion circuit 111bcLimited energy stored, primary winding voltage V generated on primary winding 1111b after discharge11The voltage value of (2) is small. At the moment, the primary sidePrimary winding voltage V generated at winding 1111b11Is less than the secondary winding voltage V on the secondary winding 111312Without causing the output voltage V of the ACF conversion circuit 111b2And (5) lifting. Thus, controller 114 controls clamp capacitor C in half-bridge circuit 1110bcAfter discharge, the voltage V of the primary winding generated on the primary winding 1111b11For boosting the output voltage V of the auxiliary winding circuit 112 only 4And the output voltage V of the power supply circuit 1135. Therefore, the controller 114 and the power module 111 thereof provided in the embodiment of the present application can not only prevent the controller 114 from being restarted due to under-voltage protection, but also prevent the output voltage V of the ACF conversion circuit 111b from being increased2The ripple of the controller can improve the stability of the power module 11 and the electronic device 10 in which the controller 114 is located.
Furthermore, the controller 114 provided in the embodiment of the present application controls the clamp capacitor C in the half-bridge circuit 1110b of the ACF conversion circuit 111bcThe noise from the input power supply 13 is not introduced, and the electromagnetic compatibility of the ACF conversion circuit 111b, the power supply module 11 in which the ACF conversion circuit is located, and the electronic device 10 can be prevented from being affected. Therefore, the controller 114 provided in the embodiment of the present application can improve the stability of the power module 11 and the electronic device 10 where the controller is located.
In an embodiment of the present application, the controller 114 may further control the clamping capacitor C in the half-bridge circuit 1110b of the ACF conversion circuit 111bcThe discharge is stopped.
In a first embodiment, at t3T after the moment4At time, clamp capacitor C of half-bridge 1110bcVoltage of capacitor VCcIs reduced to be less than or equal to the preset capacitance voltage value VCc3. In one embodiment, the preset capacitor voltage value V Cc3Can be greater than or equal to the clamping capacitance C of half-bridge circuit 1110b when ACF conversion circuit 111b is in continuous operationcVoltage value V of the capacitor voltageCc. Controller 114 adjusts the clamping capacitance C according to half-bridge circuit 1110bcVoltage of capacitor VCcAnd a predetermined capacitor voltage value VCc3As a result of the comparison, controller 114 controls clamp capacitor C of half-bridge circuit 1110bcStopping discharge. Specifically, the detection unit 1141 of the controller 114 detects the clamp capacitance C of the half-bridge circuit 1110bcVoltage of capacitor VCcAnd determines the clamp capacitance C of half-bridge 1110bcVoltage of capacitor VCcLess than or equal to the preset capacitor voltage value VCc3. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd (6) turning off. At this time, clamp capacitor C of half-bridge circuit 1110bcPower tube Q of primary winding 1111b and half-bridge circuit 1110bHThe formed discharge circuit is opened, and the clamping capacitor C of the half-bridge circuit 1110bcThe discharge is stopped.
Thus, controller 114 may pass through clamp capacitor C of half-bridge circuit 1110bcStopping discharging to avoid clamping capacitor CcVoltage of capacitor VCcThe ACF conversion circuit 111b is affected by too low to recover the continuous operation state, so that the stability of the power module 11 and the electronic device 10 where the power module is located is further improved.
In a second embodiment, at t3T after the moment of time4At that moment, the output voltage V of the auxiliary winding circuit 1124The voltage value of the voltage is increased to be more than or equal to a fourth preset value V42. The controller 114 is responsive to the output voltage V of the auxiliary winding circuit 1124Voltage value of (d) and a fourth preset value V42As a result of the comparison, the controller 114 controls the clamp capacitor C of the half-bridge circuit 1110bcThe discharge is stopped. Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the auxiliary winding circuit 1124And determines the output voltage V of the auxiliary winding circuit 1124Is less than or equal to the preset capacitor voltage value VCc3. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd (4) turning off. At this time, clamp capacitor C of half-bridge circuit 1110bcPower tube Q of primary winding 1111b and half-bridge circuit 1110bHThe formed discharge circuit is opened, and the clamping capacitor C of the half-bridge circuit 1110bcThe discharge is stopped.
Thus, controller 114 may pass through clamp capacitor C of half-bridge circuit 1110bcStopping discharge to avoidOutput voltage V of auxiliary winding circuit 1124The voltage of the power supply circuit 113 and the controller 114 is too high, which further improves the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located.
In a third embodiment, at t3T after the moment of time4At that time, the output voltage V of the power supply circuit 1135Is increased to be greater than or equal to a fifth preset value V53. The controller 114 is controlled according to the output voltage V of the power circuit 1135Voltage value of (d) and a fifth preset value V53As a result of the comparison, controller 114 controls clamp capacitor C of half-bridge circuit 1110bcThe discharge is stopped. Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the power supply circuit 1135And determines the output voltage V of the power supply circuit 1135Is greater than or equal to a fifth preset value V53. The driving unit 1142 of the controller 114 transmits a first control signal GLSo that the auxiliary power tube QHAnd (6) turning off. At this time, clamp capacitor C of half-bridge circuit 1110bcPower tube Q of primary winding 1111b and half-bridge circuit 1110bHThe formed discharge circuit is opened, and the clamping capacitor C of the half-bridge circuit 1110bcThe discharge is stopped. Thus, controller 114 may control clamp capacitance C of half-bridge circuit 1110bcStopping discharge to avoid the output voltage V of the power circuit 1134The voltage of the power supply is too high to damage the controller 114, so that the stability of the controller 114 and the power supply module 11 and the electronic device 10 in which the controller is located is further improved.
At t4After time, clamp capacitor C of half-bridge circuit 1110b cAfter stopping discharging, the clamping capacitor CcVoltage of capacitor VCcThe voltage value of (2) stops decreasing. Accordingly, the primary winding voltage V11Resulting in an auxiliary winding voltage V3And (4) descending. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) decreases, and the output voltage V of the power supply circuit 113 decreases5The voltage value of (2) decreases.
In one embodiment of the present application, at t4After the moment when the output voltage V of the auxiliary winding circuit 112 is reached4Is reduced to be less than or equal to a second preset value V41Or the output voltage V of the power supply circuit 1135Is reduced to be less than or equal to a third preset value V52When desired, controller 114 may control clamp capacitance C of half-bridge circuit 1110bcAnd discharging again. The specific process is as described in the above examples, and will not be repeated.
In one embodiment of the present application, the clamping capacitor C of half-bridge circuit 1110bcAfter the discharge is started or stopped, the controller 114 also outputs the voltage V according to the ACF conversion circuit 111b2Controls the operation state of the ACF conversion circuit 111b to be switched from the pause operation state to the continuous operation state. At t2After the time, the controller 114 controls the ACF conversion circuit 111b to operate in the suspended state, and accordingly the output voltage V of the ACF conversion circuit 111b 2The voltage value of (2) decreases. In one embodiment, clamp capacitor C at half-bridge circuit 1110bcAfter the start of discharge and before the stop of discharge, the output voltage V of the ACF conversion circuit 111b2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the ACF conversion circuit 111b to be switched from the pause operation state to the continuous operation state. In one embodiment, clamp capacitor C in half-bridge circuit 1110bcAfter the discharge is stopped, the output voltage V of the ACF conversion circuit 111b2To a voltage value less than or equal to a rated voltage V20The controller 114 controls the operation state of the ACF conversion circuit 111b to be switched from the pause operation state to the continuous operation state.
At t3T after the moment5At that time, the output voltage V of the ACF conversion circuit 111b2To a voltage value less than or equal to the rated output voltage V20. The controller 114 outputs the voltage V according to the ACF conversion circuit 111b2Voltage value of and rated output voltage V20Controls the operation state of the ACF conversion circuit 111b to switch from the pause operation state to the continuous operation state. Specifically, the detection unit 1141 of the controller 114 detects the output voltage V of the ACF conversion circuit 111b2And determines the output voltage of the ACF conversion circuit 111b Pressure V2Is less than or equal to the rated output voltage V20. The driving unit 1142 of the controller 114 periodically transmits the first control signal GLAnd a second control signal GHControlling the main power tube QLAnd an auxiliary power tube QHThe ACF conversion circuit 111b is turned on and off periodically, so that the continuous operation state is restored. At this time, the controller 114 sends a first control signal GLAnd a second control signal GHIs marked as G7、G8、G9… are provided. Each control signal G7、G8、G9… are the same as those shown in FIG. 25 and will not be described in detail. Also for example, the control signal G7、G8、G9… may also be synchronized with the control signal G1、G2、G3… …, or with the same period as G4、G5、G6… … are equal in period. At t5After the time point, the output voltage V of the ACF conversion circuit 111b2Is restored to the rated output voltage V20The output voltage V of the auxiliary winding circuit 1124Is restored to V40Output voltage V of power supply circuit 1135Is restored to V50。
Fig. 26 is a schematic diagram of an embodiment in which a controller controls discharge of clamp capacitors of an ACF conversion circuit. Fig. 26 differs from fig. 24 in that the controller 114 controls the clamp capacitance C of the primary winding circuit 1111b in the ACF conversion circuit 111bcIs discharged periodically. The following description will be made with reference to fig. 22 and 26.
At t3At this time, the controller 114 controls the auxiliary power transistor Q in the half-bridge circuit 1110bHIs periodically turned on to enable the clamping capacitor C in the half-bridge circuit 1110bcAnd (4) discharging. Specifically, the controller 114 does not supply the main power transistor Q with powerLSending a first control signal GLSo that the main power tube QLAnd (6) turning off. And, the controller 114 periodically supplies the auxiliary power transistor Q with the electric powerHSending a second control signal GHSo that the auxiliary power tube QHIs periodically turned on. Auxiliary power tube of half-bridge circuit 1110bQHWhen conducting, the primary winding 1111b and the clamping capacitor C of the half-bridge circuit 1110bcAuxiliary power tube Q of half-bridge circuit 1110bHA discharge loop may be formed. Accordingly, auxiliary power transistor Q of half-bridge circuit 1110bHPeriodically conducting, can cause the clamping capacitor C in half-bridge circuit 1110bcIs discharged periodically.
In the embodiment of the present application, the controller 114 controls the auxiliary power transistor QHThe period T1, which is periodically turned on, may be pre-configured, or the controller 114 may be based on the current clamping capacitance CcVoltage of capacitor VCcOr stored electric energy is calculated. In one embodiment, the clamping capacitor CcVoltage of capacitor VCcThe period T1 may be set smaller when the voltage value of (a) is higher or the stored electric energy is larger. In one embodiment, the period T1 may also be related to the control signal G 1、G2、G3… … or G4、G5、G6… … are identical in period. In the embodiment of the present application, the controller 114 controls and controls the auxiliary power tube Q in each periodHThe duration of the on or off may be the same or different.
Fig. 27 is a schematic diagram illustrating a change in capacitance voltage of a clamp capacitor of an ACF conversion circuit according to the present application. As shown in fig. 27, the clamp capacitor CcPeriodically discharged, clamping capacitor CcVoltage of capacitor VCcFrom VCc2Descending stepwise. At t3Time t4Between moments, clamp capacitor CcVoltage of capacitor VCcWith auxiliary power tube QHThe periodic conduction exhibits a stepwise decrease. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of the power supply circuit 113 also shows a step-like increase, and the output voltage V of the power supply circuit5Also exhibits a step-like increase in voltage value.
Thus, the controller 114 controls the clamp capacitor C in the ACF conversion circuit 111bcDischarge periodically to make the clamping capacitor CcVoltage of capacitor VCcThe stepped descending can avoid the influence of the quick descending on the operation of the ACF conversion circuit 111b, thereby improving the power supplyStability of the module 11. Furthermore, the controller 114 controls the clamp capacitor C in the ACF conversion circuit 111bcThe periodic discharge can cause the output voltage V of the auxiliary winding circuit 112 to be 4And an output voltage V of the power supply circuit 1135The step-type ground lifting avoids the circuit device damage caused by the too fast voltage lifting, thereby improving the stability of the power module 11.
Fig. 28 is a schematic diagram of another embodiment of a controller for controlling discharge of clamp capacitors of an ACF conversion circuit according to the present application. FIG. 28 is different from FIG. 26 in that the controller 114 controls the auxiliary power transistor Q in the primary winding circuit 1111b in the ACF conversion circuit 111bHAnd a main power tube QLPeriodically and alternately conducting to make the clamping capacitor CcIs discharged periodically.
At t3At that time, the controller 114 periodically controls the main power transistor QLAnd an auxiliary power tube QHAlternately conducted and controls the auxiliary power tube QHAnd a main power tube QLNot simultaneously conducting. Specifically, the controller 114 periodically and sequentially supplies the auxiliary power transistor Q with the electric powerHSending a second control signal GHSecondary power tube QLThe transmitted first control signal GLSo that the auxiliary power tube QHAnd a main power tube QLSequentially conducted and auxiliary power tube QHAnd a main power tube QLNot conducting at the same time. Auxiliary power tube Q of half-bridge circuit 1110bHWhen conducting, the primary winding 1111b and the clamping capacitor C of the half-bridge circuit 1110bcAuxiliary power tube Q of half-bridge circuit 1110bHA discharge loop may be formed. Clamping capacitor C cVoltage of capacitor VCcReference is made to fig. 27 for a variation of (c).
In one embodiment, the controller 114 controls the auxiliary power transistor Q each cycleHFirst-conducting main power tube QLThen conducting.
First, the controller 114 controls the auxiliary power transistor QHConducting main power tube QLAnd (5) cutting off. Specifically, the controller 114 supplies the auxiliary power transistor Q with the electric currentHSending a second control signal GHAnd does not supply the main power tube QLSending a first controlSignal GL. Accordingly, the clamping capacitor CcPrimary winding a and auxiliary power tube QHForming a current loop, clamping a capacitor CcAnd (4) discharging. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (1) is raised, and the output voltage V of the power circuit 113 is increased5The voltage value of (2) is raised.
The controller 114 then controls the auxiliary power transistor QHCut-off and main power tube QLAnd conducting. Specifically, the controller 114 does not supply the auxiliary power transistor QHSending a second control signal GHAnd to the main power tube QLSending a first control signal GL. At this time, the input voltage V1A primary winding a and a main power tube QLA loop is formed. Accordingly, the input voltage V1Generating a primary winding voltage V on both sides of a primary winding a11. Primary winding voltage V11Coupled via a transformer 1112b, an auxiliary winding voltage V is generated across the auxiliary winding c 3. Accordingly, the output voltage V of the auxiliary winding circuit 1124The voltage value of (3) is raised, and the output voltage V of the power supply circuit 113 is increased5The voltage value of (2) is raised.
Therefore, the controller 114 controls the clamp capacitance C of the primary winding circuit 1111b in the ACF conversion circuit 111bcDischarge periodically to make the clamping capacitor CcVoltage of capacitor VCcThe stepped drop avoids the operation of the ACF conversion circuit 111b being affected by the too fast drop, thereby improving the stability of the power module 111. Further, the controller 114 controls the clamp capacitance C of the primary winding circuit 1111b in the ACF conversion circuit 111bcThe periodic discharge can cause the output voltage V of the auxiliary winding circuit 1124And an output voltage V of the power supply circuit 1135The step-type lifting avoids damaging circuit devices due to too fast lifting, thereby improving the stability of the power module 111.
In one embodiment, the controller 114 may control the main power transistor Q every cycleLFirst-conducting auxiliary power tube QHThen conducting. In the embodiment of the present application, the controller 114 controls the main power transistor QLAnd an auxiliary power tube QHPeriodically alternateThe period T2 of conduction may be pre-configured or the controller 114 may be based on the current clamp capacitance CcVoltage of capacitor V CcOr the stored electric energy is calculated. In one embodiment, the clamping capacitor CcVoltage of capacitor VCcThe period T2 may be set smaller when the voltage value of (a) is higher or the stored electric energy is larger. In one embodiment, the period T2 may be related to the control signal G1、G2、G3… … period or G4、G5、G6… … are identical. In the embodiment of the present application, the controller 114 controls the main power transistor Q in each periodLDuration of conduction, control auxiliary power tube QHThe duration of the conduction may be the same or different. In the embodiment of the present application, the first control signal G sent by the controller 114LAnd a second control signal GHMay be the same or different.
In the scenario that the load level L of the power module 11 drops, the controller 114 provided in the embodiment of the present application only needs to control the main power transistor Q in the ACF conversion circuit 111bLAnd an auxiliary power tube QHOn or off. Therefore, the controller 114 provided in the embodiment of the present application can not only improve the stability of the ACF transformation circuit 111b, the power module 11, and the electronic device 10, but also simplify the configuration of the controller 114, so that the controller is more suitable for various products.
The present application further provides an electronic device including the controller 114 as provided in any embodiment of the present application, or including the power module 11 as provided in any embodiment of the present application.
In the foregoing embodiment, the method executed by the controller 114 provided in the embodiment of the present application is described, and in order to implement each function in the method provided in the embodiment of the present application, the controller 114 serving as an execution subject may include a hardware structure and/or a software module, and implement each function in the form of a hardware structure, a software module, or a hardware structure and a software module. Whether any of the above-described functions is implemented as a hardware structure, a software module, or a hardware structure plus a software module depends upon the particular application and design constraints imposed on the technical solution. It should be noted that the division of the modules of the above apparatus is only a logical division, and the actual implementation may be wholly or partially integrated into one physical entity, or may be physically separated. And these modules can all be implemented in the form of software invoked by a processing element; or can be implemented in the form of hardware; and part of the modules can be realized in the form of calling software by the processing element, and part of the modules can be realized in the form of hardware. The processing element may be a separate processing element, or may be integrated into a chip of the apparatus, or may be stored in a memory of the apparatus in the form of program code, and a processing element of the apparatus may call and execute the functions of the above determination module. Other modules are implemented similarly. In addition, all or part of the modules can be integrated together or can be independently realized. The processing element described herein may be an integrated circuit having signal processing capabilities. In implementation, each step of the above method or each module above may be implemented by an integrated logic circuit of hardware in a processor element or an instruction in the form of software. For example, the above modules may be one or more integrated circuits configured to implement the above methods, such as: one or more Application Specific Integrated Circuits (ASICs), or one or more microprocessors (DSPs), or one or more Field Programmable Gate Arrays (FPGAs), among others. For another example, when some of the above modules are implemented in the form of a processing element scheduler code, the processing element may be a general-purpose processor, such as a Central Processing Unit (CPU) or other processor that can call program code. As another example, these modules may be integrated together, implemented in the form of a system-on-a-chip (SOC).
In the above embodiments, the steps performed by the controller 114 may be implemented in whole or in part by software, hardware, firmware, or any combination thereof. When implemented in software, it may be implemented in whole or in part in the form of a computer program product. The computer program product includes one or more computer instructions. The procedures or functions described in accordance with the embodiments of the application are all or partially generated when the computer program instructions are loaded and executed on a computer. The computer may be a general purpose computer, a special purpose computer, a network of computers, or other programmable device. The computer instructions may be stored in a computer readable storage medium or transmitted from one computer readable storage medium to another, for example, from one website site, computer, server, or data center to another website site, computer, server, or data center via wired (e.g., coaxial cable, fiber optic, Digital Subscriber Line (DSL)) or wireless (e.g., infrared, wireless, microwave, etc.). The computer-readable storage medium can be any available medium that can be accessed by a computer or a data storage device, such as a server, a data center, etc., that includes one or more available media. The usable medium may be a magnetic medium (e.g., a floppy disk, a hard disk, a magnetic tape), an optical medium (e.g., a DVD), or a semiconductor medium (e.g., a Solid State Disk (SSD)), among others.
The present application also provides a computer-readable storage medium storing computer instructions that, when executed, may be used to perform a method performed by the controller 114 as in any of the previous embodiments of the present application.
Embodiments of the present application further provide a chip for executing instructions, where the chip is configured to perform any one of the methods performed by the controller 114 as described above in the present application.
Embodiments of the present application further provide a computer program product, which includes a computer program stored in a storage medium, from which the computer program can be read by at least one processor, and the computer program can be executed by the at least one processor, so as to implement the method performed by the controller 114 according to any one of the foregoing methods.
Those of ordinary skill in the art will understand that: all or a portion of the steps for implementing the above embodiments may be performed by hardware associated with program instructions. The foregoing program may be stored in a computer-readable storage medium. When executed, the program performs steps comprising the method embodiments described above; and the aforementioned storage medium includes: various media that can store program codes, such as ROM, RAM, magnetic or optical disks.
Those of ordinary skill in the art will understand that: for convenience of explaining the technical solution of the present application, the functional modules in the embodiments of the present application are described separately, and circuit devices in the respective modules may partially or completely overlap, which is not intended to limit the scope of the present application.
Finally, it should be noted that: the above embodiments are only used for illustrating the technical solutions of the present application, and not for limiting the same; although the present application has been described in detail with reference to the foregoing embodiments, it should be understood by those of ordinary skill in the art that: the technical solutions described in the foregoing embodiments may still be modified, or some or all of the technical features may be equivalently replaced; and the modifications or the substitutions do not make the essence of the corresponding technical solutions depart from the scope of the technical solutions of the embodiments of the present application.

Claims (13)

1. A controller for an active clamp flyback conversion circuit, the active clamp flyback conversion circuit comprising a half-bridge circuit, a transformer and a rectifying circuit, the half-bridge circuit comprising a main power tube, an auxiliary power tube and a clamp capacitor, the transformer comprising a primary winding, a secondary winding and an auxiliary winding circuit, the auxiliary winding circuit supplying power to a power circuit of the controller, the controller being characterized in that the controller is configured to:
Controlling the active clamp flyback conversion circuit to operate in a continuous working state, so that the output voltage of the active clamp flyback conversion circuit is a rated output voltage;
judging that the output voltage of the active clamp flyback conversion circuit is higher than a first preset value, and controlling the active clamp flyback conversion circuit to operate in a suspended working state; the first preset value is smaller than the overvoltage protection voltage of the active clamp flyback conversion circuit and larger than the rated output voltage of the active clamp flyback conversion circuit;
when the output voltage of the auxiliary winding circuit is judged to be less than or equal to a second preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the second preset value is smaller than the rated input voltage of the power circuit and larger than the undervoltage protection voltage of the power circuit; alternatively, the first and second electrodes may be,
when the output voltage of the power supply circuit is judged to be less than or equal to a third preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the third preset value is smaller than the rated input voltage of the controller and larger than the undervoltage protection voltage of the controller.
2. The controller of claim 1, wherein the controller is configured to:
And if the output voltage of the active clamping flyback conversion circuit is judged to be less than or equal to the rated output voltage, controlling the active clamping flyback conversion circuit to be switched from a suspended working state to a continuous working state.
3. The controller according to any one of claims 1-2, wherein the controller controls the active-clamp flyback converter circuit to operate in a suspended operation state, and comprises:
the controller controls the auxiliary power tube and the main power tube of the half-bridge circuit to be turned off.
4. The controller according to any one of claims 1-3, wherein the controller controls the clamp capacitor to discharge, comprising:
the controller controls the auxiliary power tube of the half-bridge circuit to be switched on and the main power tube of the half-bridge circuit to be switched off; alternatively, the first and second liquid crystal display panels may be,
the controller controls the auxiliary power tube of the half-bridge circuit to be periodically switched on and the main power tube of the half-bridge circuit to be switched off; alternatively, the first and second electrodes may be,
the controller controls the auxiliary power tube and the main power tube of the half-bridge circuit to be periodically and alternately switched on and off.
5. The controller according to any one of claims 1 to 4, wherein the controller is configured to:
if the capacitor voltage of the clamping capacitor is judged to be less than or equal to a preset capacitor voltage value, controlling the clamping capacitor to stop discharging; the preset capacitor voltage value is the voltage value of the capacitor voltage of the clamp capacitor when the active clamp flyback conversion circuit operates in a continuous working state; alternatively, the first and second electrodes may be,
If the output voltage of the auxiliary winding circuit is judged to be greater than or equal to a fourth preset value, the clamping capacitor is controlled to stop discharging; the fourth preset value is smaller than the overvoltage protection voltage of the power circuit and larger than the rated input voltage of the power circuit; alternatively, the first and second electrodes may be,
if the output voltage of the power supply circuit is judged to be greater than or equal to a fifth preset value, the clamping capacitor is controlled to stop discharging; the fifth preset value is larger than the rated input voltage of the controller and smaller than the overvoltage protection voltage of the controller.
6. The controller according to claim 5, wherein the controller controls the clamp capacitor to stop discharging, comprising:
the controller controls the auxiliary power tube of the half-bridge circuit to be turned off.
7. The utility model provides a power module, includes active clamp flyback converter circuit, auxiliary winding circuit, power supply circuit and controller, its characterized in that includes:
the active clamping flyback conversion circuit is used for receiving input voltage, performing voltage conversion processing on the input voltage and then providing output voltage for a load; the active clamp flyback converter circuit comprises: the power supply comprises a half-bridge circuit, a transformer and a rectifying circuit, wherein the half-bridge circuit comprises a main power tube, an auxiliary power tube and a clamping capacitor;
The auxiliary winding circuit is used for supplying power to the power supply circuit;
the power supply circuit is used for supplying power to the controller;
the controller is configured to:
controlling the active clamp flyback conversion circuit to operate in a continuous working state, wherein the output voltage of the active clamp flyback conversion circuit is a rated output voltage;
judging that the output voltage of the active clamp flyback conversion circuit is higher than a first preset value, and controlling the active clamp flyback conversion circuit to operate in a suspended working state; the first preset value is smaller than the overvoltage protection voltage of the active clamp flyback conversion circuit and larger than the rated output voltage of the active clamp flyback conversion circuit;
when the output voltage of the auxiliary winding circuit is judged to be less than or equal to a second preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the second preset value is smaller than the rated input voltage of the power circuit and larger than the undervoltage protection voltage of the power circuit; alternatively, the first and second electrodes may be,
when the output voltage of the power supply circuit is judged to be less than or equal to a third preset value, the clamping capacitor of the half-bridge circuit is controlled to discharge; the third preset value is smaller than the rated input voltage of the controller and larger than the undervoltage protection voltage of the controller.
8. The power module of claim 7, wherein the controller is configured to,
and if the output voltage of the active clamp flyback conversion circuit is judged to be less than or equal to the rated output voltage, controlling the active clamp flyback conversion circuit to be switched from a pause working state to a continuous working state.
9. The power module as claimed in any one of claims 7-8, wherein the controller controls the active-clamp flyback converter circuit to operate in a suspended state, including:
the controller controls the auxiliary power tube and the main power tube of the half-bridge circuit to be turned off.
10. The power module as claimed in any one of claims 7-9, wherein the controller controls the clamp capacitor to discharge, and comprises:
the controller controls the auxiliary power tube of the half-bridge circuit to be switched on and the main power tube of the half-bridge circuit to be switched off; alternatively, the first and second electrodes may be,
the controller controls the auxiliary power tube of the half-bridge circuit to be periodically switched on and the main power tube of the half-bridge circuit to be switched off; alternatively, the first and second electrodes may be,
the controller controls the auxiliary power tube and the main power tube of the half-bridge circuit to be periodically and alternately switched on and off.
11. The power module as claimed in any one of claims 7-10, wherein the controller is configured to:
If the capacitor voltage of the clamping capacitor is judged to be less than or equal to a preset capacitor voltage value, controlling the clamping capacitor to stop discharging; the preset capacitor voltage value is the voltage value of the capacitor voltage of the clamp capacitor when the active clamp flyback conversion circuit operates in a continuous working state; alternatively, the first and second electrodes may be,
if the output voltage of the auxiliary winding circuit is judged to be greater than or equal to a fourth preset value, the clamping capacitor is controlled to stop discharging; the fourth preset value is smaller than the overvoltage protection voltage of the power circuit and larger than the rated input voltage of the power circuit; alternatively, the first and second electrodes may be,
if the output voltage of the power supply circuit is judged to be greater than or equal to a fifth preset value, the clamping capacitor is controlled to stop discharging; the fifth preset value is larger than the rated input voltage of the controller and smaller than the overvoltage protection voltage of the controller.
12. The power module as claimed in claim 11, wherein the controller controls the clamp capacitor to stop discharging, and comprises:
the controller controls the auxiliary power tube of the half-bridge circuit to be turned off.
13. An electronic device comprising a controller of an active-clamp flyback converter circuit as claimed in any of claims 1-6, or comprising a power module as claimed in any of claims 7-12.
CN202210374393.7A 2022-04-11 2022-04-11 Controller of active clamping flyback conversion circuit, power supply module and electronic equipment Pending CN114759796A (en)

Priority Applications (2)

Application Number Priority Date Filing Date Title
CN202210374393.7A CN114759796A (en) 2022-04-11 2022-04-11 Controller of active clamping flyback conversion circuit, power supply module and electronic equipment
PCT/CN2022/140116 WO2023197660A1 (en) 2022-04-11 2022-12-19 Controller for active clamp flyback conversion circuit, power source module, and electronic device

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202210374393.7A CN114759796A (en) 2022-04-11 2022-04-11 Controller of active clamping flyback conversion circuit, power supply module and electronic equipment

Publications (1)

Publication Number Publication Date
CN114759796A true CN114759796A (en) 2022-07-15

Family

ID=82329506

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202210374393.7A Pending CN114759796A (en) 2022-04-11 2022-04-11 Controller of active clamping flyback conversion circuit, power supply module and electronic equipment

Country Status (2)

Country Link
CN (1) CN114759796A (en)
WO (1) WO2023197660A1 (en)

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023197660A1 (en) * 2022-04-11 2023-10-19 华为数字能源技术有限公司 Controller for active clamp flyback conversion circuit, power source module, and electronic device

Family Cites Families (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US10148188B2 (en) * 2016-09-06 2018-12-04 Fairchild Semiconductor Corporation Clamp voltage detection and over-voltage protection for power supply topologies
US10141853B2 (en) * 2017-02-09 2018-11-27 Delta Electronics, Inc. Power converter and method of control thereof
CN110957915B (en) * 2018-09-27 2021-09-07 通嘉科技股份有限公司 Active clamping flyback power converter capable of switching operation modes
CN110572037B (en) * 2019-09-05 2020-12-18 深圳南云微电子有限公司 Control method and circuit of active clamp flyback converter
CN110677045B (en) * 2019-09-20 2020-09-15 广州金升阳科技有限公司 Control method of active clamp flyback converter
CN114759796A (en) * 2022-04-11 2022-07-15 上海华为数字能源技术有限公司 Controller of active clamping flyback conversion circuit, power supply module and electronic equipment
CN114759763A (en) * 2022-04-11 2022-07-15 上海华为数字能源技术有限公司 Controller, power module and electronic equipment of asymmetric half-bridge conversion circuit

Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
WO2023197660A1 (en) * 2022-04-11 2023-10-19 华为数字能源技术有限公司 Controller for active clamp flyback conversion circuit, power source module, and electronic device

Also Published As

Publication number Publication date
WO2023197660A1 (en) 2023-10-19

Similar Documents

Publication Publication Date Title
KR102138109B1 (en) Adapter and charging control method
US10790696B2 (en) Charging device and method, power adapter and terminal
US9960686B2 (en) System and method for detecting a loss of AC power in a switched-mode power supply
CN114759763A (en) Controller, power module and electronic equipment of asymmetric half-bridge conversion circuit
US20160118900A1 (en) Power supply adaptor
EP2557656A1 (en) Power-fail retaining circuit, method and power supply system
JP6255577B2 (en) DC power supply circuit
US20190260218A1 (en) Charging system, charging method, and power adapter
TWI774085B (en) Pulse width modulation control chip and power conversion system
US20230198371A1 (en) Power source providing apparatus, and charging method and system
TWI649947B (en) Control module with active surge absorber and related flyback power conversion device
US10110058B2 (en) Power conversion device and method for preventing abnormal shutdown thereof
CN110380619B (en) Direct current conversion circuit, control method thereof and direct current conversion device
CN114759796A (en) Controller of active clamping flyback conversion circuit, power supply module and electronic equipment
EP3276780B1 (en) Charging device and method, power adapter and terminal
WO2024016301A1 (en) Control circuit for asymmetrical half-bridge flyback circuit, power supply module, and electronic device
US20230198280A1 (en) Charging circuit, terminal device, adapter, and charging system and method
US20220037985A1 (en) Power generation and zvs control in a power supply
US9948189B2 (en) Power conversion device and method for correcting decision threshold level thereof
CN115459579A (en) Power module, electronic equipment and control circuit of power factor correction circuit
JP6274209B2 (en) Information processing apparatus and power supply circuit

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination