CN113962094B - High-frequency transformer optimization design method comprehensively considering vibration noise - Google Patents

High-frequency transformer optimization design method comprehensively considering vibration noise Download PDF

Info

Publication number
CN113962094B
CN113962094B CN202111244996.7A CN202111244996A CN113962094B CN 113962094 B CN113962094 B CN 113962094B CN 202111244996 A CN202111244996 A CN 202111244996A CN 113962094 B CN113962094 B CN 113962094B
Authority
CN
China
Prior art keywords
loss
winding
magnetic core
frequency transformer
inspection
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Active
Application number
CN202111244996.7A
Other languages
Chinese (zh)
Other versions
CN113962094A (en
Inventor
张鹏宁
李伟
李博凡
苏景豪
郝玉垚
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
China University of Mining and Technology Beijing CUMTB
Original Assignee
China University of Mining and Technology Beijing CUMTB
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by China University of Mining and Technology Beijing CUMTB filed Critical China University of Mining and Technology Beijing CUMTB
Priority to CN202111244996.7A priority Critical patent/CN113962094B/en
Publication of CN113962094A publication Critical patent/CN113962094A/en
Application granted granted Critical
Publication of CN113962094B publication Critical patent/CN113962094B/en
Active legal-status Critical Current
Anticipated expiration legal-status Critical

Links

Images

Classifications

    • G—PHYSICS
    • G06—COMPUTING; CALCULATING OR COUNTING
    • G06F—ELECTRIC DIGITAL DATA PROCESSING
    • G06F30/00—Computer-aided design [CAD]
    • G06F30/20—Design optimisation, verification or simulation
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F41/00—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F41/00—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties
    • H01F41/02—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties for manufacturing cores, coils, or magnets
    • H01F41/0206—Manufacturing of magnetic cores by mechanical means
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01F—MAGNETS; INDUCTANCES; TRANSFORMERS; SELECTION OF MATERIALS FOR THEIR MAGNETIC PROPERTIES
    • H01F41/00—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties
    • H01F41/02—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties for manufacturing cores, coils, or magnets
    • H01F41/04—Apparatus or processes specially adapted for manufacturing or assembling magnets, inductances or transformers; Apparatus or processes specially adapted for manufacturing materials characterised by their magnetic properties for manufacturing cores, coils, or magnets for manufacturing coils

Landscapes

  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Manufacturing & Machinery (AREA)
  • Physics & Mathematics (AREA)
  • Theoretical Computer Science (AREA)
  • Computer Hardware Design (AREA)
  • Evolutionary Computation (AREA)
  • Geometry (AREA)
  • General Engineering & Computer Science (AREA)
  • General Physics & Mathematics (AREA)
  • Coils Or Transformers For Communication (AREA)

Abstract

The application discloses a high-frequency transformer optimal design method comprehensively considering vibration noise, which comprises the following steps: designing a magnetic core design scheme of the high-frequency transformer to obtain magnetic core design parameters; designing a winding design scheme of the high-frequency transformer to obtain winding design parameters; according to the design parameters of the magnetic core and the winding, carrying out loss inspection, temperature rise inspection and efficiency inspection; and calculating vibration noise to carry out vibration noise inspection. The method is easy to be applied to engineering practice, is convenient for the rapid optimization design of the high-frequency transformer, optimizes the structure of the high-frequency transformer, and has important theoretical and engineering guiding significance.

Description

High-frequency transformer optimization design method comprehensively considering vibration noise
Technical Field
The application belongs to the technical field of high-frequency transformers, and particularly relates to a high-frequency transformer optimization design method comprehensively considering vibration noise.
Background
In recent years, the problem of environmental pollution is increasingly prominent, the energy crisis is gradually increased, pollution-free renewable energy sources such as solar energy, wind energy and the like are increasingly emphasized, and the advantages of large resource amount and recyclability of clean energy sources are not possessed by traditional energy sources, so that the pollution-free renewable energy sources are the key points of development and utilization. Due to the randomness and the fluctuation of wind energy and light energy, the energy router plays an important role in the stable operation of the new energy power generation system and the dispatching of a power grid with the advantages of energy transmission and conversion and electric energy quality control. The traditional transformer has the problems of large volume, large energy consumption ratio, difficulty in control and the like, and the requirement of a new energy power grid on the transformer is difficult to meet. With the development of power electronic technology and the breakthrough of new materials, power electronic transformers with high frequency, high power and large capacity are applied to the fields of energy routers and the like.
A Power Electronic Transformer (Power Electronic Transformer) is also called a Solid-State Transformer (Solid-State Transformer), and generally refers to a novel Transformer based on a Power Electronic technology, and has various functions, and is suitable for the connection of a plurality of micro-grids and a novel energy structure. The High-frequency Transformer (HFT) has the advantages of small volume, large capacity, low weight, strong controllability, large power density, alternating current and direct current mixing and the like, is an indispensable core device in a power electronic Transformer, and has important significance for alternating current and direct current mixing networks, micro-grids, photovoltaics, wind power, flexible looped networks and the like. HFTs are small in size and weight, and have a high power density, making them better suited for use in energy routers.
Due to the use of the novel magnetic material with high magnetic permeability and high saturation magnetic flux density, the high-frequency transformer has the characteristics of smaller volume and higher power density. But the higher the operating frequency, the greater its losses, vibrations and noise under the influence of high frequency effects. At present, the vibration noise of the high-frequency transformer is not taken as a constraint condition of the optimization design, but the serious vibration noise of the high-frequency transformer affects the service life of the high-frequency transformer, so that the body structure of the high-frequency transformer needs to be optimized and designed by comprehensively considering efficiency, loss, leakage inductance, temperature rise, insulation and vibration noise.
Disclosure of Invention
The method for optimizing the design of the high-frequency transformer comprehensively considering the vibration noise comprises the steps of preliminarily designing key parameters of the high-frequency transformer to form a preliminary design scheme, and optimizing parameter design to obtain an optimal design scheme through multiple tests on the design scheme, particularly establishing a verification mode of the vibration noise.
In order to achieve the above purpose, the present application provides the following solutions:
a high-frequency transformer optimization design method comprehensively considering vibration noise comprises the following steps:
s1, designing a magnetic core design scheme of the high-frequency transformer to obtain magnetic core design parameters, wherein the magnetic core design parameters comprise magnetic core size and air gap length;
s2, designing a winding design scheme of the high-frequency transformer according to the magnetic core parameters to obtain winding design parameters, wherein the winding design parameters comprise winding turns, wire diameter and wire strand number;
s3, according to the magnetic core design parameters and the winding design parameters, conducting loss inspection, temperature rise inspection and efficiency inspection, if the results of the loss inspection, the temperature rise inspection and the efficiency inspection meet the design requirements, turning to S4, if the results of the loss inspection and/or the temperature rise inspection and/or the efficiency inspection do not meet the design requirements, adjusting the magnetic core design parameters, and repeating S1-S3;
s4, carrying out vibration noise calculation according to the magnetic core design parameters and the winding design parameters, if the result of the vibration noise calculation meets the design requirements, the magnetic core design parameters and the winding design parameters are the optimal magnetic core parameters and the optimal winding parameters, if the result of the vibration noise calculation does not meet the design requirements, the magnetic core design parameters are adjusted, and S1-S4 are repeated.
Preferably, in S1, the size of the magnetic core is obtained by an area product AP method.
Preferably, in S1, the air gap length is obtained according to a core saturation threshold and a magnetic permeability.
Preferably, in S2, the number of winding turns is obtained based on the area product AP method.
Preferably, the loss test includes a winding loss test and a core loss test.
Preferably, before the winding loss inspection, fourier decomposition is performed on the non-sinusoidal excitation applied to the high-frequency transformer;
the formula for calculating the corrected winding loss under non-sinusoidal excitation is as follows:
Figure BDA0003320549160000031
preferably, the magnetic core loss inspection is performed according to the ratio of the eddy current loss and the residual loss under the non-sinusoidal excitation to the eddy current loss under the sinusoidal excitation;
the total loss at non-sinusoidal is:
Figure BDA0003320549160000041
when considering the skin effect, the total loss is:
Figure BDA0003320549160000042
wherein C ish、Ce、CaAlpha and beta are loss coefficients, ReAnd RaThe ratios of eddy current loss, residual loss and sinusoidal excitation decomposition loss are respectively.
Preferably, the efficiency check is performed based on an optimal working magnetic flux density;
the optimal magnetic flux density is:
Figure BDA0003320549160000043
preferably, in S4, the vibration equation for calculating the vibration noise is
Figure BDA0003320549160000044
Where m is the mass matrix, k is the stiffness matrix, and u is the displacement vector. FvmsIs the magnetostrictive volume force, FvmaxIs the maxwell volumetric force.
The beneficial effect of this application does:
the application discloses a high-frequency transformer optimization design method comprehensively considering vibration noise, which forms a preliminary design scheme by preliminarily designing key parameters of the high-frequency transformer, optimizes parameter design by multiple tests on the design scheme, particularly establishes a verification mode of the vibration noise, and obtains an optimal design scheme; the structure of the high-frequency transformer is optimally designed by combining factors such as efficiency, temperature rise, leakage inductance, winding parameters, magnetic core parameters, vibration noise and the like, and the method has important theoretical and engineering guiding significance; the method and the device can prolong the service life of the high-frequency transformer, promote environmental friendliness around the high-frequency transformer, and have good engineering practical value.
Drawings
In order to more clearly illustrate the technical solution of the present application, the drawings needed to be used in the embodiments are briefly introduced below, and it is obvious that the drawings in the following description are only some embodiments of the present application, and it is obvious for those skilled in the art that other drawings can be obtained according to these drawings without inventive exercise.
Fig. 1 is a schematic flow chart of a high-frequency transformer optimization design method comprehensively considering vibration noise in an embodiment of the present application.
Detailed Description
The technical solutions in the embodiments of the present application will be clearly and completely described below with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present application.
In order to make the aforementioned objects, features and advantages of the present application more comprehensible, the present application is described in further detail with reference to the accompanying drawings and the detailed description.
The technical scheme comprehensively considers factors such as a magnetic core, a winding, temperature rise, vibration noise and the like of the target transformer. And selecting a magnetic core scheme, selecting a winding scheme, arranging transformer insulation and heat dissipation, calculating the efficiency and temperature rise limit of the model, finally calculating the vibration noise value of the high-frequency transformer, and returning to redesign if the vibration noise value does not meet the requirement. The design flow of the high-frequency transformer in the embodiment of the application is shown in fig. 1, and mainly comprises the following steps:
the design of the transformer firstly needs to select a proper magnetic core material according to target design parameters, and the parameters of the selected soft magnetic material are closely related to the performance of the designed high-frequency transformer. At present, silicon steel sheets, ferrite and amorphous alloy have various limitations or defects, and nanocrystalline serving as a novel soft magnetic material has excellent characteristics enough to meet the performance requirements of the high-frequency transformer at present. After the magnetic core material is determined, the structure of the magnetic core needs to be determined, and the common magnetic core structure is shown in table 1.
TABLE 1
Figure BDA0003320549160000061
After selecting the core material, it is generally necessary to determine whether the core is open to air gap, and to consider the core heat dissipation, electromagnetic shielding, winding method, etc.
S1, designing a magnetic core design scheme of the high-frequency transformer to obtain magnetic core design parameters including magnetic core size and air gap length.
S1.1 determining magnetic core size
After the magnetic core material is selected, the effective sectional area of the magnetic core is often calculated, and generally, the two methods, namely an area product AP method and a geometric coefficient KG method, are commonly used.
The AP method (Area Product) is simple and clear in calculation and is a transformer design method widely applied in the current engineering. The principle is that the window area A of the magnetic core is depended onwAnd the effective cross-sectional area A of the magnetic coreeFind ApAnd selecting the size of the magnetic core meeting the requirement by referring to the model of the manufacturer. Area of window AwEffective cross-sectional area A in relation to the spatial position of the windingeIn relation to the maximum power of the core, it can be approximately equal to the geometric cross-sectional area of the core.
The AP value selected in the actual engineering is generally larger than the theoretical calculation value so as to ensure the performance requirement of the transformer. The calculation formula of the AP method is Ap＝Aw·Ae. The apparent power of the target transformer can be determined.
According to Faraday's law of electromagnetic induction, there are
Figure BDA0003320549160000071
In the above formula, N1B is the flux density in the core, ω is the angular frequency of excitation, and t is the time, for the number of primary winding turns.
The effective value of the voltage excited by the sine wave can be obtained (in the embodiment, the voltage and the current are effective values if nothing specially mentioned)
Figure BDA0003320549160000072
Defining the form factor of a sine wave excitation
Figure BDA0003320549160000073
To facilitate the analysis of non-sinusoidal waveform excitation, a conceptual form factor is introduced in this embodiment
Figure BDA0003320549160000074
Wherein
Figure BDA0003320549160000075
Is the average value of the voltage.
The form factor of the sine wave excitation
Figure BDA0003320549160000076
Wherein U ispAt the peak voltage, it is clear that the two differ by a factor of four. Here, the form factors of several common excitation waveforms are summarized as shown in Table 2 (the average value of the waveforms due to existence)
Figure BDA0003320549160000077
Zero, in which case the mean absolute value is substituted
Figure BDA0003320549160000078
Instead of calculation).
TABLE 2
Figure BDA0003320549160000081
For the primary side of the high-frequency transformer, the following components are adopted:
Figure BDA0003320549160000082
the primary winding number calculation formula can be obtained as follows:
Figure BDA0003320549160000083
the same can be obtained:
Figure BDA0003320549160000091
in the above formula, T is the average turn length of the winding, U1And U2The effective values of the voltage of the primary and secondary windings, respectively, when the windings are fully utilized, the current density J, the window filling factor K, are recordedwGuide, leadThe cross-sectional area of the wire is:
Figure BDA0003320549160000092
in the above formula, I1And I2The current effective values of the primary winding and the secondary winding are respectively.
Can obtain the area of the magnetic core window as
Figure BDA0003320549160000093
And substituting and arranging to obtain an AP method calculation formula.
Figure BDA0003320549160000094
The apparent power of the transformer has a relation S ═ P1+P2，P1And P2For the actual transmission power and the target output power of the transformer, the efficiency of the transformer
Figure BDA0003320549160000095
Substitution can obtain:
Figure BDA0003320549160000096
s1.2 determining the air gap length
The core is air-gapped to prevent saturation, but the air-gap length is selected to be appropriate. In practical engineering, a magnetic core with a ring-shaped notch (Air Gap) is often used. After the air gap is formed in the magnetic core, although the magnetic conductivity is reduced and leakage magnetic flux is generated, the maximum magnetic field intensity in the magnetic core is reduced, the residual magnetism is also reduced, the B-H magnetic hysteresis loop of the magnetic core drifts to the right, the saturation phenomenon of the magnetic core is greatly improved, the energy storage is increased, the direct current superposition characteristic is improved, and the leakage magnetic flux under direct current bias is smaller.
The larger the air gap is, the higher the saturation threshold of the magnetic core is, but the larger the air gap is, the lower the magnetic permeability, the lower the structural stability, the higher the cost and the like. Therefore, the air gap length needs to be comprehensively considered in combination with the actual situation.
In this embodiment, the air gap length calculation method includes:
Figure BDA0003320549160000101
in the above formula, N1Is the number of turns, BmIs peak magnetic flux density, mucIs relative magnetic permeability, I0For no-load current, magnetic circuit length lcIt can be known by the core manufacturer's manual that no-load tests can be passed.
And S2, designing a winding design scheme of the high-frequency transformer according to the magnetic core parameters to obtain winding design parameters including the number of turns of the winding, the wire diameter of the wire and the number of strands of the wire.
S2.1 determining the number of winding turns
The calculation method of the number of turns of the primary winding and the secondary winding is obtained in the calculation process of the AP method, and the specific formula is as follows:
Figure BDA0003320549160000102
in the above formula, U1Is the rated voltage of the primary winding, KfThe form factor, k, of a sine wave excitationfIs a form factor, AeThe effective sectional area of the magnetic core, B is the working magnetic density, and f is the excitation frequency.
S2.2 determining the wire diameter and strand number of the wire
In this embodiment, the wire diameter is selected to be approximately twice the skin depth. If a stranded wire is selected, the number of strands can be calculated by current density:
Figure BDA0003320549160000111
in the above formula, A is the sectional area of the wire, I is the effective value of the current, and r is the single-strand wireD is the wire diameter of the single-strand wire, NsThe number of strands of the litz wire.
And S3, carrying out loss inspection, temperature rise inspection and efficiency inspection according to the magnetic core design parameters and the winding design parameters, turning to S4 if the results of the loss inspection, the temperature rise inspection and the efficiency inspection meet the design requirements, adjusting the magnetic core design parameters if the results of the loss inspection and/or the temperature rise inspection and/or the efficiency inspection do not meet the design requirements, and repeating S1-S3.
S3.1 loss test
After the scheme of the magnetic core and the winding is designed, the loss characteristic needs to be calculated, and whether the efficiency of the transformer meets the requirement or not is checked. The high-frequency transformer loss is divided into a winding loss and a magnetic core loss.
1) Winding loss of high-frequency transformer
The Winding loss (Winding Losses) means that the alternating current resistance is greatly increased due to the aggravation of skin effect and proximity effect under the condition of high frequency of a Winding lead, and redundant heating loss is generated. Non-sinusoidal excitation (square wave and the like) is usually added to a high-frequency transformer in engineering, while the application scene of the original Dowlel model is sinusoidal waveform excitation, and Fourier decomposition and respective calculation are required to be carried out on the non-sinusoidal excitation. Therefore, the formula for calculating the corrected winding loss under non-sinusoidal excitation is as follows:
Figure BDA0003320549160000121
wherein R isacIs an alternating current resistance, RdcIs a direct current resistance, IdcIs an effective value of the component of the direct current IrmsThe effective value of the non-sinusoidal current. At n-th harmonic, RancIs an alternating current resistance, IrmsnIs the effective value of the harmonic current, FrnIs the ac winding coefficient.
2) High frequency transformer core loss
With the same core, the hysteresis loss is not changed as long as the frequency and the magnetic flux density are not changed. I.e. non-sinusoidal waveform excitation, only the influence of the other two losses on the loss separation method formula is considered. And measuring the change condition of the magnetic core loss by the ratio of the eddy current loss and the residual loss under the non-sinusoidal waveform to the eddy current loss under the sine waveform. The total loss at non-sinusoidal is:
Figure BDA0003320549160000122
when considering the skin effect, the total loss is:
Figure BDA0003320549160000123
wherein C ish、Ce、CaAlpha and beta are loss coefficients, BmPeak value of magnetic flux density, ReAnd RaThe ratios of eddy current loss, residual loss and sinusoidal excitation decomposition loss are respectively.
S3.2 temperature rise test
In the embodiment, the calculation formula for solving the temperature rise Δ T of the transformer in the engineering is used as follows:
Figure BDA0003320549160000124
in the above formula: ksThe temperature rise coefficient depends on the magnetic core. P is the total loss of the transformer. By the aid of the calculated temperature rise of the high-frequency transformer, the maximum capacity of the high-frequency transformer can be calculated under the condition that the temperature rise limit of the high-frequency transformer is met by setting the structure and the size of the magnetic core of the high-frequency transformer, and the high-frequency transformer can be designed better.
S3.3 efficiency test
In the high-frequency transformer, under the condition that the size and the structure of the magnetic core are fixed, the optimal working magnetic flux density needs to be considered and selected so as to achieve the minimum total loss of the high-frequency transformer, namely, the efficiency needs to be optimized.
Combining the loss characteristic analysis of the high-frequency transformer, the loss calculation method of the high-frequency transformer is as follows:
Figure BDA0003320549160000131
Figure BDA0003320549160000132
wherein. f is the excitation frequency, Pw1And Pw2Is the primary and secondary winding loss, Fr1And Fr2The AC resistivity of the primary and secondary windings, I1And I2Respectively, the effective value of the primary and secondary winding current, VcIs the volume of the magnetic core, KmIs a magnetic core loss characteristic parameter, N is the number of turns of primary and secondary windings, TmlThe average turn length of the primary and secondary windings is shown, and rho is the resistivity.
The winding turn number calculation formula is as follows:
Figure BDA0003320549160000133
wherein A iseIs the effective cross-sectional area of the magnetic core, BmFor peak working flux density, UiThe rated voltage of the primary side or the secondary side winding.
The total loss of the transformer is as follows:
Figure BDA0003320549160000141
the magnetic flux density of the above formula is derived, and the optimal magnetic flux density is obtained by sorting:
Figure BDA0003320549160000142
in order to obtain the optimal magnetic flux density with the highest efficiency when designing the transformer, a set initial magnetic flux density is needed, and then relevant parameters are calculated to obtain the optimal solution of the magnetic flux density. Then, each parameter of the high-frequency transformer needs to be recalculated according to the obtained optimal magnetic flux density, redesigning is carried out, and finally a design scheme is determined.
S4, carrying out vibration noise calculation according to the magnetic core design parameters and the winding design parameters, if the result of the vibration noise calculation meets the design requirements, the magnetic core design parameters and the winding design parameters are the optimal magnetic core parameters and the optimal winding parameters, if the result of the vibration noise calculation does not meet the design requirements, the magnetic core design parameters are adjusted, and S1-S4 are repeated.
For the calculation of the vibration of the high-frequency transformer, the intrinsic magnetostrictive model of the soft magnetic material from the viewpoint of mechanical and internal energy conservation is as follows
Figure BDA0003320549160000143
Figure BDA0003320549160000144
Figure BDA0003320549160000151
In the above formula, M is the magnetization in the core, and θ is a step function, εpIs the elastic strain under prestress. The first term in equation (20) is the prestress σpWherein E is the intrinsic young's modulus. Lambda (sigma)p) Is the initial magnetostrictive strain εcFor total magnetostrictive strain, Ms(σp) For saturating the wall-moving magnetization, lambda, under the action of prestressing forcem(0) Is the saturated magnetostriction coefficient measured by the magnetic ring.
The two-dimensional Maxwell stress method shows that FmaxCan pass through the Maxwell stress tensor TmThe surface area of (a) is calculated by the following formula:
Figure BDA0003320549160000152
in the above formula, BxAnd ByIs the magnetic flux density in the x-axis and y-axis directions, HxAnd HyIs the magnetic field strength in the x-axis and y-axis directions, nxAnd nyIs a normal vector in the x-axis and y-axis directions, TmIs a second order tensor, and S is a closed surface surrounding the entire magnetic mass in air.
According to the theory of elastic mechanics, considering the orthotropic properties of magnetic materials, the two-dimensional stress strain constitutive relation is as follows:
Figure BDA0003320549160000161
in the above formula, σ is normal stress, τ is shear stress, ν is poisson's ratio, E is elastic modulus, epsilon is normal strain, and γ is shear strain.
The damping effect of the high-frequency transformer core is negligible, so the vibration equation can be simplified as follows:
Figure BDA0003320549160000162
in the above equation, m is a mass matrix, k is a stiffness matrix, and u is a displacement vector. FvmsIs the magnetostrictive volume force, FvmaxIs the maxwell volumetric force.
In the acoustic model, the surface velocity or acceleration of the high-frequency transformer core is applied to the boundary of the solid-air interface, and the relationship with the sound pressure is as follows:
Figure BDA0003320549160000163
in the above formula, the first and second carbon atoms are,
Figure BDA0003320549160000164
is a normal vector pointing outwards from the inside of the high-frequency transformer,
Figure BDA0003320549160000165
and
Figure BDA0003320549160000166
the normal acceleration and the surface velocity of the high-frequency transformer core, respectively. p is a radical oftIs the total sound pressure, i.e. the sum of the sound pressure generated by the high-frequency transformer and the background sound pressure, p is the density of the medium,
Figure BDA0003320549160000167
in the form of a normal acceleration, the acceleration,
Figure BDA0003320549160000168
is the normal velocity.
The above-described embodiments are merely illustrative of the preferred embodiments of the present application, and do not limit the scope of the present application, and various modifications and improvements made to the technical solutions of the present application by those skilled in the art without departing from the spirit of the present application should fall within the protection scope defined by the claims of the present application.

Claims (9)

1. A high-frequency transformer optimization design method comprehensively considering vibration noise is characterized by comprising the following steps:
s1, designing a magnetic core design scheme of a high-frequency transformer to obtain magnetic core design parameters, wherein the magnetic core design parameters comprise magnetic core size and air gap length;
s2, designing a winding design scheme of the high-frequency transformer according to the magnetic core design parameters to obtain winding design parameters, wherein the winding design parameters comprise winding turns, wire diameter and wire strand number;
s3, according to the magnetic core design parameters and the winding design parameters, conducting loss inspection, temperature rise inspection and efficiency inspection, if the results of the loss inspection, the temperature rise inspection and the efficiency inspection meet the design requirements, turning to S4, if the results of the loss inspection and/or the temperature rise inspection and/or the efficiency inspection do not meet the design requirements, adjusting the magnetic core design parameters, and repeating S1-S3;
s4, carrying out vibration noise calculation according to the magnetic core design parameters and the winding design parameters, if the result of the vibration noise calculation meets the design requirements, the magnetic core design parameters and the winding design parameters are the optimal magnetic core parameters and the optimal winding parameters, if the result of the vibration noise calculation does not meet the design requirements, the magnetic core design parameters are adjusted, and S1-S4 are repeated.
2. The method for optimally designing a high frequency transformer considering vibration noise in combination as set forth in claim 1, wherein in said S1, the size of said magnetic core is obtained by an area product AP method.
3. The method as claimed in claim 2, wherein in S1, the air gap length is obtained according to a core saturation threshold and a magnetic permeability.
4. The method as claimed in claim 2, wherein in S2, the number of winding turns is obtained based on the area product AP method.
5. The method of claim 1, wherein the loss test includes a winding loss test and a core loss test.
6. The method for optimally designing a high-frequency transformer comprehensively considering vibration noise according to claim 5, wherein before the winding loss inspection is carried out, Fourier decomposition is carried out on non-sinusoidal excitation applied to the high-frequency transformer;
the formula for calculating the corrected winding loss under non-sinusoidal excitation is as follows:
Figure FDA0003562174180000021
Racis an alternating current resistance, RdcIs a direct current resistance, IdcIs an effective value of the component of the direct current IrmsIs a non-sinusoidal current with effective value, R, at n harmonicsacnIs an alternating current resistance, IrmsnIs the effective value of the harmonic current, FrnIs the ac winding coefficient.
7. The method for optimally designing a high-frequency transformer with comprehensive consideration of vibration noise according to claim 6, wherein the magnetic core loss inspection is performed according to the ratio of the eddy current loss under the non-sinusoidal excitation, the residual loss and the sinusoidal excitation;
the total loss at non-sinusoidal is:
Figure FDA0003562174180000022
when considering the skin effect, the total loss is:
Figure FDA0003562174180000031
wherein C ish、Ce、CaAlpha and beta are loss coefficients, ReAnd RaThe ratios of eddy current loss, residual loss and sinusoidal excitation decomposition loss are respectively;
Bmis the peak magnetic flux density; f is the excitation frequency.
8. The high-frequency transformer optimal design method comprehensively considering vibration noise according to claim 1, characterized in that the efficiency test is performed based on an optimal working magnetic flux density;
the optimal magnetic flux density is:
Figure FDA0003562174180000032
f is the excitation frequency; fr1And Fr2The AC resistivity of the primary and secondary windings, I1And I2Respectively, the effective value of the primary and secondary winding current, VcIs the volume of the magnetic core, KmFor core loss characteristic parameters, U1And U2Effective values of the voltages of the primary and secondary windings, respectively; a. theeThe effective cross-sectional area of the core.
9. The method as claimed in claim 1, wherein in step S4, the vibration equation for calculating the vibration noise is as follows
Figure FDA0003562174180000033
Where m is the mass matrix, k is the stiffness matrix, u is the displacement vector, FvmsIs the magnetostrictive volume force, FvmaxMaxwell volume force, t is time.
CN202111244996.7A 2021-10-26 2021-10-26 High-frequency transformer optimization design method comprehensively considering vibration noise Active CN113962094B (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202111244996.7A CN113962094B (en) 2021-10-26 2021-10-26 High-frequency transformer optimization design method comprehensively considering vibration noise

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202111244996.7A CN113962094B (en) 2021-10-26 2021-10-26 High-frequency transformer optimization design method comprehensively considering vibration noise

Publications (2)

Publication Number Publication Date
CN113962094A CN113962094A (en) 2022-01-21
CN113962094B true CN113962094B (en) 2022-04-26

Family

ID=79466920

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202111244996.7A Active CN113962094B (en) 2021-10-26 2021-10-26 High-frequency transformer optimization design method comprehensively considering vibration noise

Country Status (1)

Country Link
CN (1) CN113962094B (en)

Families Citing this family (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN115343663A (en) * 2022-08-12 2022-11-15 保定天威顺达变压器有限公司 Transformer winding monitoring device

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105118647A (en) * 2015-08-28 2015-12-02 华北电力大学 Determining method for optimal working frequency of large-capacity high-frequency transformer
CN105183947A (en) * 2015-08-12 2015-12-23 华北电力大学 Parasitic parameter effect analysis based high-frequency transformer transmission characteristic optimization method
CN105183992A (en) * 2015-09-08 2015-12-23 国网智能电网研究院 Determining method for maximum design capacity of high-frequency transformer
CN110556233A (en) * 2019-09-02 2019-12-10 清华大学 Serialized leakage inductance integrated high-frequency transformer structure and implementation method
CN113486548A (en) * 2021-06-17 2021-10-08 浙江大学 Design method of high-capacity medium-voltage high-frequency transformer

Family Cites Families (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN102708262B (en) * 2012-06-07 2014-07-23 蒋雪峰 Comprehensive energy-saving and noise-reduction multi-target optimal design method for power transformer

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN105183947A (en) * 2015-08-12 2015-12-23 华北电力大学 Parasitic parameter effect analysis based high-frequency transformer transmission characteristic optimization method
CN105118647A (en) * 2015-08-28 2015-12-02 华北电力大学 Determining method for optimal working frequency of large-capacity high-frequency transformer
CN105183992A (en) * 2015-09-08 2015-12-23 国网智能电网研究院 Determining method for maximum design capacity of high-frequency transformer
CN110556233A (en) * 2019-09-02 2019-12-10 清华大学 Serialized leakage inductance integrated high-frequency transformer structure and implementation method
CN113486548A (en) * 2021-06-17 2021-10-08 浙江大学 Design method of high-capacity medium-voltage high-frequency transformer

Non-Patent Citations (5)

* Cited by examiner, † Cited by third party
Title
Design and Optimization of a 200-kW Medium-Frequency Transformer for Medium-Voltage SiC PV Inverters;Zhicheng Guo 等;《IEEE TRANSACTIONS ON POWER ELECTRONICS》;20210217;第36卷(第9期);第10548-10560页 *
Vibration and noise characteristics of high-frequency amorphous transformer under sinusoidal and non-sinusoidal voltage excitation;Pengning Zhang 等;《Electrical Power and Energy Systems》;20200708;第123卷;第106298页 *
基于改进遗传算法的高频变压器优化设计;杨芷婷 等;《工业控制计算机》;20170525;第30卷(第05期);第155-156,159页 *
电力电子变压器中高频变压器损耗分析与设计;梁湘湘 等;《电力机车与城轨车辆》;20200520;第43卷(第03期);第6-12页 *
非晶合金铁心损耗与磁致伸缩特性测量与模拟;迟青光 等;《电工技术学报》;20210705;第36卷(第18期);第3876-3883页 *

Also Published As

Publication number Publication date
CN113962094A (en) 2022-01-21

Similar Documents

Publication Publication Date Title
CN113962094B (en) High-frequency transformer optimization design method comprehensively considering vibration noise
Kuang et al. Magnetic field energy harvesting from current-carrying structures: electromagnetic-circuit coupled model, validation and application
Chen et al. Improved winding loss theoratical calculation of magnetic component with air-gap
Vaisambhayana et al. State of art survey for design of medium frequency high power transformer
Ye et al. A calculation method to adjust the short-circuit impedance of a transformer
Islam et al. Design and implementation of amorphous magnetic material common magnetic bus for the replacement of common dc bus
Yu et al. Comparative analysis of AC copper loss with round copper wire and flat copper wire of high-speed stator-PM flux-switching machine
Yoo et al. Investigation of vibration and acoustic noise emission of powder core inductors
Wang et al. Sensitivity analysis for performance and power density improvements in salient-pole synchronous generators
Saha et al. Multi magnetic material laminated cores: Concept and modelling
Wang et al. Modeling of air gap magnetic characteristics of anode saturable reactors under impulse current excitation
Kim et al. Load noise prediction of high-voltage transformers by equation Applying 3-D EMCN
Wu et al. Investigation and Comparison of Different Calculation Methods for AC Copper Loss of Flat Copper Wire in Axial Flux Permanent Magnet Motor
Chen et al. Vibration Simulation and Experimental Analysis of Medium-Frequency Transformer With the Nanocrystalline Core
Fu et al. Multi-physics Coupling Analysis of Vibration and Noise of Dry-type Distribution Transformer Core
Li et al. Analysis and Optimization of Winding Losses of Axial Flux Permanent Magnet Machine with Concentrated Winding Flat Wires
Lu et al. Simulation Analysis of Electromagnetic Force of Winding of UHV Shunt Reactor
Jiang et al. Multi-objective Optimization Considering PET's Vibration Suppression of Dual Active Bridge Converter Based on BP-NSGA-II
Wei et al. Design considerations of inductor for 500 kVA PV inverter based on Euro efficiency
Chen et al. Multifunction transformer with adjustable magnetic stage based on nanocomposite semihard magnets
Hane et al. Hysteresis modeling of magnetic devices based on reluctance network analysis
Wang et al. A Higher-Order Loss-separation Model for Fast Estimation of Core Loss in High-frequency Transformers
Feng Design of simplifying modeling of stacked iron core transformer
Li et al. Optimize the Winding Structure of Flyback Transformers with Arbitrary Phase-Shifted Current Waveforms
Memon et al. Modeling and analysis of linear permanent magnet generator for wave energy conversion using finite element method

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
GR01 Patent grant
GR01 Patent grant