CN113890327B - Boost circuit integrating APFC (active Power factor correction) and switch capacitor converter and control method - Google Patents

Boost circuit integrating APFC (active Power factor correction) and switch capacitor converter and control method Download PDF

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CN113890327B
CN113890327B CN202111205803.7A CN202111205803A CN113890327B CN 113890327 B CN113890327 B CN 113890327B CN 202111205803 A CN202111205803 A CN 202111205803A CN 113890327 B CN113890327 B CN 113890327B
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pwm signal
input
diode
switch tube
circuit
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CN113890327A (en
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付青
陈一山
苏奕星
杨航
韦仲爽
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Sun Yat Sen University
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Sun Yat Sen University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H02M3/1582—Buck-boost converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention provides a boost circuit integrating an APFC (active power factor converter) and a switch capacitor converter and a control method, which relate to the technical field of power electronics, wherein the APFC and the switch capacitor converter are integrated by sharing two switch tubes, and two PWM (pulse width modulation) signals are utilized to respectively control the conduction states of the two switch tubes, so that the inductive current in the boost circuit changes along with the input voltage, the active power factor correction is realized, the control method is simple and convenient, and the short-circuit phenomenon does not exist; due to the introduction of the switch capacitor converter unit, the inherent capacitor in the switch capacitor converter is used for replacing direct current between the traditional two-stage power factor correction circuit or replacing a buffer large capacitor in the single-stage power factor correction circuit, the inherent capacitor is matched with the conduction state of the switch tube to release and store energy, and the wide-range and high-voltage output voltage is realized while the power factor correction is realized.

Description

Boost circuit integrating APFC (active Power factor correction) and switch capacitor converter and control method
Technical Field
The invention relates to the technical field of power electronics, in particular to a boost circuit integrating an APFC (active Power factor controller) and a switch capacitor converter and a control method.
Background
Along with social development, the application scenes of electrical equipment in human life are gradually increased, and harmonic pollution and power loss caused by the electrical equipment are more serious. In order to reduce the pollution of harmonic waves to a Power grid and increase the efficiency of electrical equipment, an Active Power Factor Correction (APFC) technology has the advantages of improving the Power Factor of a Power electronic device on the grid side, reducing the line loss, saving energy, reducing the harmonic wave pollution of the Power grid, improving the Power supply quality of the Power grid and the like, and is widely applied to many industries.
The traditional power factor correction circuit is generally formed by cascading two stages of circuits, the front stage generally adopts a Boost circuit to realize the function of tracking input voltage by input current through control so as to improve the power factor of the circuit, the rear stage circuit is realized by using basic circuits such as Buck, Buck-Boost and the like according to actual output requirements, but the traditional two-stage power factor correction circuit needs to add a direct-current large capacitor between two stages so as to ensure that the direct-current bus voltage is stable and two stages of switching tubes are in a state of being controlled respectively, and the traditional two-stage power factor correction circuit has the defects of more required elements, complex circuit, low utilization rate of devices and the like. To improve such disadvantages, a Single-stage Power Factor Correction (Single-stage Power Factor Correction) circuit is proposed. At present, most of single-stage power factor correction circuits which are widely applied are generally formed by combining Boost, Buck, Forward, Fly-back and other basic circuits in pairs, and an isolated or non-isolated single-stage power factor correction circuit is realized by sharing one or two switching devices.
On 12.27.2010, a bridge-free single-stage PFC circuit integrating a BOOST and a BUCK is disclosed in Chinese invention patent (publication number: CN102005915A), wherein a power MOSFET (metal-oxide-semiconductor field effect transistor) S1 is used as one of switch tubes of the bridge-free BOOST circuit and is also used as a switch tube of the BUCK circuit; the energy storage capacitor C1 serves as an output capacitor of the bridgeless BOOST circuit to store energy transmitted by the bridgeless BOOST circuit, and is used as an input capacitor of the BUCK circuit to provide energy for a load of the BUCK circuit, the proposal combines the power factor correction stage circuit and the post-stage DC-DC circuit, can simultaneously complete the power factor correction and the output voltage regulation functions by using one controller, has fewer devices, improves the efficiency, reduces the cost, but also has the disadvantages of large voltage stress of the switching device, limited boosting effect, and the need of large capacitance as a buffer capacitance when the input power and the output power are unbalanced, and in addition, in each working mode mentioned in the scheme, when the switching tube is controlled to be switched on and off based on the change of the positive and negative polarities of the alternating-current input power supply so as to regulate the output voltage, the switching tube has a dead zone and cannot realize the voltage regulation in a wide range.
Disclosure of Invention
In order to solve the problems that the complexity of the current single-stage power factor correction circuit is high and the wide-range voltage regulation cannot be realized, the invention provides a boost circuit integrating an APFC and a switch capacitor converter and a control method.
In order to achieve the technical effects, the technical scheme of the invention is as follows:
a boost circuit integrating an APFC with a switched capacitor converter, the circuit comprising: power input conversion unit and input inductor LinA first switch tube Q1A second switch tube Q2The device comprises a switch capacitor converter unit, an output unit, a first PWM signal generator, a second PWM signal generator and a mode distribution unit;
one end of the power input conversion unit is connected with an input inductor LinInput terminal of (2), input inductance LinThe output end of the switch capacitor converter unit is respectively connected with the first end of a first switch tube Q1 and the first input end of the switch capacitor converter unit, the second end of a first switch tube Q1 is respectively connected with the first end of a second switch tube Q2 and the second input end of the switch capacitor converter unit, the second end of a second switch tube Q2 is connected with the other end of the power input conversion unit, the first output end of the switch capacitor converter unit is connected with one end of the output unit, and the other end of the output unit and the second output end of the switch capacitor converter unit are both connected with the second end of a second switch tube Q2;
the mode distribution unit sends a first switching tube Q to the first PWM signal generator and the second PWM signal generator according to the active power factor correction and the boosting requirement 1A second switch tube Q2The first PWM signal generator generates the first PWM signal P according to the mode assignment indication1The output end of the second PWM signal generator is connected with the third end of the first switching tube Q1, and the second PWM signal generator generates a second PWM signal S according to the mode distribution indication2The output end of the second switch tube Q2 is connected with the third end of the second switch tube Q2; first PWM Signal P1Controlling the conducting state of the first switch tube Q1 and the second PWM signal S2The conducting state of the second switch tube Q2 is controlled, so that the input inductor LinOf inductive current-following power input switching unitThe input voltage varies, active power factor correction is achieved, and the output voltage is boosted based on the switched capacitor converter unit.
In the present technical solution, the power input conversion unit provides the required input voltage for the whole boost circuit, and the APFC (active power factor correction) and the switched capacitor converter unit share the first switching tube Q1A second switch tube Q2The integration is carried out, the inherent capacitor in the switch capacitor converter replaces the direct current between the traditional two-stage power factor correction circuit or replaces the buffer large capacitor in the single-stage power factor correction circuit, the complexity of the circuit is reduced, the utilization rate of the device is structurally increased, and two PWM signals are introduced to respectively control the first switch tube Q 1A second switch tube Q2So that the input inductance L is ininThe inductive current of the switch capacitor converter is changed along with the input voltage of the power input conversion unit to realize active power factor correction, and high voltage is provided by utilizing the high-boost function of the switch capacitor converter to realize high-voltage output.
Preferably, the power input conversion unit includes: an AC input power supply AC and a rectifier bridge including a diode D1Diode D2Diode D3Diode D4Diode D1Respectively connected with one end of an AC input power supply AC and a diode D4Cathode of (2), diode D1Respectively with a diode D2Cathode and input inductor L ofinIs connected to the input terminal of a diode D2Anode of the diode is respectively connected with the other end of the AC input power supply AC and the diode D3Cathode of (2), diode D3The anodes of the first switching tube Q2 are respectively connected to the second end of the second switching tube Q2, and the rectifier bridge converts the AC sine wave of the AC input power source into an arch wave.
Preferably, the switched capacitor converter unit comprises a diode D5Diode D6Diode D7Diode D8First flying capacitor C1A second flying capacitor C2And a third flying capacitor C3(ii) a Diode D of a switched capacitor converter unit5As an anode of The first end of the first switch tube Q1 is connected with the first input end of the switch capacitance converter unit; diode D5Respectively connected with a diode D6Anode and first flying capacitor C1One terminal of (C), a first flying capacitor C1The other end of the first switch tube Q1, the first end of the first switch tube Q1 and the third flying capacitor C are respectively connected as the second input end of the switch capacitor converter unit3One terminal of (2), diode D6Respectively connected with a second flying capacitor C2And a diode D7Anode of (2), diode D7Respectively connected with a third flying capacitor C3Another terminal of and diode D8Anode of (2), diode D8The cathode of the switch capacitor converter unit is used as a first output end of the switch capacitor converter unit and is connected with one end of the output unit, and the second flying capacitor C2The other end of the first switch tube Q2 is connected with the other end of the output unit and the second end of the second switch tube Q2 respectively as the second output end of the switch capacitance converter unit;
the output unit comprises a capacitor C4And an output resistor RoutSaid capacitor C4And an output resistor RoutAre connected in parallel.
Preferably, when the first switch tube Q1And a second switching tube Q2When the AC input sine waves are all switched on, the AC sine waves input by the AC input power supply are converted into the arched waves to charge the input inductor, and the inductor current I inRising, diode D5Diode D6Diode D8Off, diode D7Open, second flying capacitor C2Through diode D7To the third flying capacitor C3Discharging;
when the first switch tube Q1On, second switch tube Q2When the circuit is turned off, the AC input power supply, the input inductor and the first flying capacitor C are connected1Connected in series and then passing through diode D6To the second flying capacitor C2Charging, simultaneously AC input power AC, input inductor and third flying capacitor C3Series backward capacitance C4Charging while passing through diode D8Is an output resistor RoutProviding energy with input inductor in charged stateInductance current IinGradually rising;
when the first switch tube Q1Turn-off, second switch tube Q2When the circuit is switched on, the alternating current input power supply AC is connected with the input inductor in series and then the first flying capacitor C is arranged1Charging, second flying capacitor C2Through diode D7To the third flying capacitor C3Discharge and pass through diode D8Is a capacitor C4Charging, the energy stored in the input inductor is released and stored in the capacitor C1In the inductor current IinThe current drops;
when the first switch tube Q1And a first switch tube Q2When the AC input power is turned off, the AC is rectified by the rectifier bridge and then connected in series with the input inductor through the diode D5Diode D6Is a second flying capacitor C2Charging, diode D 7Diode D8Off, capacitance C4Is an output resistor RoutProviding energy.
Preferably, the first PWM signal generator includes a first operational amplifier circuit, a multiplier, a second operational amplifier circuit, and a third operational amplifier circuit, and a reference voltage V is input to a positive terminal of the first operational amplifier circuitrefThe negative terminal of the first operational amplifier circuit receives the output voltage V of the output unitc4The first operational amplifier circuit is provided with an input resistor Z1And a resistance Z2The negative terminals of the first operational amplifier circuit are respectively connected with the input resistors Z1And a resistor Z2One terminal of (1), input resistance Z1Is connected with the output voltage V of the output unitc4Resistance Z2The other end of the first operational amplifier circuit is connected with the output end of the first operational amplifier circuit;
the output end of the first operational amplification circuit is connected with the first input end of the multiplier, the unit arch wave | sin ω x | is input to the second input end of the multiplier, the output end of the multiplier is connected with the positive end of the second operational amplification circuit, and the inductive current I is input to the negative end of the second operational amplification circuitinThe output end of the second operational amplifier circuit is connected with the positive end of the third operational amplifier circuit, the negative end of the third operational amplifier circuit inputs sawtooth waves, and the third operational amplifier circuitThe output end of the large circuit outputs a first PWM signal P 1First PWM Signal P1The generation of the voltage-stabilizing circuit does not need to consider the dead zone of a switching tube, so that the wide-range voltage output is realized while the power factor correction is realized.
Preferably, the second PWM signal generator includes a fourth amplifying circuit, an and circuit, a not circuit, or a gate circuit; the positive end input of the fourth amplifying circuit is constant direct-current voltage VDCThe negative end of the fourth amplifying circuit inputs sawtooth waves, and the output end of the fourth amplifying circuit outputs a PWM signal P with constant duty ratio11Constant duty cycle PWM signal P11And the first PWM signal P1Are all input to an AND gate circuit, while a first PWM signal P1The output of the NOT gate circuit and the output of the AND gate circuit are used as the input of an OR gate circuit, and the OR gate circuit outputs a second PWM signal S2Second PWM signal P2The generation of the voltage regulator does not need to consider the dead zone of the switching tube, thereby being convenient for realizing wide-range voltage output while realizing power factor correction.
Preferably, the first PWM signal P is adjusted given an average current value of the boost circuit1At a high level, the second PWM signal S2At high level, the first switch tube Q1And a second switching tube Q2Are all in the on mode, and input inductance LinOf the inductor current I inRise as input inductance LinOf the inductor current IinWhen the average current value is larger than the first PWM signal P, the first PWM signal P is adjusted1At a low level, the second PWM signal S2At high level, the first switch tube Q1On/off state, second switch tube Q2In the on mode, the input inductance LinOf the inductor current IinDecrease when the input inductance L is decreasedinOf the inductor current IinWhen the average current value is less than the first value, the first PWM signal P is adjusted1At a high level, the second PWM signal S2At high level, the first switch tube Q1And a second switching tube Q2Are all in the on mode, and input inductance LinOf the inductor current IinRise so that the input inductance LinThe inductance current follows the average current valueChanging to realize active power factor correction;
adjusting the first PWM signal P1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure GDA0003680648450000051
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11Represents a PWM signal with a constant duty cycle,
Figure GDA0003680648450000052
indicating that the first PWM signal is negated.
Preferably, the first PWM signal P is adjusted1At a high level, the second PWM signal S2At a low level, the first switch tube Q1On, second switch tube Q2Off mode, power input conversion unit, first flying capacitor C1All release energy as second flying capacitor C 2Charging, and increasing the output voltage;
adjusting the first PWM signal P1And a second PWM signal S2The logic function expression of the high and low level states of (1) is as follows:
P1＝P1
Figure GDA0003680648450000053
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11A PWM signal representing a constant duty cycle,
Figure GDA0003680648450000054
indicating that the first PWM signal is negated.
The first PWM signal generator and the second PWM signal generator are used for generating pulse signals corresponding to the mode allocation logic for controllingThe main circuit and the mode distribution logic are mainly used for ensuring the function of active power factor correction and realizing the boosting effect under the premise. In order to realize active power factor correction, the first switch tube Q is needed to be firstly1And a second switching tube Q2When the inductor current exceeds a given average current value, the first switch tube Q1Turn-off, second switch tube Q2When the inductor is switched on and works in the mode, the inductor current is reduced, and when the inductor current is lower than a given average current value, the inductor current is switched to the first switching tube Q again1And a second switching tube Q2Simultaneously, the working mode is switched on, so that the inductor current signal is repeatedly finished to follow a given average current value to finish power factor correction, namely, the inductor current signal firstly enters the first switching tube Q in a period 1Second switch tube Q2All conducted modes enter a first switch tube Q1Turn off, the second switch tube Q2The open mode.
After ensuring the power factor correction, in order to realize the boost function, a part of the first switch tube Q is connected in a cycle1And a second switch tube Q2The time for which the represented modes are all switched on is allocated to the first switching tube Q1On and off of the second switch tube Q2The represented mode is turned off to complete the boost function.
In general, in one cycle, the first switch tube Q is entered first1And a second switching tube Q2All are conducted to the represented mode and then enter the first switch tube Q1On, second switch tube Q2The represented mode is turned off, and finally the mode enters a first switching tube Q1Turn-off, second switch tube Q2The represented mode is switched on, and then the cycle is repeated continuously to complete the functions of main circuit active power factor correction and boosting.
The invention also provides a control method of the boost circuit of the integrated APFC and switched capacitor converter, which is used for controlling the boost circuit of the integrated APFC and switched capacitor converter and comprises the following steps:
mode allocation unitReceiving the active power factor correction and boosting requirements issued by the user, and sending a first switching tube Q to a first PWM signal generator and a second PWM signal generator 1A second switch tube Q2A modality assignment indication of (a);
generating a first PWM signal P by a first PWM signal generator according to the mode allocation indication1Generating a second PWM signal S by a second PWM signal generator2；
The first PWM signal P1The second PWM signal S is input to the third terminal of the first switch tube Q12A third terminal of the first switching tube Q2;
adjusting the first PWM signal P when the input voltage of the power input conversion unit rises1At a high level, the second PWM signal S2At high level, the first switch tube Q is turned on1And a second switching tube Q2Are all in the opening mode;
adjusting the first PWM signal P when the input voltage of the power input converting unit is decreased1At a low level, the second PWM signal S2At high level, the first switch tube Q1On/off state, second switch tube Q2In the open mode;
adjusting the first PWM signal P when the output voltage needs to be raised1At a high level, the second PWM signal S2At low level, the first switch tube Q is turned on1On, the second switch tube Q2In the off mode.
Here, the modality assignment indication includes: first switch tube Q1And a second switching tube Q2The modes are all switched on; first switch tube Q1On/off state, second switch tube Q2In the open mode; first switch tube Q 1On the second switch tube Q2In the off mode.
Preferably, the first PWM signal P is regulated1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure GDA0003680648450000071
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11Represents a PWM signal with a constant duty cycle,
Figure GDA0003680648450000072
indicating that the first PWM signal is negated.
Compared with the prior art, the technical scheme of the invention has the beneficial effects that:
the invention provides a boost circuit integrating an APFC (active power factor converter) and a switch capacitor converter and a control method, wherein the APFC and the switch capacitor converter are integrated by sharing two switch tubes, and the conduction states of the two switch tubes are respectively controlled by using two PWM (pulse width modulation) signals, so that the inductive current in the boost circuit is changed along with the input voltage, the active power factor correction is realized, the control method is simple and convenient, and the short circuit phenomenon does not exist; and because the switch capacitor converter unit is introduced, the inherent capacitor in the switch capacitor converter is utilized to replace direct current between the traditional two-stage power factor correction circuit or replace a buffer large capacitor in a single-stage power factor correction circuit, the inherent capacitor is matched with the conduction state of the switch tube to release and store energy, and the wide-range and high-voltage output voltage is realized while the power factor correction is realized.
Drawings
Fig. 1 is a diagram showing a configuration of a boost circuit integrating an APFC and a switched capacitor converter according to embodiment 1 of the present invention;
fig. 2 is a circuit diagram of the boost circuit integrating the APFC and the switched capacitor converter according to embodiment 1 of the present invention in a first operating mode;
fig. 3 is a circuit diagram of the boost circuit integrating the APFC and the switched capacitor converter according to embodiment 1 of the present invention in a second operating mode;
fig. 4 is a circuit diagram of the boost circuit integrating the APFC and the switched capacitor converter according to the embodiment 1 of the present invention in a third operating mode;
fig. 5 is a circuit diagram illustrating an operation of the boost circuit integrating the APFC and the switched capacitor converter in the fourth operation mode according to embodiment 1 of the present invention;
fig. 6 is a circuit diagram showing an operation of the first PWM signal generator proposed in embodiment 1 of the present invention;
fig. 7 is a circuit diagram showing an operation of the second PWM signal generator proposed in embodiment 1 of the present invention;
fig. 8 is a simulated waveform diagram of the boost circuit integrating the APFC and the switched capacitor converter in a plurality of power frequency cycles when the input voltage is 220V, the output voltage is 700V, and the load is 500 Ω according to embodiment 1 of the present invention;
Fig. 9 is a simulated waveform diagram of the boost circuit integrating the APFC and the switched capacitor converter in a plurality of power frequency cycles when the input voltage is 220V, the output voltage is 700V, and the load is 250 Ω according to embodiment 1 of the present invention;
fig. 10 is a simulated waveform diagram of the boost circuit integrating the APFC and the switched capacitor converter in a plurality of power frequency cycles when the input voltage is 220V, the output voltage is 1000V, and the load is 500 Ω according to embodiment 1 of the present invention;
fig. 11 is a simulated waveform diagram of the boost circuit integrating the APFC and the switched capacitor converter in a plurality of power frequency cycles when the input voltage is 220V, the output voltage is 1000V, and the load is 250 Ω according to embodiment 1 of the present invention;
fig. 12 is a simulated waveform diagram of the boost circuit integrating the APFC and the switched capacitor converter in a plurality of power frequency cycles when the input voltage is 220V, the output voltage is 1500V, and the load is 500 Ω according to embodiment 1 of the present invention;
fig. 13 is a simulated waveform diagram of the boost circuit integrating the APFC and the switched capacitor converter in the embodiment 1 of the present invention, when the input voltage is 220V, the output voltage is 1500V, and the load is 250 Ω, in a plurality of power frequency cycles.
Detailed Description
The drawings are for illustrative purposes only and are not to be construed as limiting the patent;
for better illustration of the present embodiment, some parts of the drawings may be omitted, enlarged or reduced, and do not represent actual sizes;
it will be understood by those skilled in the art that certain descriptions of well-known structures in the drawings may be omitted.
The positional relationships depicted in the drawings are for illustrative purposes only and should not be construed as limiting the present patent;
the technical solution of the present invention is further described with reference to the drawings and the embodiments.
Example 1
A boost circuit integrating an APFC with a switched capacitor converter as shown in fig. 1, the circuit comprising, with reference to fig. 1: power input conversion unit 1 and input inductor LinA first switch tube Q1A second switch tube Q2The device comprises a switched capacitor converter unit 2, an output unit 3, a first PWM signal generator, a second PWM signal generator and a mode distribution unit;
one end of the power input conversion unit 1 is connected with an input inductor LinInput terminal of, input inductance LinThe output end of the first switch tube Q1 is connected with a first end of a first switch tube Q1 and a first input end of a switch capacitor converter unit 2, a second end of the first switch tube Q1 is connected with a first end of a second switch tube Q2 and a second input end of the switch capacitor converter unit 2, a second end of the second switch tube Q2 is connected with the other end of a power input conversion unit 1, a first output end of the switch capacitor converter unit 2 is connected with one end of an output unit 3, and the other end of the output unit 3 and a second output end of the switch capacitor converter unit 2 are both connected with a second end of a second switch tube Q2;
The mode distribution unit sends a first switching tube Q to the first PWM signal generator and the second PWM signal generator according to the active power factor correction and the boosting requirement1A second switch tube Q2According to the mode assignment indication, the first PWM signal generator generates the first PWM signal P1The output end of the second PWM signal generator is connected with the third end of the first switching tube Q1, and the second PWM signal generator generates a second PWM signal S according to the mode distribution indication2The output end of the first switch tube is connected with a second switch tube Q2, a third end; the input inductor is used for controlling the period of stored energy, and the first PWM signal P1Controlling the conducting state of the first switch tube Q1 and the second PWM signal S2The conducting state of the second switch tube Q2 is controlled, so that the input inductor LinThe inductive current of (2) changes along with the input voltage of the power input conversion unit (1), so that active power factor correction is realized, and the output voltage is increased based on the switched capacitor converter unit (2).
In the present embodiment, the power input conversion unit 1 includes: an AC input source AC for supplying electric energy and a rectifier bridge comprising a diode D1Diode D2Diode D3Diode D4Diode D1Respectively connected with one end of an AC input power supply AC and a diode D 4Cathode of (2), diode D1Respectively with a diode D2Cathode and input inductance LinIs connected to the input terminal of a diode D2Anode of the diode is respectively connected with the other end of the AC input power supply AC and the diode D3Cathode of (2), diode D3The anodes of the first switching tube Q2 are respectively connected to the second end of the second switching tube Q2, and the rectifier bridge converts the AC sine wave of the AC input power source into an arch wave.
In the present embodiment, the switched-capacitor converter unit 2 is a second-order switched-capacitor converter, which comprises a diode D, see fig. 15Diode D6Diode D7Diode D8First flying capacitor C1A second flying capacitor C2And a third flying capacitor C3The diode is used for controlling the energy flow direction; diode D of the switched capacitor converter unit 25Is used as a first input terminal of the switched capacitor converter unit 2, and is connected with a first end of a first switching tube Q1; diode D5Respectively connected with a diode D6Anode and first flying capacitor C1One terminal of (C), a first flying capacitor C1The other end of the first switch tube Q1, the first end of the first switch tube Q1 and the third fly-power are respectively connected as the second input end of the switch capacitor converter unit 2 Container C3One terminal of (2), diode D6Respectively connected with a second flying capacitor C2And a diode D7Anode of (2), diode D7Respectively connected with a third flying capacitor C3And a diode D8Anode of (2), diode D8As a first output terminal of the switched-capacitor converter unit 2, to one end of an output unit 3, and a second flying capacitor C2The other end of the first switch tube Q2 is connected to the other end of the output unit 3 and the second end of the second switch tube Q2 respectively as the second output end of the switched capacitor converter unit 2; here, as shown in fig. 1, in an actual implementation, the switched capacitor converter unit 2 can be expanded from one switched capacitor converter to n-th order, and increasing the number of switched capacitor stages can effectively increase the boosting capability.
Referring to fig. 1, the output unit 3 includes a capacitor C4And an output resistor RoutCapacitor C4And an output resistor RoutAre connected in parallel.
In this embodiment, the first switch tube Q1And a second switching tube Q2The on-state of the boost circuit can be divided into four modes of operation, wherein,
the first modality: referring to fig. 2, when the first switch tube Q is turned on1And a second switching tube Q2When both are on, the solid line represents current flow, and the dashed line represents no current flow. Under the working mode, an alternating current sine wave input by an alternating current input power supply AC is converted into an arch wave and then becomes an input inductor L inCharging, inductor current IinRising, diode D5Diode D6Diode D8Off, diode D7On, second flying capacitor C2Through diode D7To the third flying capacitor C3Discharging;
the second mode is as follows: referring to fig. 3, when the first switch tube Q is turned on1On, second switch tube Q2When turned off, the solid line represents current flow and the dashed line represents no current flow. Under the working mode, AC input power supply and input inductance LinA first flying capacitor C1Pass through diode after being connected in seriesD6To the second flying capacitor C2Charging, simultaneously AC input power AC and input inductance LinA third flying capacitor C3Series backward capacitance C4Charging while passing through diode D8Is an output resistor RoutEnergy supply, input inductance LinIn the charging state, the inductor current IinGradually rising;
the third mode is as follows: referring to fig. 4, when the first switch tube Q is turned on1Turn-off, second switch tube Q2When on, the solid line represents current flow and the dashed line represents no current flow. Under the working mode, AC input power supply and input inductance LinSeries backward first flying capacitor C1Charging, second flying capacitor C2Through diode D7To the third flying capacitor C3Discharge and pass through diode D8Is a capacitor C4Charging, input inductance L inThe stored energy is released and stored in the capacitor C1In the inductor current IinThe current is reduced;
a fourth modality: referring to FIG. 5, when the first switch tube Q is turned on1And a first switch tube Q2All off, the solid line represents current flow and the dashed line represents no current flow. Under the working mode, an alternating current input power supply AC is rectified by a rectifier bridge and then is connected with an input inductor LinIn series through a diode D5Diode D6Is a second flying capacitor C2Charging, diode D7Diode D8Off, capacitance C4Is an output resistor RoutProviding energy.
Referring to fig. 6, in the present embodiment, the first PWM signal generator includes a first operational amplifier circuit, a multiplier, a second operational amplifier circuit, and a third operational amplifier circuit, and a positive input of the first operational amplifier circuit is a reference voltage VrefThe negative terminal of the first operational amplifier circuit receives the output voltage V from the output unit 3c4The first operational amplifier circuit has an input resistor Z1And a resistance Z2The negative terminals of the first operational amplifier circuit are respectively connected with the input resistors Z1And a resistor Z2One terminal of (1), input resistance Z1Is connected with the output voltage V of the output unitc4Resistance Z2The other end of the first operational amplifier circuit is connected with the output end of the first operational amplifier circuit;
The output end of the first operational amplification circuit is connected with the first input end of the multiplier, the unit arch wave | sin ω x | is input to the second input end of the multiplier, the output end of the multiplier is connected with the positive end of the second operational amplification circuit, and the inductive current I is input to the negative end of the second operational amplification circuitinThe output end of the second operational amplifier circuit is connected with the positive end of the third operational amplifier circuit, the negative end of the third operational amplifier circuit inputs sawtooth waves, and the output end of the third operational amplifier circuit outputs a first PWM signal P1First PWM signal P1The generation of the voltage regulator does not need to consider the dead zone of the switching tube, thereby being convenient for realizing wide-range voltage output while realizing power factor correction.
Referring to fig. 7, the second PWM signal generator includes a fourth amplifying circuit, an and circuit, a not circuit, or a gate circuit; the positive end input of the fourth amplifying circuit is constant direct current voltage VDCThe negative end of the fourth amplifying circuit inputs sawtooth waves, and the output end of the fourth amplifying circuit outputs a PWM signal P with constant duty ratio11Constant duty cycle PWM signal P11And the first PWM signal P1Are all input to an AND gate circuit, while a first PWM signal P1The output of the NOT gate circuit and the output of the AND gate circuit are used as the input of an OR gate circuit, and the OR gate circuit outputs a second PWM signal S 2Second PWM signal P2The generation of the voltage regulator does not need to consider the dead zone of the switching tube, thereby being convenient for realizing wide-range voltage output while realizing power factor correction.
With reference to fig. 6 and 7, the first PWM signal P1And a second PWM signal S2The two switching tubes are controlled by adopting a control mode of combining average current control and a gate circuit to control the booster circuit in the invention so as to realize power factor correction and control of output voltage, and the whole control effect is that the input current waveform follows the input voltage waveform, namely the inductive current waveform follows the rectified arch wave waveform so as to improve the power factor and correct the active power factorOn the basis, the duty ratio of the four working modes in the whole period is controlled to regulate and control the output voltage.
Because the first switch tube Q of the booster circuit1A second switch tube Q2All open or first switch tube Q1On, second switch tube Q2At turn-off, the inductor current IinAre all in a rising state; first switch tube Q of booster circuit1A second switch tube Q2Are all turned off, or the first switching tube Q1Turn-off, second switch tube Q2At turn-on, the inductor current IinAll are in a falling state, the first PWM signal P1When the voltage is high level, the booster circuit should work in the first switch tube Q 1Second switch tube Q2All open or first switch tube Q1On, second switch tube Q2Turning off the two operating modes, the first PWM signal P1When the voltage is at low level, the booster circuit should work in the switch tube Q1，Q2Are all turned off, or the first switching tube Q1Turn-off, second switch tube Q2The two operating states are switched on. Because the switched capacitor converter only needs to work on the first switching tube Q when working1Turn-off, second switch tube Q2Turn on and first switch tube Q1On, second switch tube Q2Turning off the two operating modes, for simplicity of control, may be performed on the first PWM signal P1When the voltage is low, only the control circuit works on the first switch tube Q1Turn-off, second switch tube Q2This mode of operation is enabled.
For the implementation of active power factor correction and boost results:
adjusting the first PWM signal P for a given average current value of the boost circuit1At a high level, the second PWM signal S2At high level, the first switch tube Q1And a second switching tube Q2Are all in the on mode, and input inductance LinOf the inductor current IinRise as input inductance LinOf the inductor current IinWhen the average current value is larger than the first PWM signal P, the first PWM signal P is adjusted1At a low level, the second PWM signal S2At high level, the first switch tube Q1On/off state, second switch tube Q 2In the on mode, the input inductance LinOf the inductor current IinDecrease when the input inductance LinOf the inductor current IinWhen the average current value is less than the first value, the first PWM signal P is adjusted1At a high level, the second PWM signal S2At high level, the first switch tube Q1And a second switching tube Q2Are all in the on mode, and input inductance LinOf the inductor current IinRise so that the input inductance LinThe inductance current of the power amplifier changes along with the average current value, so that active power factor correction is realized;
adjusting the first PWM signal P1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure GDA0003680648450000121
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11Represents a PWM signal with a constant duty cycle,
Figure GDA0003680648450000122
indicating that the first PWM signal is negated.
First PWM Signal P1At a low level, the second PWM signal S2When the voltage is high, the first switch tube Q1Turn-off, second switch tube Q2On, first flying capacitor C1Storage of electric energy, second flying capacitor C2And a third flying capacitor C3The voltage of (d) remains the same;
adjusting the first PWM signal P1At a high level, the second PWM signal S2At a low level, the first switch tube Q1On, second switch tube Q2Off mode, power input conversion unit, first flying capacitor C1All release energy as second flying capacitor C 2And charging, and increasing the output voltage, thereby completing the voltage boosting function of the switched capacitor converter.
Adjusting the first PWM signal P1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure GDA0003680648450000123
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11Represents a PWM signal with a constant duty cycle,
Figure GDA0003680648450000131
indicating that the first PWM signal is negated.
With reference to fig. 8 to 13, the boosting validity of the circuit provided in embodiment 1 of the present invention is further verified, and with reference to specific simulations, the parameters of the components are set according to specific situations, such as the input voltage value of the AC input power source AC, and the inductive current IinValue of (C), first flying capacitor C1Value of (C), second flying capacitor C2Third flying capacitor C3The fourth flying capacitor C4And the value of the output resistance.
Wherein the abscissa in each figure is a period, the ordinate represents the voltage, and the input voltage and the first flying capacitor C are sequentially arranged from top to bottom in each figure1Voltage V ofc1Output voltage, i.e. capacitor C4Voltage V ofc4。
Fig. 8 and 9 show simulations of loads 500 Ω and 250 Ω when the input voltage is 220V and the output voltage is 700V, where the output voltages are the same and the loads are different; in fig. 8, the input voltage is 220V ac, the reference voltage is set to 700V, the average output voltage is 699V, the load is 500 Ω, the average input current is 5.51A, the power factor is 0.99, and the power is 980W. In fig. 9, the input voltage is 220V ac, the reference voltage is set to 700V, the average output voltage is 699V, the load is 250 Ω, the average input current is 11.40A, the power factor is 0.99, and the power is 1960W
Fig. 10 and 11 show simulations of loads 500 Ω and 250 Ω when the input voltage is 220V and the output voltage is 1000V, where the output voltages are the same and the loads are different; in fig. 10, the input voltage is 220V alternating current, the set reference voltage is 1000V, the average value of the output voltage is 997V, the load is 500 Ω, the average input current is 11.50A, the power factor is 0.99, and the power is 2000W; in fig. 11, the input voltage is 220V ac, the reference voltage is set to 1000V, the average value of the output voltage is 997V, the load is 500 Ω, the average input current is 11.50A, the power factor is 0.99, and the power is 2000W.
Fig. 12 and 13 show the simulation under the conditions of input voltage of 220V, output voltage of 1500V, load of 500 Ω and load of 250 Ω, in which the output voltage is the same and the load is different; in fig. 12, the input voltage is 220V ac, the reference voltage is set to 1500V, the average output voltage is 1490V, the load is 500 Ω, the average input current is 25.20A, the power factor is 0.984, and the power is 4500W; in fig. 13, the input voltage is 220V ac, the reference voltage is set to 1500V, the average value of the output voltage is 1483V, the load is 250 Ω, the average input current is 48.00A, the power factor is 0.99, and the power is 9000W.
Fig. 8, fig. 10 and fig. 12 show simulation comparisons of different output voltage voltages when the input voltage is 220V and the load is 500 Ω;
fig. 9, 11 and 13 show simulation comparisons of different output voltage voltages when the input voltage is 220V and the load is 250 Ω;
with reference to fig. 8 to 13, on the premise that the input voltage is increased to some extent, the intermediate level Vc1 is reached, and the input voltage is connected in series with the Vc1 voltage to form the second flying capacitor C2Voltage Vc2 and second flying capacitor C3The voltage Vc3 rises and finally the input voltage is connected in series with the capacitor C3 to supply the C4, so that the voltage across C4, i.e., the output voltage, is at its highest.
Example 2
Embodiment 2 of the present invention provides a method for controlling a boost circuit integrated with an APFC and a switched capacitor converter, where the method is used to control the boost circuit integrated with the APFC and the switched capacitor converter described in embodiment 1, and the method includes:
the mode distribution unit receives the active power sent by the userSending a first switching tube Q to a first PWM signal generator and a second PWM signal generator according to the requirements of frequency factor correction and voltage boosting1A second switch tube Q2A modality assignment indication of (a);
generating a first PWM signal P by a first PWM signal generator according to the mode allocation indication1Generating a second PWM signal S by a second PWM signal generator 2；
A first PWM signal P1The second PWM signal S is input to the third terminal of the first switch tube Q12A third terminal of the first switching tube Q2;
adjusting the first PWM signal P when the input voltage of the power input conversion unit rises1At a high level, the second PWM signal S2At high level, the first switch tube Q is turned on1And a second switching tube Q2Are all in the opening mode;
adjusting the first PWM signal P when the input voltage of the power input converting unit is decreased1At a low level, the second PWM signal S2At high level, the first switch tube Q1On/off state, second switch tube Q2In the open mode;
adjusting the first PWM signal P when the output voltage needs to be raised1At a high level, the second PWM signal S2At a low level, the first switch tube Q is turned on1On the second switch tube Q2In the off mode.
In the present embodiment, the first PWM signal P is adjusted1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure GDA0003680648450000141
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11Represents a PWM signal with a constant duty cycle,
Figure GDA0003680648450000142
indicating that the first PWM signal is negated, the first PWM signal generator is used to generate the first PWM signal P1Generating a second PWM signal S by a second PWM signal generator 2The process comprises the following steps:
setting a parameter value of a boost circuit, comprising: reference voltage values, element parameter values; the element parameters represent the constituent elements of the boost circuit, such as capacitance and resistance, diodes, switching tubes, and the like.
Detecting and sampling the output voltage and the inductive current of the booster circuit, and acquiring the sampled output voltage and inductive current;
inputting a reference voltage into the positive end of a first operational amplification circuit, inputting an output voltage into the negative end of the first operational amplification circuit, operating through a first operational amplifier, and obtaining an error a between an actual output voltage and the reference voltage through PI compensation;
inputting the error a and the unit arch wave into a multiplier to obtain an arch wave containing error information of output voltage and reference voltage as a current tracking signal, inputting the current tracking signal into the positive end of a second operational amplification circuit, and inputting the inductive current into the negative end of the second operational amplification circuit to obtain an error b of the inductive current and the current tracking signal; when the sampled input current Iin signal is smaller than the current tracking signal, the first PWM signal P1The output is high level, which represents that the first switch tube Q is simultaneously switched on1And a second switch tube Q2Or only turn on the first switch tube Q1When the voltage is low, the first switch tube Q is switched off 1Turning on the second switch tube Q2。
Inputting the error b into the positive terminal of the third operational amplifier circuit, setting the amplitude and frequency of the first sawtooth wave, in this embodiment, setting the amplitude to be 1V and the frequency to be 100Khz, inputting the first sawtooth wave into the negative terminal of the third operational amplifier circuit, and obtaining the first PWM signal P with the same frequency as the first sawtooth wave and 100Khz1；
Introducing a constant DC voltage VDCInputting the second sawtooth wave into the positive terminal of a fourth amplifying circuit, setting the amplitude and frequency of the second sawtooth wave, inputting the second sawtooth wave into the negative terminal of the fourth amplifying circuit, and performing fourth amplificationPWM signal P with constant duty ratio output by large circuit11；
Constant duty cycle PWM signal P11And the first PWM signal P1Input to an AND gate circuit while the first PWM signal P is1The output of the NOT gate circuit and the output of the AND gate circuit are used as the input of an OR gate circuit, and the OR gate circuit outputs a second PWM signal S2。
The positional relationships depicted in the drawings are for illustrative purposes only and are not to be construed as limiting the present patent;
it should be understood that the above-described embodiments of the present invention are merely examples for clearly illustrating the present invention and are not intended to limit the embodiments of the present invention. Other variations and modifications will be apparent to persons skilled in the art in light of the above description. And are neither required nor exhaustive of all embodiments. Any modification, equivalent replacement, and improvement made within the spirit and principle of the present invention should be included in the protection scope of the claims of the present invention.

Claims (8)

1. A boost circuit integrating an APFC with a switched capacitor converter, the circuit comprising: power input conversion unit and input inductor LinA first switch tube Q1A second switch tube Q2The device comprises a switch capacitor converter unit, an output unit, a first PWM signal generator, a second PWM signal generator and a mode distribution unit; one end of the power input conversion unit is connected with an input inductor LinInput terminal of, input inductance LinThe output end of the first switch tube Q1 and the first input end of the switch capacitor converter unit are respectively connected, the second end of the first switch tube Q1 is respectively connected with the first end of the second switch tube Q2 and the second input end of the switch capacitor converter unit, the second end of the second switch tube Q2 is connected with the other end of the power input conversion unit, the first output end of the switch capacitor converter unit is connected with one end of the output unit, the other end of the output unit and the second output end of the switch capacitor converter unit are both connected with the second end of the second switch tube Q2Connecting;
the mode distribution unit sends a first switching tube Q to the first PWM signal generator and the second PWM signal generator according to the active power factor correction and the boosting requirement1A second switch tube Q 2According to the mode assignment indication, the first PWM signal generator generates the first PWM signal P1The output end of the second PWM signal generator is connected with the third end of the first switching tube Q1, and the second PWM signal generator generates a second PWM signal S according to the mode distribution indication2The output end of the second switch tube Q2 is connected with the third end of the second switch tube Q2; first PWM signal P1Controlling the conducting state of the first switch tube Q1 and the second PWM signal S2The conducting state of the second switch tube Q2 is controlled, so that the input inductor LinThe inductive current of the power supply is changed along with the input voltage of the power supply input conversion unit, so that active power factor correction is realized, and the output voltage is increased based on the switched capacitor converter unit;
the first PWM signal generator comprises a first operational amplifier circuit, a multiplier, a second operational amplifier circuit and a third operational amplifier circuit, wherein the positive end input of the first operational amplifier circuit is a reference voltage VrefThe negative terminal of the first operational amplifier circuit receives the output voltage V of the output unitc4The first operational amplifier circuit has an input resistor Z1And a resistance Z2The negative terminals of the first operational amplifier circuit are respectively connected with the input resistors Z1And a resistor Z2One terminal of (1), input resistance Z1Is connected with the output voltage V of the output unit c4Resistance Z2The other end of the first operational amplifier circuit is connected with the output end of the first operational amplifier circuit;
the output end of the first operational amplification circuit is connected with the first input end of the multiplier, the unit arch wave | sin ω x | is input into the second input end of the multiplier, the output end of the multiplier is connected with the positive end of the second operational amplification circuit, and the inductive current I is input into the negative end of the second operational amplification circuitinThe output end of the second operational amplification circuit is connected with the positive end of the third operational amplification circuit, the negative end of the third operational amplification circuit inputs sawtooth waves, and the output end of the third operational amplification circuit outputs a first PWM signal P1；
The second PWM signal generator comprises a fourth amplifying circuit, an AND gate circuit, a NOT gate circuit and an OR gate circuit; the positive end input of the fourth amplifying circuit is constant direct current voltage VDCThe negative end of the fourth amplifying circuit inputs sawtooth waves, and the output end of the fourth amplifying circuit outputs a PWM signal P with constant duty ratio11Constant duty cycle PWM signal P11And the first PWM signal P1Are all input to an AND gate circuit, while a first PWM signal P1The output of the NOT gate circuit and the output of the AND gate circuit are used as the input of an OR gate circuit, and the OR gate circuit outputs a second PWM signal S2。
2. The APFC and switched capacitor converter integrated boost circuit of claim 1, wherein said power input conversion unit comprises: an AC input power supply AC and a rectifier bridge including a diode D 1Diode D2Diode D3Diode D4Diode D1The anode of the diode is respectively connected with one end of an AC input power supply AC and the diode D4Cathode of (2), diode D1Respectively with a diode D2Cathode and input inductance LinIs connected to the input terminal of a diode D2Anode of the diode is respectively connected with the other end of the AC input power supply AC and the diode D3Cathode of (2), diode D3Respectively connected to the second terminal of the second switching tube Q2 and the diode D4The rectifier bridge converts an alternating sine wave input by an alternating input power source AC into an arch wave.
3. The APFC/switched capacitor converter integrated boost circuit of claim 2, wherein the switched capacitor converter unit comprises a diode D5Diode D6Diode D7Diode D8A first flying capacitor C1A second flying capacitor C2And a third flying capacitor C3(ii) a Diode D of a switched capacitor converter unit5As a first input terminal of the switched capacitor converter unit, connected toA first terminal of a first switching tube Q1; diode D5Respectively connected with a diode D6Anode and first flying capacitor C1One terminal of (C), a first flying capacitor1The other end of the first switch tube Q1, the first end of the second switch tube Q2 and the third flying capacitor C are respectively connected as the second input end of the switch capacitor converter unit 3One terminal of (D), diode D6The cathodes of the two capacitors are respectively connected with a second flying capacitor C2And a diode D7Anode of (2), diode D7Respectively connected with a third flying capacitor C3Another terminal of (2) and diode D8Anode of (2), diode D8The cathode of the switch capacitor converter unit is used as a first output end of the switch capacitor converter unit and is connected with one end of the output unit, and the second flying capacitor C2The other end of the first switch tube Q2 is connected with the other end of the output unit and the second end of the second switch tube Q2 respectively as the second output end of the switch capacitance converter unit;
the output unit comprises a capacitor C4And an output resistor RoutSaid capacitor C4And an output resistor RoutAre connected in parallel.
4. The APFC/switched capacitor converter integrated boost circuit of claim 3, wherein the first switch transistor Q is connected to the output of the first transistor1And a second switching tube Q2When the input inductance L is switched on, the AC sine wave input by the AC input power supply is converted into the arch wave and then becomes the input inductance LinCharging, inductor current IinRising, diode D5Diode D6Diode D8Turn-off, diode D7Open, second flying capacitor C2Through diode D7To a third flying capacitor C3Discharging;
when the first switch tube Q1On, second switch tube Q2When the power is turned off, the AC input power supply AC and the input inductor L are connected inFirst flying capacitor C1Connected in series and then passes through diode D6To the second flying capacitor C2Charging, simultaneous AC input power AC and input inductance LinAnd a third flying capacitor C3Series backward capacitor C4Charging while passing through diode D8Is an output resistor RoutEnergy supply, input inductance LinIn the charging state, the inductor current IinGradually rising;
when the first switch tube Q1Turn-off, second switch tube Q2When the switch is on, the AC input power supply and the input inductor L are connectedinSeries backward first flying capacitor C1Charging, second flying capacitor C2Through diode D7To the third flying capacitor C3Discharge and pass through diode D8Is a capacitor C4Charging, input inductance LinThe stored energy is released and stored to the capacitor C1In the inductor current IinThe current drops;
when the first switch tube Q1And a first switch tube Q2When all the input inductors are switched off, the AC of the AC input power supply is rectified by the rectifier bridge and then is connected with the input inductor LinIn series through a diode D5Diode D6Is a second flying capacitor C2Charging, diode D7Diode D8Off, capacitance C4Is an output resistor RoutProviding energy.
5. The APFC/switched capacitor converter integrated boost circuit of claim 4, wherein the first PWM signal Pp is adjusted for a given average current value of the boost circuit 1At a high level, a second PWM signal S2At a high level, the first switch tube Q1And a second switch tube Q2Are all in the open mode, and input inductance LinOf the inductor current IinRise as input inductance LinOf the inductor current IinWhen the current value is larger than the average current value, the first PWM signal P is adjusted1At a low level, the second PWM signal S2At a high level, the first switch tube Q1On/off state, second switch tube Q2In the on mode, the input inductance LinOf the inductor current IinDecrease when the input inductance L is decreasedinOf the inductor current IinWhen the average current value is less than the first value, the first PWM signal P is adjusted1At a high level, the second PWM signal S2At a high level, the firstA switch tube Q1And a second switching tube Q2Are all in the on mode, and input inductance LinOf the inductor current IinRise so that the input inductance LinThe inductance current of the power amplifier changes along with the average current value, so that active power factor correction is realized;
adjusting the first PWM signal P1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure FDA0003680648440000031
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11Represents a PWM signal with a constant duty cycle,
Figure FDA0003680648440000041
indicating that the first PWM signal is negated.
6. The APFC/switched capacitor converter integrated boost circuit of claim 5, wherein the first PWM signal P is regulated 1At a high level, a second PWM signal S2At a low level, the first switch tube Q1On and off of the second switch tube Q2A power-off mode, a power input conversion unit, a first flying capacitor C1All release energy as a second flying capacitor C2Charging, and increasing the output voltage;
adjusting the first PWM signal P1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure FDA0003680648440000042
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal，P11Represents a PWM signal with a constant duty cycle,
Figure FDA0003680648440000043
indicating that the first PWM signal is negated.
7. A method for controlling a boost circuit of an integrated APFC and switched capacitor converter, the method being used for controlling the boost circuit of the integrated APFC and switched capacitor converter of claim 1, comprising:
the modal distribution unit receives the active power factor correction and the boosting requirement issued by a user and sends a first switching tube Q to the first PWM signal generator and the second PWM signal generator1A second switch tube Q2A modality assignment indication of (a);
generating a first PWM signal P by a first PWM signal generator according to the mode allocation indication1Generating a second PWM signal S by a second PWM signal generator2；
The first PWM signal P1The second PWM signal S is input to the third terminal of the first switch tube Q1 2The third end of the first switching tube Q2 is input;
adjusting the first PWM signal P when the input voltage of the power input conversion unit rises1At a high level, a second PWM signal S2At a high level, the first switch tube Q is turned on1And a second switch tube Q2Are all in the opening mode;
adjusting the first PWM signal P when the input voltage of the power input converting unit is decreased1At a low level, a second PWM signal S2At high level, the first switch tube Q1On/off state, second switch tube Q2In the open mode;
adjusting the first PWM signal P when the output voltage needs to be raised1At a high level, the second PWM signal S2At low level, the first switch tube Q is turned on1On, the second switch tube Q2In the off mode.
8. The method of claim 7The control method of the boost circuit integrating APFC and the switch capacitor converter is characterized in that the first PWM signal P is regulated1And a second PWM signal S2The logic function expression of the high and low states of the level is as follows:
P1＝P1
Figure FDA0003680648440000051
wherein S is2Representing a second PWM signal, P1Representing a first PWM signal, P11Represents a PWM signal with a constant duty cycle,
Figure FDA0003680648440000052
indicating that the first PWM signal is negated.
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