CN112928921B - Low-output fluctuation soft switching modulation method for wireless power transmission system - Google Patents

Low-output fluctuation soft switching modulation method for wireless power transmission system Download PDF

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CN112928921B
CN112928921B CN202110126136.7A CN202110126136A CN112928921B CN 112928921 B CN112928921 B CN 112928921B CN 202110126136 A CN202110126136 A CN 202110126136A CN 112928921 B CN112928921 B CN 112928921B
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switching frequency
sequence
subsequences
inverter
switching
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CN112928921A (en
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那拓扑
唐佳棋
李为汉
张千帆
朱春波
张明涛
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Harbin Institute of Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
    • H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

A low-output fluctuation soft switch modulation method for a wireless power transmission system relates to the field of soft switch modulation. The invention aims to solve the problem of large output fluctuation of the existing method for realizing the soft switching of the inverter of the wireless power transmission system. The modulation method reasonably optimizes the pulse sequence and reduces the fluctuation of the output voltage and current of the inverter. The application reorders the output voltage and the current waveforms, so that the output voltage and the current waveforms are more stable, and the fluctuation of the current and the voltage is reduced. The soft switching circuit is used for realizing soft switching operation of the inverter.

Description

Low-output fluctuation soft switching modulation method for wireless power transmission system
Technical Field
The invention relates to a soft switching modulation method. Relates to the field of soft switch modulation.
Background
In order to reduce the loss of the power electronic converter of the wireless power transmission system, most of the existing methods make the input characteristic of the system become inductive by making the switching frequency of the system work higher than the resonant frequency of the wireless power transmission system, so as to realize the soft switching of the inverter of the wireless power transmission system. However, the working frequency of the system can be rapidly increased along with the reduction of the output power, the power factor of the inverter is reduced, and the conduction loss of the inverter is increased; the current frequency of the system deviates from the resonant frequency, causing the frequency of the coupling mechanism to decrease. Other soft switch modulation methods which can be used for a wireless electric energy transmission system or an auxiliary circuit is added, so that the circuit cost is increased, and the system reliability is reduced; or the output fluctuation is large, and large capacitance filtering is needed, so that the power density of the system is reduced.
Disclosure of Invention
The invention aims to solve the problem of large output fluctuation of the existing method for realizing the soft switching of the inverter of the wireless power transmission system. A low output ripple soft switching modulation method for wireless power transfer systems is now provided.
A low output ripple soft switching modulation method for a wireless power transfer system, the method comprising the steps of:
step 1, obtaining the number of 2 switching frequency half cycles which are respectively N according to a set per unit value of the output voltage of the inverternAnd Nn+2N is a positive integer;
step 2, judging whether N is availablen>Nn+2If so, make NA1＝Nn,NB1＝Nn+2Is a reaction of NnCorresponding switching frequency fnThe half period is used as the 1 st switching frequency half period in each subsequence, if not, N is enabledA1＝Nn+2,NB1＝NnIs a reaction of Nn+2Corresponding switching frequency fn+2The half period is used as the 1 st switching frequency half period in each subsequence;
step 3, calculating
Figure BDA0002923575780000011
Quotient q and remainder r;
step 4, judging whether the remainder satisfies r>NB1-r, if so, the number N of 1 st subsequences in the new sequenceAR, the number of the 2 nd subsequence in the new sequence NB＝NB1-r, the 1 st sub-sequence switching frequency half-cycle combination being
Figure BDA0002923575780000012
The 2 nd sub-sequence switching frequency half-cycle combination is
Figure BDA0002923575780000013
The switching frequency half cycles of the two subsequences are combined to form a new sequence;
if not, the number N of the 1 st subsequences in the new sequenceA＝NB1-r, 2 nd sub-sequence in the new sequenceNumber of sequences NBR, the combination of the switching frequency half-cycles of the 1 st subsequence is
Figure BDA0002923575780000021
The 2 nd sub-sequence switching frequency half-cycle combination is
Figure BDA0002923575780000022
The switching frequency half cycles of the two subsequences are combined to form a new sequence;
step 5, respectively using N to the number of the two subsequences of the new sequence obtained in step 4nAnd Nn+2Representing that the steps 2 to 4 are repeatedly executed until the remainder obtained after dividing the number of the 2 subsequences in the obtained final sequence is 0, and synthesizing the 2 subsequences when the remainder is 0 into 1 sequence as a final switching frequency half-cycle sequence;
and 6, controlling the switching state of the inverter according to the final switching frequency half-cycle sequence to realize the soft switching operation of the inverter.
Preferably, in step 1, the number of half cycles of two switching frequencies is obtained according to a per unit value of the set inverter output voltage, specifically:
according to a set per unit value d formula of the output voltage of the inverter:
Figure BDA0002923575780000023
obtaining a switching frequency of fnNumber of half cycles NnAnd a switching frequency of fn+2Number of half cycles Nn+2。
Preferably, the switching frequency fnExpressed as:
Figure BDA0002923575780000024
in the formula, TnIs fnPeriod of (a), (b), (c) and (d)0Is the resonant frequency of the wireless power transfer system.
The invention has the beneficial effects that:
the modulation method reasonably optimizes the pulse sequence (switching frequency) and reduces the output voltage and current fluctuation of the inverter. The application reorders the output voltage and the current waveforms, so that the output voltage and the current waveforms are more stable, and the fluctuation of the current and the voltage is reduced.
According to the soft switch modulation method for the wireless power transmission system, on the premise that resonant cavity current is not changed, system hardware and resonant current frequency are not changed, the inverter can achieve soft switch operation, equivalent switching frequency of the inverter can be reduced, output voltage and current fluctuation are reduced, and switching loss of the inverter is further reduced.
The volume of the output voltage-stabilizing capacitor can be reduced due to low output voltage and current fluctuation, the switching loss of a power device is reduced due to the soft switch, and the volume of the radiating fins is reduced, so that the cost of the system is reduced while the efficiency of a wireless power transmission system is improved.
Drawings
FIG. 1 is a diagram of a typical wireless power transfer system;
FIG. 2 is a graph of inverter output voltage and current waveforms;
FIG. 3 is a graph of unsorted output waveforms;
FIG. 4 is a flow chart for reordering half cycles of two switching frequencies;
FIG. 5 is a waveform diagram after a first reordering;
fig. 6 is a waveform diagram of the final sequence of switching frequency half cycles.
Detailed Description
The first embodiment is as follows: the present embodiment is described with reference to fig. 1 to 6, and the method for soft switching modulation with low output fluctuation for a wireless power transmission system according to the present embodiment includes the following steps:
step 1, obtaining the number of 2 switching frequency half cycles which are respectively N according to a set per unit value of the output voltage of the inverternAnd Nn+2N is a positive integer;
step 2, judging whether N is availablen>Nn+2If so, make NA1＝Nn,NB1＝Nn+2Is a reaction of NnCorresponding switching frequency fnThe half period is used as the 1 st switching frequency half period in each subsequence, if not, N is enabledA1＝Nn+2,NB1＝NnIs a reaction of Nn+2Corresponding switching frequency fn+2The half period is used as the 1 st switching frequency half period in each subsequence;
step 3, calculating
Figure BDA0002923575780000031
Quotient q and remainder r;
step 4, judging whether the remainder satisfies r>NB1-r, if so, the number N of 1 st subsequences in the new sequenceAR, the number of the 2 nd subsequence in the new sequence NB＝NB1-r, the 1 st sub-sequence switching frequency half-cycle combination being
Figure BDA0002923575780000032
The 2 nd sub-sequence switching frequency half-cycle combination is
Figure BDA0002923575780000033
The switching frequency half cycles of the two subsequences are combined to form a new sequence;
if not, the number N of the 1 st subsequences in the new sequenceA＝NB1-r, number of 2 subsequences in new sequence NBR, the combination of the switching frequency half-cycles of the 1 st subsequence is
Figure BDA0002923575780000034
The 2 nd sub-sequence switching frequency half-cycle combination is
Figure BDA0002923575780000035
The switching frequency half cycles of the two subsequences are combined to form a new sequence;
step 5, respectively using N to the number of the two subsequences of the new sequence obtained in step 4nAnd Nn+2To indicate heavyRepeating the steps 2 to 4 until the remainder obtained after dividing the number of the 2 subsequences in the obtained final sequence is 0, and synthesizing the 2 subsequences with the remainder being 0 into 1 sequence serving as a final switching frequency half-cycle sequence;
and 6, controlling the switching state of the inverter according to the final switching frequency half-cycle sequence to realize the soft switching operation of the inverter.
In the present embodiment, mod in fig. 4 is a function of the remainder, SubAk represents the 1 st sub-sequence switching frequency half-cycle combination, SubBk represents the 2 nd sub-sequence switching frequency half-cycle combination, and k is a count variable.
The present application can be applied to wireless power transmission systems with various compensation network topologies, and fig. 1 shows an example of a series compensation network topology wireless power transmission system structure, in which an inductor L is1、L2Is a primary coil and a secondary coil, the coupled mutual inductance is M, four diodes form a rectifier bridge of the secondary, Cf1And Cf2Filter capacitances on the input side and the output side, respectively. By applying the modulation method provided by the application, no other auxiliary circuit is needed. Fig. 2 shows output voltage and current waveforms when the output voltage per unit value d is 9/13, and it can be seen that the current value is zero every time the output voltage is switched, and the inverter realizes soft switching. In the following, we will describe the embodiment by taking the output voltage per unit value d as 9/16 as an example:
for a given output per unit value d, N can be found using the following equationn
Figure BDA0002923575780000041
Here NnThe square wave of the output voltage of the inverter has a frequency fnNumber of half cycles of fnIs composed of
Figure BDA0002923575780000042
Where f is0Is the resonant frequency of the wireless power transfer system.
So, for any given output per unit value d, there is a set of NnAnd Nn+2Equation (1) is established. Given an output per unit d of 9/16, there is N 111 and N 37. The unsorted output waveform is shown in fig. 3, where the voltage fluctuation is large.
In order to reduce the output voltage and current fluctuation, the two frequency components need to be interlaced as much as possible, and the formed new sequence also needs to be interlaced, and is shown in fig. 5.
The next step is to set 11 frequencies as f1Half period of (3) and 7 frequencies of f3Are staggered in accordance with the steps of fig. 4 to reduce the output waveform.
Because of N1/N3Has a quotient of 1 and a remainder of 4, so that the above sequence can be composed of 3 f1f3And 4 f1f1f3The first sorting is completed and the waveforms are as shown in fig. 5.
Repeating the above sequence procedure to obtain 3 f1f3And 4 f1f1f3Can form 2 f1f3f1f1f3Subsequence and 1 f1f3f1f1f3f1f1f3And (4) sequencing.
The above sorting process is repeated until the remainder of 2/1 is 0, indicating that only one subsequence, i.e., the final output sequence, exists, as shown in fig. 6.
The second embodiment is as follows: in this embodiment, as to a method for modulating a soft switch with low output fluctuation for a wireless power transmission system described in the first embodiment, in step 1, the number of half cycles of two switching frequencies is obtained according to a per unit value of a set inverter output voltage, specifically:
according to a set per unit value d formula of the output voltage of the inverter:
Figure BDA0002923575780000051
obtaining a switching frequency of fnNumber of half cycles NnAnd a switching frequency of fn+2Number of half cycles Nn+2。
The third concrete implementation mode: in this embodiment, the switching frequency f is the same as the switching frequency f used in the method for modulating the low-output-fluctuation soft switch in the wireless power transmission system according to the second embodimentnExpressed as:
Figure BDA0002923575780000052
in the formula, TnIs fnPeriod of (a), (b), (c) and (d)0Is the resonant frequency of the wireless power transfer system.

Claims (3)

1. A low output ripple soft switching modulation method for a wireless power transfer system, the method comprising the steps of:
step 1, obtaining the number of 2 switching frequency half cycles which are respectively N according to a set per unit value of the output voltage of the inverternAnd Nn+2N is a positive integer;
step 2, judging whether N is availablen>Nn+2If so, make NA1＝Nn,NB1＝Nn+2Is a reaction of NnCorresponding switching frequency fnThe half period is used as the 1 st switching frequency half period in each subsequence, if not, N is enabledA1＝Nn+2,NB1＝NnIs a reaction of Nn+2Corresponding switching frequency fn+2The half period is used as the 1 st switching frequency half period in each subsequence;
step 3, calculating
Figure FDA0002923575770000011
Quotient q and remainder r;
step 4, judging whether the remainder satisfies r>NB1-r, if so, the number N of 1 st subsequences in the new sequenceAR, the 2 nd subsequence in the new sequenceNumber NB＝NB1-r, the 1 st sub-sequence switching frequency half-cycle combination being
Figure FDA0002923575770000012
The 2 nd sub-sequence switching frequency half-cycle combination is
Figure FDA0002923575770000013
The switching frequency half cycles of the two subsequences are combined to form a new sequence;
if not, the number N of the 1 st subsequences in the new sequenceA＝NB1-r, number of 2 subsequences in new sequence NBR, the combination of the switching frequency half-cycles of the 1 st subsequence is
Figure FDA0002923575770000014
The 2 nd sub-sequence switching frequency half-cycle combination is
Figure FDA0002923575770000015
The switching frequency half cycles of the two subsequences are combined to form a new sequence;
step 5, respectively using N to the number of the two subsequences of the new sequence obtained in step 4nAnd Nn+2Representing that the steps 2 to 4 are repeatedly executed until the remainder obtained after dividing the number of the 2 subsequences in the obtained final sequence is 0, and synthesizing the 2 subsequences when the remainder is 0 into 1 sequence as a final switching frequency half-cycle sequence;
and 6, controlling the switching state of the inverter according to the final switching frequency half-cycle sequence to realize the soft switching operation of the inverter.
2. The method according to claim 1, wherein in step 1, the number of half cycles of two switching frequencies is obtained according to a per unit value of the inverter output voltage, specifically:
according to a set per unit value d formula of the output voltage of the inverter:
Figure FDA0002923575770000021
obtaining a switching frequency of fnNumber of half cycles NnAnd a switching frequency of fn+2Number of half cycles Nn+2。
3. The low output ripple soft switching modulation method of claim 2 wherein the switching frequency f isnExpressed as:
Figure FDA0002923575770000022
in the formula, TnIs fnPeriod of (a), (b), (c) and (d)0Is the resonant frequency of the wireless power transfer system.
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Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108400739A (en) * 2018-05-02 2018-08-14 上海灿瑞科技股份有限公司 A kind of adaptive low noise soft switch circuit of single-phase motor
CN109347345A (en) * 2018-10-29 2019-02-15 河北工业大学 Sine wave inverter
CN110380637A (en) * 2019-03-29 2019-10-25 南京航空航天大学 A kind of hybrid modulation stratgy and its control program of the full-bridge inverter based on critical current mode
CN111934443A (en) * 2020-07-14 2020-11-13 中国矿业大学 Electric energy and signal synchronous wireless transmission method based on soft switch harmonic characteristics

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* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
KR101928437B1 (en) * 2013-01-14 2018-12-12 삼성전자주식회사 Method and Apparatus for controlling output voltage of inverter driving motor

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN108400739A (en) * 2018-05-02 2018-08-14 上海灿瑞科技股份有限公司 A kind of adaptive low noise soft switch circuit of single-phase motor
CN109347345A (en) * 2018-10-29 2019-02-15 河北工业大学 Sine wave inverter
CN110380637A (en) * 2019-03-29 2019-10-25 南京航空航天大学 A kind of hybrid modulation stratgy and its control program of the full-bridge inverter based on critical current mode
CN111934443A (en) * 2020-07-14 2020-11-13 中国矿业大学 Electric energy and signal synchronous wireless transmission method based on soft switch harmonic characteristics

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