CN112260568B - Zero-voltage soft-switching single-phase boost inverter and control method - Google Patents
Zero-voltage soft-switching single-phase boost inverter and control method Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
- H02M7/53871—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration with automatic control of output voltage or current
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0051—Diode reverse recovery losses
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Abstract
The invention belongs to the technical field of inverters, and discloses a zero-voltage soft-switching single-phase boost inverter and a control method thereofFirst inductance L1The first bridge arm, the second bridge arm and the first direct current bus capacitor Cdc1A second DC bus capacitor Cdc2And a second inductor L2And an auxiliary branch circuit with bidirectional current flowing is formed. In a positive half power frequency period, the first bridge arm works in an SPWM mode, and the second bridge arm works in a PWM mode; and in a negative half power frequency period, the working states of the first bridge arm and the second bridge arm are exchanged. The inverter realizes zero-voltage soft switching of two lower bridge arm tubes and one upper bridge arm tube, effectively solves the problem of serious reverse recovery loss of the anti-reverse diode in the traditional integrated inverter, and improves the conversion efficiency.
Description
Technical Field
The invention belongs to the technical field of inverters, and particularly relates to a zero-voltage soft-switching single-phase boost inverter and a control method thereof.
Background
In order to deal with the problems of the traditional fossil energy crisis and the environmental pollution, the renewable energy distributed power generation system has been vigorously developed in various countries in recent years. In these power supply systems, the input side is usually a photovoltaic cell, a fuel cell, or a storage battery, and the output voltage thereof is low and the fluctuation range is large. Therefore, a two-stage structure of a DC/DC Boost converter (such as Boost) cascaded voltage source inverter is commonly used in a distributed power generation system to meet the voltage requirement of a power grid or an alternating current load device. The two-stage boosting inversion scheme can better adapt to the wide variation range of input voltage, is simpler to control, but has more devices and higher cost, and the overall efficiency is difficult to further promote. To this end, researchers have proposed that the Boost converter and the full-bridge inverter in the two-stage Boost inverter be integrated by multiplexing the switching tubes, as shown in fig. 1. Compared with the traditional two-stage boost inverter, the traditional integrated boost inverter shown in fig. 1 realizes the functions of boosting and inverting simultaneously through one-stage power conversion, and has higher conversion efficiency; moreover, a switch tube and a driving device thereof are omitted, and the system cost is reduced. However, all power tubes of the integrated boost inverter are in a high-frequency hard switching state, and the switching loss is serious.
Disclosure of Invention
In view of this, the present application provides a zero-voltage soft-switching single-phase boost inverter, which can realize zero-voltage soft switching of two lower bridge arm tubes and one upper bridge arm tube, and effectively solve the problem of severe reverse recovery loss of an anti-reverse diode in a conventional integrated inverter, thereby improving conversion efficiency.
In order to achieve the purpose, the technical scheme provided by the invention is as follows:
a zero-voltage soft switch single-phase boost inverter comprises a first DC bus capacitor Cdc1A second DC bus capacitor Cdc2DC power supply UinA first inductor L1A second inductor L2A first auxiliary switch tube SaA second auxiliary switch tube SbFirst bridge arm, second bridge arm and filter inductor LfFilter capacitor CfAnd an alternating current load R;
the first bridge arm comprises a first switch tube S1And a second switching tube S2；
The second bridge arm comprises a third switching tube S3And a fourth switching tube S4；
The DC power supply UinAnd the first inductor L1One end is connected;
the first inductor L1And the other end of the second inductor L2ToEnd, the first auxiliary switch tube SaOne end of the second auxiliary switching tube SbIs connected with one end of the connecting rod;
the first auxiliary switch tube SaAnd the other end of the first switch tube S1Source electrode of, the second switching tube S2Drain electrode of, the filter inductance LfIs connected with one end of the connecting rod;
the second auxiliary switch tube SbAnd the other end of the third switching tube S3Source electrode of, the fourth switching tube S4Drain electrode of (1), the filter capacitor CfIs connected to one end of the alternating current load R;
the other end of the alternating current load R and the filter inductor LfAnother terminal of (1), the filter capacitor CfThe other end of the first and second connecting rods is connected;
the DC power supply UinAnd the second switch tube S2Source electrode of, the fourth switching tube S4Source electrode of, the second dc bus capacitor Cdc2The negative electrode of (1) is connected;
the second DC bus capacitor Cdc2And the first direct current bus capacitor Cdc1Negative pole of (1), the second inductance L2The other end of the first and second connecting rods is connected;
the first DC bus capacitor Cdc1And the first switch tube S1The drain electrode of the third switching tube S3Is connected with the drain electrode of the transistor;
all the switch tubes in the first bridge arm and the second bridge arm can be metal oxide semiconductor field effect transistors with diodes, or switch tubes without diodes and diodes are reversely connected in parallel.
Further, a first auxiliary switch tube SaAnd a second auxiliary switch tube SbAre all bidirectional thyristor switch tubes.
Further, the first inductor L1Current peak to peak value Δ IL1The second inductor L2Current peak to peak value Δ IL2And said filter inductance LfCurrent peak to peak value Δ ILfIs enough to satisfyThe following conditions:
in the above formula, when the inverter works in the positive half power frequency cycle, D is the duty cycle of the control signal of the fourth switching tube S4, and when the inverter works in the negative half power frequency cycle, D is the duty cycle of the control signal of the second switching tube S2, M is the modulation ratio, U is the duty cycle of the control signal of the fourth switching tube S3578, andinis a DC supply voltage, IinAs average value of input current, TdAs dead time, CSEach switching tube outputs the capacitance value of the parasitic capacitance, Udc1Is a first DC bus capacitor Cdc1Voltage of Udc2Is a second DC bus capacitor Cdc2R is the ac load resistance.
The invention also provides a control method of the zero-voltage soft-switching single-phase boost inverter, which comprises the following steps: when the inverter works in a positive half power frequency period, a first bridge arm of the inverter works in an SPWM mode, and a second bridge arm works in a PWM mode; when the inverter works in a negative half power frequency period, a first bridge arm of the inverter works in a PWM mode, and a second bridge arm of the inverter works in an SPWM mode.
Further, the control method specifically comprises the following steps:
DC modulated signal urdcWith a unipolar triangular carrier signal ucObtaining a PWM signal through a first comparator CA 1;
sinusoidal ac modulation signal urAnd the unipolar triangular carrier signal ucGenerating an SPWM1 signal via a second comparator CA 2;
the sine AC modulation signal urAnd the unipolar triangular carrier signal ucAfter the superposition, the signal and the zero potential are subjected to the third comparator CA3 to generate an SPWM2 signal;
after the SPWM2 signal is inverted, the signal and an SPWM1 signal pass through an OR gate to obtain an SPWM3 signal;
the sine AC modulation signal urPasses through a fourth comparator CA4 with a zero potential point to obtain positiveA negative polarity decision signal PD, which is simultaneously used as a second auxiliary switch tube SbThe control signal of (2); inverting the positive and negative polarity determination signal PD signal as a first auxiliary switch tube SaThe control signal of (2);
the positive and negative polarity determination signal PD and the SPWM3 signal pass through a first NAND gate NAND1 to obtain an SPWM4 signal;
after the positive and negative polarity determination signal PD is inverted, the SPWM3 signal and the inverted positive and negative polarity determination signal PD pass through a second NAND gate 2 to obtain an SPWM5 signal;
the SPWM4 signal AND the PWM signal pass through a first NAND gate AND1 to obtain a third switching tube S3The control signal of (2); a third switch tube S3The control signal of (1) is inverted to be used as a fourth switch tube S4The control signal of (2);
the SPWM5 signal AND the PWM signal pass through a second NAND gate AND2 to obtain a first switching tube S1The control signal of (2); a first switch tube S1The control signal of (A) is inverted to be used as a second switch tube S2The control signal of (2).
Further, the voltage gain of the zero-voltage soft-switching single-phase boost inverter
Compared with the prior art, the technical scheme of the invention has the following advantages:
the zero-voltage soft-switching single-phase boost inverter provided by the invention replaces two anti-reverse diodes in the traditional integrated boost inverter with two bidirectional thyristors (complementary conduction and one switch per power frequency period), and adopts a first direct-current bus capacitor Cdc1A second DC bus capacitor Cdc2And a second inductance L2The auxiliary branch circuit with bidirectional current circulation is formed, so that zero-voltage soft switching of two lower bridge arm tubes and one upper bridge arm tube is realized, the problem of serious reverse recovery loss of a reverse diode in the traditional integrated inverter is effectively solved, and the conversion efficiency is improved.
Drawings
Fig. 1 is a schematic circuit diagram of a conventional integrated boost inverter;
fig. 2 is a schematic circuit structure diagram of a zero-voltage soft-switching single-phase boost inverter according to an embodiment of the present application;
fig. 3 is a schematic diagram of the switching tube driving signal generation of the zero-voltage soft-switching single-phase boost inverter shown in fig. 2 under the modulation strategy;
fig. 4(a) to (h) are equivalent diagrams of 8 operation modes of the zero-voltage soft-switching single-phase boost inverter shown in fig. 2 in one switching period;
FIG. 5 is a waveform diagram illustrating the main operation of the zero voltage soft switching single phase boost inverter shown in FIG. 2 during a switching cycle;
fig. 6(a) and (b) are simulation waveforms of the zero-voltage soft-switching single-phase boost inverter shown in fig. 2.
Detailed Description
The technical solutions in the embodiments of the present application will be described clearly and completely with reference to the drawings in the embodiments of the present application, and it is obvious that the described embodiments are only a part of the embodiments of the present application, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Fig. 2 shows a schematic circuit structure diagram of a zero-voltage soft-switching single-phase boost inverter according to an embodiment of the present application. As an exemplary and non-limiting embodiment, the zero-voltage soft-switching single-phase boost inverter comprises a first leg, a second leg, a DC power source UinA first DC bus capacitor Cdc1A second DC bus capacitor Cdc2A first inductor L1A second inductor L2A first auxiliary switch tube SaA second auxiliary switch tube SbFilter inductor LfFilter capacitor CfAn alternating current load R; the first bridge arm comprises a first switch tube S1And a second switching tube S2A first switch tube S1Source electrode of and second switching tube S2The drain electrode of the first bridge arm is connected, and the connection point is a point a of the first bridge arm; the second bridge arm comprises a third switching tube S3And a fourthClosing pipe S4A third switching tube S3Source electrode and fourth switching tube S4The drain electrode of the first bridge arm is connected, and the connection point is a point b of the middle point of the second bridge arm; DC power supply UinPositive pole and first inductance L1One end is connected; first inductance L1And the other end of the second inductor L2One end of (1), a first auxiliary switch tube SaOne end of (1), a second auxiliary switch tube SbIs connected with one end of the connecting rod; first auxiliary switch tube SaAnd the other end of the first switch tube S1Source electrode of the first switching tube S2Drain electrode of (1), filter inductor LfIs connected with one end of the connecting rod; second auxiliary switch tube SbThe other end of the first switch tube and the third switch tube S3Source electrode and fourth switching tube S4Drain electrode and filter capacitor CfOne end of the AC load R is connected with one end of the AC load R; the other end of the AC load R and the filter inductor LfAnother terminal of (1), filter capacitor CfThe other end of the first and second connecting rods is connected; DC power supply UinAnd the second switch tube S2Source electrode and fourth switching tube S4Source electrode of the first direct current bus capacitor Cdc2The negative electrode of (1) is connected; second DC bus capacitor Cdc2Positive electrode of the capacitor and a first DC bus capacitor Cdc1Negative pole of (1), second inductance L2The other end of the first and second connecting rods is connected; first DC bus capacitor Cdc1Positive pole and first switch tube S1Drain electrode of (1), third switching tube S3Is connected to the drain of (1).
In this embodiment, all the switch transistors in the first leg and the second leg may be mosfets with diodes or switches without diodes connected in reverse parallel to the diodes.
In this embodiment, the first auxiliary switch tube SaAnd a second auxiliary switch tube SbAre all bidirectional thyristor switch tubes.
Specifically, in this embodiment, the first inductor L1And a filter inductance LfThe inductor is designed conventionally, namely according to the pulsating quantity of the inductor current not exceeding 20% of the maximum current. The second inductance L is designed according to the following conditions2：
In the above formula,. DELTA.IL1Is a first inductance L1Current peak-to-peak value of,. DELTA.IL2Is a second inductance L2Current peak-to-peak value of,. DELTA.ILfIs a filter inductor LfWhen the inverter works in a positive half power frequency period, D is the duty ratio of a control signal of a fourth switching tube S4, when the inverter works in a negative half power frequency period, D is the duty ratio of a control signal of a second switching tube S2, M is a modulation ratio, U is a peak value of the current, and the current is measured by a voltage measuring deviceinIs a DC supply voltage, IinAs average value of input current, TdAs dead time, CsIs the output parasitic capacitance value of the switch tube, Udc1Is a first DC bus capacitor Cdc1Voltage of Udc2Is a second DC bus capacitor Cdc2The voltage of (c).
The control method of the zero-voltage soft-switching single-phase boost inverter (as shown in fig. 2) according to the modulation strategy shown in fig. 3 is described below.
Fig. 3 shows a schematic diagram of the generation of the driving signal of the switching tube under the modulation strategy. In FIG. 3, the DC modulated signal urdcWith a unipolar triangular carrier signal ucObtaining a PWM signal through a first comparator CA 1; sinusoidal ac modulation signal urAnd a unipolar triangular carrier signal ucGenerating an SPWM1 signal via a second comparator CA 2; sinusoidal ac modulation signal urAnd a unipolar triangular carrier signal ucAfter the superposition, the signal and the zero potential are subjected to the third comparator CA3 to generate an SPWM2 signal; after the SPWM2 signal is inverted, the SPWM2 signal and an SPWM1 signal pass through an OR gate to obtain an SPWM3 signal; sinusoidal ac modulation signal urThe positive and negative polarity determination signals PD are obtained by passing through a fourth comparator CA4 with a zero potential point, and are simultaneously used as a second auxiliary switching tube SbTo the second auxiliary switching tube SbThe switching action of (3) is controlled; inverting positive and negative polarity determination signal PD signal as first auxiliary switch tube SaTo the first auxiliary switching tube SaThe switching operation of (2) is controlled. The positive and negative polarity decision signals PD and the SPWM3 signal pass through a first NAND gate NAND1 to obtain an SPWM4 signal; after the positive and negative polarity determination signal PD is inverted, the positive and negative polarity determination signal PD and the SPWM3 signal pass through a second NAND gate NAND2 to obtain an SPWM5 signal; the SPWM4 signal AND the PWM signal pass through a first NAND gate AND1 to obtain a third switch tube S3To the third switch tube S3The switching action of (3) is controlled; a third switch tube S3The control signal of (1) is inverted to be used as a fourth switch tube S4To the fourth switching tube S4The switching action of (3) is controlled; the SPWM5 signal AND the PWM signal pass through a second NAND gate AND2 to obtain a first switching tube S1To the first switching tube S1The switching action of (3) is controlled; a first switch tube S1The control signal of (A) is inverted to be used as a second switch tube S2To the second switching tube S2The switching action of (3) is controlled; regulating a DC modulated signal urdcThe duty cycle D (D ═ u) can be variedrdc/Ucm，UcmIs a unipolar triangular carrier signal ucAmplitude), realizing boost control; adjusting a sinusoidal AC modulated signal urPeak value of UrmThe modulation ratio M (M ═ U) can be changedrm/Ucm) Therefore, the AC output regulation and the waveform control of the inverter are realized.
Under the modulation strategy, the following are:
in the formula of UdcIs a DC bus voltage (equal to the first DC bus capacitance voltage U)dc1And the voltage U of the second DC bus capacitordc2The sum).
In the formula of UomIn the embodiment of the present invention, the output voltage is the voltage across the ac load R, which is the peak value of the output voltage.
Thus, the voltage gain of the soft-switched boost inverter is:
wherein the content of the first and second substances,
M＜D (4)
the operation of the zero-voltage soft-switching single-phase boost inverter according to the circuit connection method of fig. 2 and the modulation strategy of fig. 3 will be described.
The operation of the inverter of the present invention can be divided into 8 modes in one switching cycle, and the current i of the first inductor is defined in fig. 2L1Current i of the second inductorL2And an input voltage UinFirst DC bus capacitor voltage Udc1A second DC bus capacitor voltage Udc2The system has entered steady state operation; except for considering the output parasitic capacitances of all the switching tubes in the first arm and the second arm, neglecting other parasitic parameters of the switching tubes, in the embodiment of the present invention, the output parasitic capacitances of the first switching tube S1, the second switching tube S2, the third switching tube S3, and the fourth switching tube S4 are equal, and all of the output parasitic capacitances are Cs(ii) a The energy storage elements are all ideal devices, a capacitor Cdc1、Cdc2Large enough that voltage ripple is negligible; first inductance L1A second inductor L2The current of (2) is continuous; in the power frequency positive half period, the first auxiliary switch tube S of the soft switch inverter provided by the inventionaIs always turned off, and the second auxiliary switch tube SbIs always on; in the negative half-cycle of power frequency, the first auxiliary switch tube SaAlways on, and the second auxiliary switch tube SbIs always turned off; the negative end of the input power supply is a zero potential reference point, and the alternating current load R is pure resistance.
When the zero-voltage soft-switching single-phase boost inverter is in a working state of a power-frequency positive half cycle, the first bridge arm is an inverter bridge arm, the second bridge arm is a boost bridge arm, and equivalent circuits of all modes are respectively shown in fig. 4(a) to 4 (h); the main waveforms in one switching cycle are schematically shown in fig. 5.
The following are distinguished:
t0before the moment, the AC load R passes through the second switch tube S2And a fourth switching tube S4Freewheeling the parasitic diode.
Mode 1: [ t ] of0-t1](the equivalent circuit is shown in FIG. 4 (a))
t0At the moment, the second switch tube S2And a fourth switching tube S4The zero voltage turns on its parasitic diodes and all turn off naturally, mode 1 begins. a. The b point potentials are all 0, and the first inductor L1A first inductor L2Are subject to a forward voltage. Thus, the first inductance L1Current i ofL1Linearly increasing, second inductance L2Current i ofL2The inverse linear decrease is expressed as:
mode 2: [ t ] of1-t2](the equivalent circuit is shown in FIG. 4 (b))
t1At the moment, the second switch tube S is turned off2 Mode 1 ends and mode 2 begins. A second switch tube S2The parasitic diode of (a) is turned on and the ac load R freewheels therethrough. First inductance L1Current i ofL1And a second inductance L2Current i ofL2Keeping the original slope to continue to increase linearly.
Modality 3: [ t ] of2-t3](the equivalent circuit is shown in FIG. 4 (c))
t2At the moment, the first switch tube S1Hard on, second switch tube S2The parasitic diode of (2) is turned off hard, mode 2 ends and mode 3 begins. The potential of the point a is changed into a DC bus voltage Udc. The direct current bus passes through a first switch tube S1And a fourth switching tube S4Power is supplied to an ac load R.First inductance L1Current i ofL1And a second inductance L2Current i ofL2The original slope is kept to continuously change linearly.
Modality 4: [ t ] of3-t4](the equivalent circuit is shown in FIG. 4 (d))
t3At the moment, the fourth switching tube S is turned off4Modality 3 ends and modality 4 begins. Third switch tube S3And a fourth switching tube S4The output parasitic capacitance of (b) is in a discharging state and a charging state respectively, and the potential of the point b gradually rises from 0. This process is of short duration and approximates to the first inductance L1Current i ofL1And a second inductance L2Current i ofL2Remain unchanged.
Mode 5: [ t ] of4-t5](the equivalent circuit is shown in FIG. 4 (e))
t4At the moment, the third switch tube S3And a fourth switching tube S4The output parasitic capacitance of (b) is charged and discharged, the point b rises to the DC bus voltage UdcA third switching tube S3The parasitic diode of (1) is turned on, mode 5 ends and mode 6 begins. The AC load R passes through the first switch tube S1And a third switching tube S3Freewheeling the parasitic diode. First inductance L1A second inductor L2Are all subject to reverse voltage, therefore, the first inductor L1Current i ofL1And a second inductance L2Current i ofL2Linear decrease, expressed as:
modality 6: [ t ] of5-t6](the equivalent circuit is shown in FIG. 4 (f))
t5At the moment, the third switch tube S3The zero voltage turns on. Modality 5 ends and modality 6 begins. The AC load R passes through the firstSwitch tube S1And a third switching tube S3Free-wheeling the channel. First inductance L1Current i ofL1And a second inductance L2Current i ofL2The original slope is kept to continuously change linearly. It should be noted that the second inductance L2Current i ofL2Decreasing to 0 increases the inverse linearity.
Modality 7: [ t ] of6-t7](the equivalent circuit is shown in FIG. 4 (g))
t6At any moment, the first switch tube S is turned off1And a third switching tube S3Mode 8 ends and mode 9 begins. A second switch tube S2The parasitic diode of (a) is turned on and the potential at the point a becomes 0. Third switch tube S3And a fourth switching tube S4The output parasitic capacitance of the capacitor is respectively in a charging state and a discharging state, and the potential of a point b is controlled by a direct current bus voltage UdcGradually decreases. This process is of short duration and approximates to the first inductance L1Current i ofL1And a second inductance L2Current i ofL2Remain unchanged.
Modality 8: [ t ] of7-t8](the equivalent circuit is shown in FIG. 4 (h))
t7At the moment, the third switch tube S3And a fourth switching tube S4The output parasitic capacitance of (1) is charged and discharged, the potential of the point b is reduced to 0, and the fourth switch tube S4The parasitic diode of (1) is turned on, mode 9 ends and mode 10 begins. The AC load R passes through the second switch tube S2And a fourth switching tube S4Freewheeling the parasitic diode. First inductance L1Current i ofL1And a second inductance L2Current i ofL2The original slope is kept to continuously change linearly.
t8At the moment, the second switch tube S2And a fourth switching tube S4Zero voltage is turned on, mode 10 ends, the next switching cycle begins, and the process is repeated.
When the single-phase boost inverter with the zero-voltage soft switching is in a power-frequency negative half-cycle working state, the first bridge arm is a boost bridge arm, the second bridge arm is an inverter bridge arm, each modal process of the inverter is similar to that in the power-frequency positive half-cycle working state, and the lower tubes of the two bridge arms and the upper tube of the boost bridge arm can also realize the zero-voltage soft switching.
Based on the above analysis of the operating principle of the inverter of the present invention, the soft switching condition thereof is analyzed below.
From the modal analysis, it can be seen that to realize the third switching tube S3And a fourth switching tube S4The zero voltage of the switching tube S is required to be completed within the dead time3And a fourth switching tube S4The charging and discharging of the output parasitic capacitance and the turning on of the body diode of (1) require:
in the formula IL1,valAnd IL2,valRespectively represent the first inductance L1And a second inductance L2The current valley magnitude of (2) as shown in fig. 4. I isf,pkFor outputting filtered inductor current peak value, CsAnd the capacitance values of output parasitic capacitances of all the switching tubes in the first bridge arm and the second bridge arm are obtained.
Setting a first inductance L1A second inductor L2Filter inductor LfRespectively has a maximum inductance current pulse quantity of delta IL1、ΔIL2、ΔILfThe following can be obtained:
in the formula Io,maxAs the maximum output current, it can be seen from equation (2):
soft switching conditions can be obtained by substituting equations (10) and (11) for equation (9):
the inverter of the present invention is subjected to parameter design as follows.
Designing parameters of the inductance and capacitance of the converter according to the following system parameters, namely, the input voltage UinIs 48V, the DC bus voltage UdcAt 223V, the output voltage amplitude UomAt 156V, switching frequency fsAt 20kHz, output power Po250W, frequency f 50Hz, and modulation ratio M of 0.7.
If the inductance L is1Is less than 20% of its maximum average current, i.e. Δ IL1≤0.2IinThen, there are:
if the filter inductance LfIs less than 20% of its maximum output current, i.e. Δ ILf≤0.2Io,maxThen, there are:
formula (12) can be substituted with formula (13) and formula (14):
namely, the requirements are as follows:
because the instantaneous input and output power of the single-stage boost inverter is unbalanced, the voltage of the direct-current bus is in double-frequency pulsation. The direct current bus voltage double frequency ripple rate is as follows:
in the formula, the DC bus voltage UdcIs the average value of the DC bus voltage, Cdc1、Cdc2Is the capacitance value of the first DC bus and the second DC busgAt angular frequency, P, of the mains voltagein,maxFor maximum input power, Δ udcThe peak value of the low-frequency ripple pulse of the direct current bus is shown. Then, the peak-to-peak value Δ u of the low-frequency ripple of the DC busdcComprises the following steps:
peak-to-peak value delta u of low-frequency ripple pulse of direct-current busdcLower than the DC bus voltage U dc1% of the first DC bus capacitor and the second DC bus capacitor have the same capacitance value Cdc1＝Cdc2＝CdcFrom equation (18):
based on the modal analysis, the soft switching condition analysis and the parameter design, the inverter is subjected to simulation verification as follows:
in order to verify the correctness of theoretical analysis, according to the parameter design, Saber simulation software is used for carrying out simulation verification on the soft switching boost inverter. The main circuit parameters are set as follows: first inductance L12mH, second inductance L290uH, the first DC bus capacitor and the second DC bus capacitor Cdc1＝Cdc23.5mF, filter capacitance Cf20uF, filter inductance Lf＝20mH。
The waveform of the simulation experiment is shown in fig. 6. FIG. 6(a) shows the input voltage, DC bus voltage, output voltage current, and first auxiliary switch S of the boost inverteraA second auxiliary switch tube SbDrive signal and terminal voltage, etc. It can be seen that the voltage gain G-156/48-3.25 realizes the inverse boostChanging; first auxiliary switch tube SaThe second boost switching tube SbComplementary conduction and switching once per power frequency period, which is consistent with theory. FIG. 6(b) shows the first switch tube S in the power frequency positive half cycle1A second switch tube S2A third switch tube S3And a fourth switching tube S4And a first switching tube S1A second switch tube S2A third switch tube S3And a fourth switching tube S4Voltage, current, etc. It can be seen that the second switch tube S is before the positive voltage of the driving signal comes2A third switch tube S3And a fourth switching tube S4The terminal voltage is reduced to zero, zero voltage switching-on is realized, and the correctness of theoretical analysis is verified.
It is noted that, herein, relational terms such as first and second, and the like may be used solely to distinguish one entity or action from another entity or action without necessarily requiring or implying any actual such relationship or order between such entities or actions. Also, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or apparatus that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or apparatus. Without further limitation, an element defined by the phrase "comprising an … …" does not exclude the presence of other identical elements in a process, method, article, or apparatus that comprises the element.
The above description of the embodiments is only intended to facilitate the understanding of the method of the invention and its core idea, and not to limit it. It should be noted that, for those skilled in the art, without departing from the principle of the present invention, several improvements and modifications can be made to the present invention, and these improvements and modifications also fall into the protection scope of the present invention.
Claims (6)
1. A zero-voltage soft-switching single-phase boost inverter is characterized in thatComprises a first DC bus capacitor Cdc1A second DC bus capacitor Cdc2DC power supply UinA first inductor L1A second inductor L2A first auxiliary switch tube SaA second auxiliary switch tube SbFirst bridge arm, second bridge arm and filter inductor LfFilter capacitor CfAnd an alternating current load R;
the first bridge arm comprises a first switch tube S1And a second switching tube S2；
The second bridge arm comprises a third switching tube S3And a fourth switching tube S4；
The DC power supply UinAnd the first inductor L1One end is connected;
the first inductor L1And the other end of the second inductor L2One end of the first auxiliary switching tube SaOne end of the second auxiliary switching tube SbIs connected with one end of the connecting rod;
the first auxiliary switch tube SaAnd the other end of the first switch tube S1Source electrode of, the second switching tube S2Drain electrode of, the filter inductance LfIs connected with one end of the connecting rod;
the second auxiliary switch tube SbAnd the other end of the third switching tube S3Source electrode of, the fourth switching tube S4Drain electrode of (1), the filter capacitor CfIs connected to one end of the alternating current load R;
the other end of the alternating current load R and the filter inductor LfAnother terminal of (1), the filter capacitor CfThe other end of the first and second connecting rods is connected;
the DC power supply UinAnd the second switch tube S2Source electrode of, the fourth switching tube S4Source electrode of, the second dc bus capacitor Cdc2The negative electrode of (1) is connected;
the second DC bus capacitor Cdc2And the first direct current bus capacitor Cdc1Negative pole of (1), the second inductance L2The other end of the first and second connecting rods is connected;
the first DC bus capacitor Cdc1And the first switch tube S1The drain electrode of the third switching tube S3Is connected with the drain electrode of the transistor;
all the switch tubes in the first bridge arm and the second bridge arm are metal-oxide-semiconductor field effect transistors with body diodes, or the switch tubes without the body diodes are reversely connected in parallel with the diodes.
2. The zero-voltage soft-switching single-phase boost inverter according to claim 1, wherein the first auxiliary switching tube SaAnd a second auxiliary switch tube SbAre all bidirectional thyristor switch tubes.
3. The zero-voltage soft-switching single-phase boost inverter according to claim 1, wherein said first inductor L1Current peak to peak value Δ IL1The second inductor L2Current peak to peak value Δ IL2And said filter inductance LfCurrent peak to peak value Δ ILfThe following conditions are satisfied:
in the above formula, when the inverter works in the positive half power frequency cycle, D is the duty cycle of the control signal of the fourth switching tube S4, and when the inverter works in the negative half power frequency cycle, D is the duty cycle of the control signal of the second switching tube S2, M is the modulation ratio, U is the duty cycle of the control signal of the fourth switching tube S3578, andinis a DC supply voltage, IinAs average value of input current, TdAs dead time, CSEach switching tube outputs the capacitance value of the parasitic capacitance, Udc1Is a first DC bus capacitor Cdc1Voltage of Udc2Is a second DC bus capacitor Cdc2R is the ac load resistance.
4. A control method of a zero-voltage soft-switching single-phase boost inverter according to any one of claims 1 to 3, characterized in that when the inverter operates in a positive half power frequency cycle, a first bridge arm of the inverter operates in an SPWM mode, and a second bridge arm operates in a PWM mode; when the inverter works in a negative half power frequency period, a first bridge arm of the inverter works in a PWM mode, and a second bridge arm of the inverter works in an SPWM mode.
5. The control method of the zero-voltage soft-switching single-phase boost inverter according to claim 4, characterized in that the control method is specifically:
DC modulated signal urdcWith a unipolar triangular carrier signal ucObtaining a PWM signal through a first comparator CA 1;
sinusoidal ac modulation signal urAnd the unipolar triangular carrier signal ucGenerating an SPWM1 signal via a second comparator CA 2;
the sine AC modulation signal urAnd the unipolar triangular carrier signal ucAfter the superposition, the signal and the zero potential are subjected to the third comparator CA3 to generate an SPWM2 signal;
after the SPWM2 signal is inverted, the signal and an SPWM1 signal pass through an OR gate to obtain an SPWM3 signal;
the sine AC modulation signal urThe positive and negative polarity determination signals PD are obtained by passing through a fourth comparator CA4 together with a zero potential point, and are simultaneously used as a second auxiliary switching tube SbThe control signal of (2); inverting the positive and negative polarity determination signal PD signal as a first auxiliary switch tube SaThe control signal of (2);
the positive and negative polarity determination signal PD and the SPWM3 signal pass through a first NAND gate NAND1 to obtain an SPWM4 signal;
after the positive and negative polarity determination signal PD is inverted, the SPWM3 signal and the inverted positive and negative polarity determination signal PD pass through a second NAND gate 2 to obtain an SPWM5 signal;
the SPWM4 signal AND the PWM signal pass through a first NAND gate AND1 to obtain a third switching tube S3The control signal of (2); a third switch tube S3The control signal of (1) is inverted to be used as a fourth switch tube S4The control signal of (2);
the SPWM5 signal AND the PWM signal pass through a second NAND gate AND2 to obtain a first switching tube S1The control signal of (2); a first switch tube S1The control signal of (A) is inverted to be used as a second switch tube S2The control signal of (2).
6. The method of claim 5, wherein the voltage gain of the zero voltage soft-switching single phase boost inverter is determined by the voltage gain control unit
M＜D，
Wherein, D is the duty ratio of the control signal of the second switching tube S2, and M is the modulation ratio.
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