CN111342475A - Modulation method of H-bridge cascaded active power filter - Google Patents

Modulation method of H-bridge cascaded active power filter Download PDF

Info

Publication number
CN111342475A
CN111342475A CN202010416828.0A CN202010416828A CN111342475A CN 111342475 A CN111342475 A CN 111342475A CN 202010416828 A CN202010416828 A CN 202010416828A CN 111342475 A CN111342475 A CN 111342475A
Authority
CN
China
Prior art keywords
carrier
phase
harmonic
frequency
harmonic current
Prior art date
Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Pending
Application number
CN202010416828.0A
Other languages
Chinese (zh)
Inventor
舒展
熊华强
李升健
陈波
程思萌
陶翔
汪硕承
蔡霞
邓健
Current Assignee (The listed assignees may be inaccurate. Google has not performed a legal analysis and makes no representation or warranty as to the accuracy of the list.)
State Grid Corp of China SGCC
Electric Power Research Institute of State Grid Jiangxi Electric Power Co Ltd
Original Assignee
State Grid Corp of China SGCC
Electric Power Research Institute of State Grid Jiangxi Electric Power Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by State Grid Corp of China SGCC, Electric Power Research Institute of State Grid Jiangxi Electric Power Co Ltd filed Critical State Grid Corp of China SGCC
Priority to CN202010416828.0A priority Critical patent/CN111342475A/en
Publication of CN111342475A publication Critical patent/CN111342475A/en
Pending legal-status Critical Current

Links

Images

Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/18—Arrangements for adjusting, eliminating or compensating reactive power in networks
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/01—Arrangements for reducing harmonics or ripples
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/24—Arrangements for preventing or reducing oscillations of power in networks
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
    • H02J3/00—Circuit arrangements for ac mains or ac distribution networks
    • H02J3/26—Arrangements for eliminating or reducing asymmetry in polyphase networks
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/20—Active power filtering [APF]
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
    • Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
    • Y02E40/50—Arrangements for eliminating or reducing asymmetry in polyphase networks

Abstract

The invention discloses a modulation method of an H-bridge cascaded active power filter, which aims to solve the problem of balancing direct-current side voltage between inner modules under the condition that a cascaded H bridge is subjected to a carrier phase shift modulation method. When the switching frequency is lower, the side frequency switch harmonic waves of the unit output voltage can be mapped to the power frequency and coupled with the power frequency current, so that the fundamental wave energy of each unit is uneven. When the switching frequency is high, the non-power frequency harmonic current is also coupled with the side frequency voltage, so that the functional quantity of each module unit is unbalanced. In addition, the active power brought by the difference of the triangular carriers in the carrier phase shift to a single module is not equal. The generation of the energy unevenness is suppressed by optimizing the carrier frequency in combination with the periodic rotation of the triangular carrier.

Description

Modulation method of H-bridge cascaded active power filter
Technical Field
The invention relates to the field of power factor correction technology and motors, in particular to a modulation method of an H-bridge cascaded active power filter.
Background
An Active Power Filter (APF) is a Power electronic device for dynamically realizing harmonic, reactive and three-phase unbalance compensation, and a chain H-bridge structure is a topology commonly applied to the current Active Power Filter. However, the problem of controlling the direct-current side voltage of each unit of the cascaded H-bridge is one of the important problems, and at present, a plurality of control methods of the direct-current side voltage achieve good effects, but few methods consider the direct-current side voltage balance of the units in the phase from the direction of a modulation method.
The existing carrier phase-shifting modulation method can enable the switching voltage harmonic of the low-order harmonic cluster to be offset in the total output voltage, but each unit still contains the harmonic components, the harmonic components are coupled with the harmonic current output by the device to generate power to cause active fluctuation, and the difference of triangular carriers also has influence on the voltage balance of each unit.
In recent years, with the rapid development of domestic economy, increasingly nonlinear, impulsive reactive and unbalanced loads are put into a power grid. This makes harmonic, reactive and three-phase imbalances in the distribution network a non-negligible problem. However, an active power filter is an effective way to solve this problem. In order to obtain a better compensation effect, a current control method, a direct-current side voltage control method and a modulation method need to be continuously explored and optimized.
In order to solve the problem of balancing the direct-current side voltage of the in-phase unit, an optimized modulation method for the cascaded H-bridge type active power filter is provided on the premise of good direct-current side voltage control, so that the problem of coupling of harmonic current and switch harmonic voltage can be solved, and the influence of triangular carrier difference on the balance of the direct-current side voltage can be reduced.
Disclosure of Invention
The technical problems to be solved by the invention are as follows: when the switching frequency is lower, the side frequency switch harmonic waves of the unit output voltage can be mapped to the power frequency and coupled with the power frequency current, so that the fundamental wave energy of each unit is uneven. When the switching frequency is high, the non-power frequency harmonic current is also coupled with the side frequency voltage, so that the functional quantity of each module unit is unbalanced. In order to suppress the generation of the energy unevenness, the invention designs an optimized modulation method aiming at the H-bridge cascade active power filter, which can be realized by optimizing the carrier frequency to ensure that the output harmonic current is inconsistent with the frequency of the harmonic voltage of the unit. In order to eliminate the phenomenon that active power brought by the difference of the triangular carriers in the carrier phase shift to a single module is unequal, the triangular carriers of each module are repeatedly and periodically rotated after a period of time.
The technical scheme adopted by the invention is as follows: a modulation method of an H-bridge cascaded active power filter solves the problem of balancing direct-current side voltage between inner modules of a cascaded H-bridge under a carrier phase shift modulation method by using a mode of optimizing carrier frequency and combining triangular carrier periodic alternation.
Taking a certain phase of the cascaded H bridge as an example, the method comprises the following steps:
s1: sequentially shifting the phase of the carrier waves of N units of the cascaded H bridge
Figure DEST_PATH_IMAGE001
。
S2: and adopting optimal offset for the carrier wave after phase shifting.
The optimal value of the offset is selected as follows: the output voltage u of the ith unit of any phase in the active power filters a, b and c can be obtained by a double Fourier transform formulaiAfter double fourier expansion:
Figure 564418DEST_PATH_IMAGE002
in the formula, MiIs the modulation ratio of the ith H-bridge unit of the phase; edciIs the DC side voltage of the ith cell of the phase of the H-bridge; omegasIs the angular frequency of the modulated wave; omegacIs the angular frequency of the triangular carrier; j. the design is a squarenIs a Bessel function; m is the fundamental wave modulation ratio; m is the carrier harmonic frequency, m is more than or equal to 1 and is an integer; n is sideband harmonic frequency, and n is an odd number;
due to side band harmonics
Figure DEST_PATH_IMAGE003
N in (1) is an odd number and m is an integer greater than or equal to 1, so that the harmonic interval of adjacent sidebands near a certain carrier harmonic is 100Hz, and in order to prevent the offset sideband harmonic voltage from coinciding with the adjacent harmonic current again, precondition constraint is carried out on the optimized offset:
Figure 758770DEST_PATH_IMAGE004
in the formula (I), the compound is shown in the specification,
Figure DEST_PATH_IMAGE005
is the carrier offset;
harmonic current output on corresponding phase of active power filter
Figure 332971DEST_PATH_IMAGE006
Is composed of
Figure DEST_PATH_IMAGE007
In the formula (I), the compound is shown in the specification,
Figure 859636DEST_PATH_IMAGE008
is the harmonic current amplitude;
Figure DEST_PATH_IMAGE009
is the harmonic current phase angle;
Figure 479973DEST_PATH_IMAGE010
is the harmonic current angular frequency;
correspondingly, the coupling power of the ith H-bridge unit corresponding to the phase is obtained by multiplying the harmonic current and the harmonic voltage flowing through the phase
Figure DEST_PATH_IMAGE011
In the formula (I), the compound is shown in the specification,
Figure 884541DEST_PATH_IMAGE012
for the ith cell corresponding to the harmonic current
Figure DEST_PATH_IMAGE013
The generated coupling power;
Figure 437882DEST_PATH_IMAGE014
is carrier offset
Figure DEST_PATH_IMAGE015
Intermediate angular frequency of output voltage of the ith unit
Figure 135448DEST_PATH_IMAGE016
A harmonic component of (a);
Figure 915185DEST_PATH_IMAGE013
the output harmonic current;
Figure DEST_PATH_IMAGE017
is the harmonic current angular frequency; m is the carrier harmonic frequency, m is more than or equal to 1 and is an integer;
Figure 372711DEST_PATH_IMAGE015
is the carrier offset;
Figure 133DEST_PATH_IMAGE018
is the harmonic current amplitude; edciIs the DC side voltage of the ith cell of the phase of the H-bridge; m is the fundamental wave modulation ratio;
Figure DEST_PATH_IMAGE019
is the harmonic current phase angle;
coupled power
Figure 822595DEST_PATH_IMAGE012
Integrating to obtain the energy exchange amount of the DC side capacitor
Figure 683104DEST_PATH_IMAGE020
In the formula (I), the compound is shown in the specification,
Figure DEST_PATH_IMAGE021
for the ith cell corresponding to the harmonic current
Figure 928010DEST_PATH_IMAGE013
The generated energy of the direct current side capacitor fluctuates;
Figure 65730DEST_PATH_IMAGE012
for the ith cell corresponding to the harmonic current
Figure 652569DEST_PATH_IMAGE013
The generated coupling power;
Figure 875740DEST_PATH_IMAGE018
is the harmonic current amplitude; edciIs the DC side voltage of the ith cell of the phase of the H-bridge; m is the fundamental wave modulation ratio; m is the carrier harmonic frequency, m is more than or equal to 1 and is an integer;
Figure 878331DEST_PATH_IMAGE017
is the harmonic current angular frequency;
Figure 745924DEST_PATH_IMAGE015
is the carrier offset;
Figure 379031DEST_PATH_IMAGE019
is the harmonic current phase angle;
the energy fluctuation of the direct current side capacitor of the active power filter corresponding to a certain harmonic current frequency is obtained by the above formula
Figure DEST_PATH_IMAGE023
Offset from carrier
Figure 214131DEST_PATH_IMAGE024
The relationship (2) of (c).
The harmonic current in actual operation contains a plurality of frequency components, and energy fluctuation generated by each subharmonic frequency component is added to obtain the fluctuation amount of the total energy of the unit
Figure DEST_PATH_IMAGE025
Adding the total energy fluctuations of N units to obtain the total energy fluctuation of a single phase
Figure 89856DEST_PATH_IMAGE026
：
Figure DEST_PATH_IMAGE027
In the formula (I), the compound is shown in the specification,
Figure 202169DEST_PATH_IMAGE026
total energy fluctuation for a single phase; n is the number of single-phase cascade modules;
Figure 130810DEST_PATH_IMAGE025
the energy of the capacitor at the direct current side of the ith unit fluctuates;
thereby obtaining total energy fluctuation
Figure 62994DEST_PATH_IMAGE026
And carrier offset
Figure 407388DEST_PATH_IMAGE024
In relation to (1) in
Figure 249573DEST_PATH_IMAGE026
Obtaining the carrier offset of the system at the minimum
Figure 958903DEST_PATH_IMAGE024
The optimum value of (c).
S3: and carrying out alternate operation on each optimized unit carrier wave in each power frequency period.
The scheme of the invention has the following beneficial effects:
meanwhile, the influence of the coupling of harmonic current and switch harmonic voltage and the difference of triangular carriers on the voltage balance of the direct current side of each unit in the phase is solved.
Drawings
Fig. 1 is a topological structure diagram of an H-bridge cascade type active power filter;
fig. 2 is a schematic diagram of a conventional carrier phase shift when the number of cascades is 4 (N = 4);
fig. 3 is a schematic diagram of carrier phase shift after carrier offset when the number of cascades is 4 (N = 4);
fig. 4 is a schematic diagram of carrier rotation after carrier offset when the cascade number is 4 (N = 4);
FIG. 5 is a block diagram illustrating an exemplary implementation of a system for obtaining an optimal carrier offset;
fig. 6 is a dc-side voltage waveform of each unit before the modulation method is optimized when the number of cascades is 4 (N = 4);
fig. 7 shows dc-side voltage waveforms of the respective cells after the modulation method is optimized when the number of cascades is 4 (N = 4).
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Fig. 1 is a structure diagram of a cascaded H-bridge converter, wherein L is a three-phase connection reactor; r is the device loss equivalent resistance;
Figure 768596DEST_PATH_IMAGE028
、
Figure DEST_PATH_IMAGE029
and
Figure 385522DEST_PATH_IMAGE030
is the system voltage;
Figure DEST_PATH_IMAGE031
、
Figure 580749DEST_PATH_IMAGE032
and
Figure DEST_PATH_IMAGE033
is the system current;
Figure 320035DEST_PATH_IMAGE034
、
Figure DEST_PATH_IMAGE035
and
Figure 492390DEST_PATH_IMAGE036
is the load current;
Figure DEST_PATH_IMAGE037
、
Figure 460478DEST_PATH_IMAGE038
and
Figure DEST_PATH_IMAGE039
to compensate for the current; n is the number of power modules of each phase,
Figure 792102DEST_PATH_IMAGE040
；
Figure DEST_PATH_IMAGE041
the value range of i is 1, 2, ˑ ˑ ˑ and N for the direct-current side capacitance of any phase i power module in the cascaded inverter units a, b and c of the converter;
Figure 108814DEST_PATH_IMAGE042
、
Figure DEST_PATH_IMAGE043
and
Figure 345629DEST_PATH_IMAGE044
is the total output voltage of each phase. A modulation method of an H-bridge cascade active power filter comprises the following 3 steps:
s1: firstly, each phase of each unit of N unit cascade H bridges is subjected to carrier phase shift in sequence, and the phase shift angle is
Figure 897833DEST_PATH_IMAGE045
As shown in fig. 2.
S2: according to the relation between the direct current side capacitance energy fluctuation and the carrier offset, the optimal value of the carrier offset corresponding to the subharmonic can be obtained.
The harmonic current of the active power filter in actual operation contains a plurality of frequency components, and the energy fluctuations of each harmonic can be added to obtain the relationship between the total energy fluctuation and the carrier offset, so as to obtain the optimal value of the carrier offset of the system, and the comprehensive implementation block diagram is shown in fig. 5. The carrier phase shift diagram after carrier offset is shown in fig. 3.
S3, performing rotation operation on the three-phase triangular carrier wave in each power frequency period, as shown in FIG. 4, at a rotation point 1, giving the carrier wave of the unit 1 to the unit 2, giving the carrier wave of the unit 2 to the unit 3, giving the carrier wave of the unit 3 to the unit 4, and giving the carrier wave of the unit 4 to the unit 1; at the rotation point 2, the carrier of cell 1 is given to cell 3, the carrier of cell 2 is given to cell 4, the carrier of cell 3 is given to cell 1, and the carrier of cell 4 is given to cell 2; at the rotation point 3, the carrier of cell 1 is given to cell 4, the carrier of cell 2 is given to cell 3, the carrier of cell 3 is given to cell 2, and the carrier of cell 4 is given to cell 1.
In order to verify the effect of the modulation method, a model of a cascade H-bridge unit is built in MATLAB/Simulink to observe the optimization effect, the cascade number is 4 (N = 4), the rated voltage of a direct-current side capacitor is 800V, and the triangular wave frequency is 600 Hz. In order to verify the influence of harmonic coupling power on the dc-side balance of each unit, the selected harmonic loads include 17, 19, and 23 times of harmonic currents, the peak values are all 10A, the dc-side voltage waveforms of each unit are as shown in fig. 6 without implementing the optimal modulation method, and the dc-side voltage waveforms of each unit after the optimal modulation method are as shown in fig. 7, so that it can be seen that the dc-side voltages of the four units maintain balance well under the optimal modulation method.
Those skilled in the art will recognize that numerous variations are possible in light of the above description, and thus the examples are intended to describe one or more specific embodiments.
The above description is only for the purpose of describing the preferred embodiments of the present invention, and is not intended to limit the scope of the present invention, and various modifications and improvements made to the technical solution of the present invention by those skilled in the art without departing from the spirit of the present invention, should fall within the protection scope defined by the claims of the present invention.

Claims (3)

1. A modulation method of an H-bridge cascaded active power filter is characterized in that: the method comprises the step of solving the problem of balancing direct-current side voltage between inner modules of a cascade H bridge under a carrier phase shift modulation method by adopting an optimized carrier frequency and triangular carrier periodic alternation mode.
2. Taking a certain phase of the cascaded H bridge as an example, the method comprises the following steps:
s1: sequentially shifting the phase of the carrier waves of N units of the cascaded H bridge
Figure 318613DEST_PATH_IMAGE001
；
S2: adopting optimized offset for the carrier wave after phase shifting;
the optimal value of the offset is selected as follows: the output voltage u of the ith unit of any phase in the active power filters a, b and c can be obtained by a double Fourier transform formulaiAfter double fourier expansion:
Figure 337385DEST_PATH_IMAGE002
in the formula, MiIs the modulation ratio of the ith H-bridge unit of the phase; edciIs the DC side voltage of the ith cell of the phase of the H-bridge; omegasIs the angular frequency of the modulated wave; omegacIs the angular frequency of the triangular carrier; j. the design is a squarenIs a Bessel function; m is the fundamental wave modulation ratio; m is the carrier harmonic frequency, m is more than or equal to 1 and is an integer; n is sideband harmonic frequency, and n is an odd number;
harmonic current output on corresponding phase of active power filter
Figure 218753DEST_PATH_IMAGE003
Is composed of
Figure 590960DEST_PATH_IMAGE004
In the formula (I), the compound is shown in the specification,
Figure 241384DEST_PATH_IMAGE005
is the harmonic current amplitude;
Figure 290111DEST_PATH_IMAGE006
is the harmonic current phase angle;
Figure 32677DEST_PATH_IMAGE007
is the harmonic current angular frequency;
correspondingly, the coupling power of the ith H-bridge unit corresponding to the phase is obtained by multiplying the harmonic current and the harmonic voltage flowing through the phase
Figure 333209DEST_PATH_IMAGE008
In the formula (I), the compound is shown in the specification,
Figure 713505DEST_PATH_IMAGE009
for the ith cell corresponding to the harmonic current
Figure 808500DEST_PATH_IMAGE003
The generated coupling power;
Figure 54674DEST_PATH_IMAGE010
is carrier offset
Figure 627738DEST_PATH_IMAGE011
Intermediate angular frequency of output voltage of the ith unit
Figure 518333DEST_PATH_IMAGE012
A harmonic component of (a);
Figure 158131DEST_PATH_IMAGE003
the output harmonic current;
Figure 501388DEST_PATH_IMAGE007
is the harmonic current angular frequency; m is the carrier harmonic frequency, m is more than or equal to 1 and is an integer;
Figure 268355DEST_PATH_IMAGE011
is the carrier offset;
Figure 13457DEST_PATH_IMAGE005
is the harmonic current amplitude; edciIs the DC side voltage of the ith cell of the phase of the H-bridge; m is the fundamental wave modulation ratio;
Figure 450255DEST_PATH_IMAGE006
is the harmonic current phase angle;
coupled power
Figure 156174DEST_PATH_IMAGE009
Integrating to obtain the energy exchange amount of the DC side capacitor
Figure 336620DEST_PATH_IMAGE013
In the formula (I), the compound is shown in the specification,
Figure 936228DEST_PATH_IMAGE014
for the ith cell corresponding to the harmonic current
Figure 934140DEST_PATH_IMAGE015
The generated energy of the direct current side capacitor fluctuates;
Figure 986410DEST_PATH_IMAGE016
for the ith cell corresponding to the harmonic current
Figure 970546DEST_PATH_IMAGE015
The generated coupling power;
Figure 798563DEST_PATH_IMAGE005
is the harmonic current amplitude; edciIs the DC side voltage of the ith cell of the phase of the H-bridge; m is the fundamental wave modulation ratio; m is the carrier harmonic frequency, m is more than or equal to 1 and is an integer;
Figure 842742DEST_PATH_IMAGE017
is the harmonic current angular frequency;
Figure 506942DEST_PATH_IMAGE018
is the carrier offset;
Figure 294769DEST_PATH_IMAGE019
is the harmonic current phase angle;
the energy fluctuation of the direct current side capacitor of the active power filter corresponding to a certain harmonic current frequency is obtained by the above formula
Figure 603391DEST_PATH_IMAGE020
Offset from carrier
Figure 693838DEST_PATH_IMAGE021
The relationship of (1);
the harmonic current in actual operation contains a plurality of frequency components, and energy fluctuation generated by each subharmonic frequency component is added to obtain the fluctuation amount of the total energy of the unit
Figure 455120DEST_PATH_IMAGE022
Adding the total energy fluctuations of N units to obtain the total energy fluctuation of a single phase
Figure 46638DEST_PATH_IMAGE023
：
Figure 334400DEST_PATH_IMAGE024
In the formula (I), the compound is shown in the specification,
Figure 720382DEST_PATH_IMAGE023
total energy fluctuation for a single phase; n is the number of single-phase cascade modules;
Figure 500120DEST_PATH_IMAGE022
the energy of the capacitor at the direct current side of the ith unit fluctuates;
thereby obtaining total energy fluctuation
Figure 738072DEST_PATH_IMAGE023
And carrier offset
Figure 631072DEST_PATH_IMAGE025
In relation to (1) in
Figure 578169DEST_PATH_IMAGE023
Obtaining the carrier offset of the system at the minimum
Figure 314044DEST_PATH_IMAGE025
The optimum value of (d);
s3: and carrying out alternate operation on each optimized unit carrier wave in each power frequency period.
3. The method for modulating an H-bridge cascaded active power filter according to claim 1, wherein: due to side band harmonics
Figure 90107DEST_PATH_IMAGE026
N in the series is an odd number and m is an integer greater than or equal to 1, so that the interval between adjacent sideband harmonics near a certain carrier harmonic is 100Hz, and in order to prevent the offset sideband harmonic voltage from coinciding with the adjacent harmonic current again, precondition constraint is carried out on the optimized offset:
Figure 493407DEST_PATH_IMAGE027
in the formula (I), the compound is shown in the specification,
Figure 221192DEST_PATH_IMAGE028
is the carrier offset.
CN202010416828.0A 2020-05-18 2020-05-18 Modulation method of H-bridge cascaded active power filter Pending CN111342475A (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
CN202010416828.0A CN111342475A (en) 2020-05-18 2020-05-18 Modulation method of H-bridge cascaded active power filter

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
CN202010416828.0A CN111342475A (en) 2020-05-18 2020-05-18 Modulation method of H-bridge cascaded active power filter

Publications (1)

Publication Number Publication Date
CN111342475A true CN111342475A (en) 2020-06-26

Family

ID=71187552

Family Applications (1)

Application Number Title Priority Date Filing Date
CN202010416828.0A Pending CN111342475A (en) 2020-05-18 2020-05-18 Modulation method of H-bridge cascaded active power filter

Country Status (1)

Country Link
CN (1) CN111342475A (en)

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113629730A (en) * 2021-07-29 2021-11-09 西南交通大学 Harmonic power adjustment-based low-frequency oscillation suppression method for high-speed rail car network coupling system
CN114785101A (en) * 2022-04-27 2022-07-22 四川大学 Harmonic group online suppression method and system of single-phase cascade H-bridge converter

Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107425545A (en) * 2017-07-31 2017-12-01 上海交通大学 The optimization modulator approach of volage current transformer in cascaded H-bridges
CN108599609A (en) * 2018-05-14 2018-09-28 合肥博鳌电气科技有限公司 A kind of improvement phase-shifting carrier wave modulator approach based on three module-cascade H bridges
CN108683350A (en) * 2018-05-25 2018-10-19 西安理工大学 A kind of three level NPC converter particular harmonics optimization modulation strategy
US20190115840A1 (en) * 2017-10-16 2019-04-18 The Florida State University Research Foundation, Modulation method for dc to dc converters
CN110048426A (en) * 2019-05-13 2019-07-23 南方电网科学研究院有限责任公司 A kind of VSC Harmonic Modeling method based on PWM modulation principle

Patent Citations (5)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN107425545A (en) * 2017-07-31 2017-12-01 上海交通大学 The optimization modulator approach of volage current transformer in cascaded H-bridges
US20190115840A1 (en) * 2017-10-16 2019-04-18 The Florida State University Research Foundation, Modulation method for dc to dc converters
CN108599609A (en) * 2018-05-14 2018-09-28 合肥博鳌电气科技有限公司 A kind of improvement phase-shifting carrier wave modulator approach based on three module-cascade H bridges
CN108683350A (en) * 2018-05-25 2018-10-19 西安理工大学 A kind of three level NPC converter particular harmonics optimization modulation strategy
CN110048426A (en) * 2019-05-13 2019-07-23 南方电网科学研究院有限责任公司 A kind of VSC Harmonic Modeling method based on PWM modulation principle

Non-Patent Citations (4)

* Cited by examiner, † Cited by third party
Title
戴珂等: "载波轮换调制在级联H桥STATCOM中的应用", 《中国电机工程学报》 *
杨擎: "H桥级联型STATCOM直流侧电压平衡策略研究", 《中国优秀硕士学位论文全文数据库 工程科技Ⅱ辑（月刊）》 *
杨泽洲等: "基于载波频率优化的级联型APF源性谐波能量不均抑制方法", 《高电压技术》 *
胡锦超: "新型通用多电平电压源变换器拓扑及其调制策略研究", 《中国优秀硕士学位论文全文数据库 工程科技Ⅱ辑（月刊）》 *

Cited By (2)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN113629730A (en) * 2021-07-29 2021-11-09 西南交通大学 Harmonic power adjustment-based low-frequency oscillation suppression method for high-speed rail car network coupling system
CN114785101A (en) * 2022-04-27 2022-07-22 四川大学 Harmonic group online suppression method and system of single-phase cascade H-bridge converter

Similar Documents

Publication Publication Date Title
CN109067193B (en) Cascade power electronic transformer and unbalance compensation control method thereof
CN106849135B (en) The power/current quality Synergistic method of microgrid inverter and active filter
CN109494995B (en) Neutral point potential balance control method suitable for VIENNA rectifier
CN111342475A (en) Modulation method of H-bridge cascaded active power filter
Ren et al. Coupling effect analysis and design principle of repetitive control based hybrid controller for SVG with enhanced harmonic current mitigation
Sarker et al. An optimized co-ordinated approach for harmonic minimization of Doubly Fed Induction Generator connected micro-grid system
CN104393609B (en) Static Synchronous generator failure traversing control method
CN109802434B (en) Grid-connected current balance control system of three-phase cascade photovoltaic inverter
CN110649619A (en) Modular multilevel active power filter sliding mode control method
CN113629763A (en) Current control method and system for medium-voltage direct-hanging energy storage converter under non-ideal power grid
CN109193692B (en) Chained SVG and method and device for controlling capacitor voltage balance on direct current side thereof
Li et al. Adaptive harmonic power flow algorithm for hybrid AC/DC transmission systems
Khramshin et al. A Novel Fundamental Frequency Modulation Strategy for Cascaded Multilevel STATCOM with Non-sinusoidal Load Currents
Xue et al. Capacitor voltage balancing control strategy for single-phase five-level ANPC photovoltaic inverter
CN110912130A (en) Circuit structure of double-alternating-current bus grid-connected converter and harmonic compensation method thereof
Song et al. An improved fuzzy voltage compensation control strategy for parallel inverter
Chen et al. Improved Dual-Mode Repetitive Control for Grid-Connected Inverters
CN108123455A (en) A kind of Novel chain type static synchronous compensator control method
Wang et al. Fast-transient repetitive controller based current control strategy for a cascaded DSTATCOM
Zhao et al. Operation of series and shunt converters with 48-pulse series connected three-level NPC converter for UPFC
Yang et al. A new cascaded multilevel converter topology with energy exchange unit for STATCOM application
Liu et al. Modulation of three-level T-type inverter supplied by series battery banks at different SOC condition
Han et al. A Splitting Modulation Strategy for Arm Multiplexing Modular Multilevel Converter
Song et al. An Modulation Method for Improving Output Characteristics of Medium-/Low-Voltage MMCs
Tekki et al. Ancillary Services Prioritization in Inverters with Virtual Synchronous Generator Functionalities

Legal Events

Date Code Title Description
PB01 Publication
PB01 Publication
SE01 Entry into force of request for substantive examination
SE01 Entry into force of request for substantive examination
RJ01 Rejection of invention patent application after publication
RJ01 Rejection of invention patent application after publication

Application publication date: 20200626