CN110719021A - Grid-connected three-phase inverter common-mode EMI filter optimization design method - Google Patents

Grid-connected three-phase inverter common-mode EMI filter optimization design method Download PDF

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CN110719021A
CN110719021A CN201911054800.0A CN201911054800A CN110719021A CN 110719021 A CN110719021 A CN 110719021A CN 201911054800 A CN201911054800 A CN 201911054800A CN 110719021 A CN110719021 A CN 110719021A
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common
grid
mode
mode emi
phase inverter
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CN110719021B (en
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李虹
丁宇航
杨志昌
张波
邵天骢
李志君
郑琼林
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Beijing Jiaotong University
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/44—Circuits or arrangements for compensating for electromagnetic interference in converters or inverters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/12—Arrangements for reducing harmonics from ac input or output
    • H02M1/123—Suppression of common mode voltage or current

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Abstract

The invention discloses an optimal design method of a grid-connected three-phase inverter common-mode EMI filter, which comprises the following steps: chaotic SPWM modulation is used in a grid-connected three-phase inverter, and a common-mode EMI frequency spectrum required to be attenuated by a converter is obtained through a linear stable impedance network; analyzing a common-mode EMI passage of the grid-connected three-phase inverter to obtain a Thevenin or Nonton equivalent circuit, and obtaining an insertion loss curve of the common-mode EMI filter according to the equivalent circuit; and obtaining the required inductance value and the required capacitance value according to the parameters of the tangent point of the insertion loss curve and the common-mode EMI frequency spectrum and the frequency folding expression of the common-mode EMI filter. Compared with a grid-connected three-phase inverter modulated by fixed-frequency SPWM, the method can improve the turning frequency of the required common-mode EMI filter, thereby reducing the required inductance and capacitance values, reducing the volume, weight and cost of the common-mode EMI filter, and improving the power density of the grid-connected three-phase inverter.

Description

Grid-connected three-phase inverter common-mode EMI filter optimization design method
Technical Field
The invention relates to the technical field of power electronics, in particular to an optimal design method of a grid-connected three-phase inverter common-mode EMI filter.
Background
With the intensive research on renewable energy power generation technologies such as solar photovoltaic power generation and wind power generation, distributed power generation becomes an important link of power grid power supply, wherein a grid-connected three-phase inverter is widely concerned as an important device for electric energy conversion, and the three-phase inverter has better high-frequency harmonic suppression and smaller inductance volume and becomes a hotspot of research. Although three-phase inverters have many advantages, power electronic devices share electromagnetic interference problems, wherein common-mode EMI problems are particularly prominent, and in order to prevent the common-mode EMI filters from influencing normal operation of the power electronic devices and other devices and ensure stable operation of the power electronic devices, the common-mode EMI filters are generally required to be additionally installed. The addition of the common-mode EMI filter increases the volume, weight and cost of equipment, reduces the power density and is not beneficial to the wide popularization of the inverter.
In the related art, methods for reducing the size of the common-mode EMI filter mainly include reducing a device-to-ground parasitic parameter, reducing an element coupling parameter, optimizing a PCB layout, and the like, but these methods are complicated, sometimes require a relatively accurate high-frequency circuit model, and are not convenient to use in engineering practice, and meanwhile, research on optimizing the common-mode EMI filter in a grid-connected three-phase inverter is less.
Disclosure of Invention
The present invention is directed to solving, at least to some extent, one of the technical problems in the related art.
Therefore, the invention aims to provide an optimal design method of a common-mode EMI filter of a grid-connected three-phase inverter, which can effectively reduce the volume, weight and cost of the common-mode EMI filter and is convenient to operate and implement.
In order to achieve the above purpose, an embodiment of the present invention provides an optimal design method for a grid-connected three-phase inverter common-mode EMI filter, including the following steps: chaotic SPWM modulation is used in a grid-connected three-phase inverter, and a common-mode EMI frequency spectrum required to be attenuated by a converter is obtained through a linear stable impedance network; analyzing a common-mode EMI passage of the grid-connected three-phase inverter to obtain a Thevenin or Nonton equivalent circuit, and obtaining an insertion loss curve of a common-mode EMI filter according to the equivalent circuit; and obtaining a required inductance value and a required capacitance value according to the parameters of the tangent point of the insertion loss curve and the common-mode EMI frequency spectrum and the frequency folding expression of the common-mode EMI filter.
Compared with the traditional fixed-frequency SPWM modulation, the grid-connected three-phase inverter common-mode EMI filter optimization design method provided by the embodiment of the invention has the advantages that the original EMI frequency spectrum amplitude is reduced due to the frequency spreading of the chaotic SPWM, namely the EMI amplitude needing to be suppressed is reduced, so that the turning frequency of the common-mode EMI filter is improved, the common-mode inductance or common-mode capacitance is reduced, the volume of the common-mode inductance is reduced, the weight and the cost are reduced when the volume of the common-mode EMI filter is reduced under the same material, the result of optimizing the EMI filter is achieved, and the problems of equipment power density reduction, weight increase and cost increase caused by the large volume of the common-mode.
In addition, the grid-connected three-phase inverter common-mode EMI filter optimization design method according to the above embodiment of the present invention may further have the following additional technical features:
further, in an embodiment of the present invention, the method further includes: and estimating the volumes of the inductor and the capacitor according to the required inductance value and the required capacitance value.
Further, in one embodiment of the present invention, the common mode EMI is obtained by the following formula:
Figure BDA0002256264730000021
wherein v isNIs the value of the voltage, v, measured on-line on N in the LISNLIs L on line in LISNThe measured voltage value;
the EMI magnitude of the desired attenuation is expressed as:
Areq＝Aori-Astandard+6dB，
wherein A isreqIs the magnitude of EMI to be attenuated, AoriIs the raw EMI amplitude, A, measured on the LISNstandardRepresenting the EMI standard amplitude of CISPR 22Class A, 6dB is the design margin.
Further, in one embodiment of the present invention, the insertion loss curve is expressed by:
Figure BDA0002256264730000022
wherein Z isCyRepresenting common-mode capacitance, RCMIs an LISN equivalent common mode test resistance, (R)CM+ZCM)//ZCyIs represented by (R)CM+ZCM) And ZCyParallel calculation of its value, ZsRepresenting the equivalent source impedance.
Further, in an embodiment of the present invention, the relationship between the inductance value and the inductance volume is as follows:
Figure BDA0002256264730000023
wherein L is inductance, N is number of turns of wire, ALIs the inductance, μ is the core permeability, h is the core thickness, d1Is the inner diameter of the magnet ring d2Is the outer diameter of the magnet ring d0Is the winding diameter and V is the inductor volume.
Additional aspects and advantages of the invention will be set forth in part in the description which follows and, in part, will be obvious from the description, or may be learned by practice of the invention.
Drawings
The foregoing and/or additional aspects and advantages of the present invention will become apparent and readily appreciated from the following description of the embodiments, taken in conjunction with the accompanying drawings of which:
fig. 1 is a flowchart of a common-mode EMI filter optimization design method of a grid-connected three-phase inverter according to an embodiment of the invention;
fig. 2 is a schematic structural diagram of a grid-connected three-phase inverter according to an embodiment of the invention;
FIG. 3 is a topology of a common mode EMI filter according to an embodiment of the invention;
FIG. 4 is a schematic diagram of an original common-mode EMI spectrum of a grid-connected three-phase inverter under chaotic SPWM according to an embodiment of the present invention;
FIG. 5 is a schematic diagram of a common mode EMI spectrum after adding a common mode EMI filter under chaotic SPWM according to an embodiment of the present invention;
FIG. 6 is a schematic diagram of a CISPR 22CLASS A standard according to an embodiment of the present invention;
FIG. 7 is a schematic diagram of the original common mode EMI spectrum of a grid-connected three-phase inverter under fixed-frequency SPWM according to an embodiment of the present invention;
FIG. 8 is a schematic diagram of the common mode EMI spectrum after adding a common mode EMI filter under a fixed frequency SPWM according to an embodiment of the present invention;
fig. 9 is a schematic diagram of common mode EMI paths of a grid-connected three-phase inverter according to an embodiment of the invention;
fig. 10 is a schematic diagram of a thevenin equivalent circuit of a common-mode path of a grid-connected three-phase inverter according to an embodiment of the invention;
FIG. 11 is a graph illustrating common mode insertion loss curves obtained after adding a common mode EMI filter according to an embodiment of the present invention;
FIG. 12 is a graph illustrating a corner frequency solution according to an insertion loss curve and an EMI spectrum to be attenuated according to an embodiment of the present invention;
FIG. 13 is a graph comparing the common mode inductance volume under constant frequency SPWM and chaotic SPWM according to the present invention.
Detailed Description
Reference will now be made in detail to embodiments of the present invention, examples of which are illustrated in the accompanying drawings, wherein like or similar reference numerals refer to the same or similar elements or elements having the same or similar function throughout. The embodiments described below with reference to the drawings are illustrative and intended to be illustrative of the invention and are not to be construed as limiting the invention.
The method for optimally designing the grid-connected three-phase inverter common-mode EMI filter provided by the embodiment of the invention is described below with reference to the attached drawings.
Fig. 1 is a flowchart of a common-mode EMI filter optimization design method for a grid-connected three-phase inverter according to an embodiment of the present invention.
As shown in fig. 1, the method for optimally designing the grid-connected three-phase inverter common-mode EMI filter includes the following steps:
in step S101, chaotic SPWM modulation is used in the grid-connected three-phase inverter, and the common-mode EMI spectrum to be attenuated by the converter is obtained through the linear stable impedance network.
It can be understood that, in the grid-connected three-phase inverter shown in fig. 2, the chaotic SPWM modulation is used, and at the same time, a linear stable impedance network (LISN) is used to obtain the common-mode EMI spectrum to be attenuated by the converter, and the method for optimizing the common-mode EMI filter by using the chaotic SPWM modulation with the characteristic of spread spectrum is easy to operate and implement. The topology of the common mode EMI filter is shown in fig. 3. The circuit parameters of the grid-connected three-phase inverter are shown in table 1.
TABLE 1
Parameter(s) Numerical value Parameter(s) Numerical value
Input voltage Vdc 750V direct current Cd 750uF
Output voltage Three-phase 380V alternating current RN/RL 50Ω
Fixed frequency switching frequency Fr 10kHz L1 1mH
Spread spectrum switching frequency f 90kHz-110kHz L2 0.12mH
C 10uF C1 0.1uF
Specifically, chaotic SPWM modulation is used in a grid-connected three-phase inverter; each cycle of the carrier wave changes according to a chaotic sequence:
fci＝Fr+d·xi·Fr，
wherein f isciIs the ith chaotic modulating wave frequency, FrIs the switching frequency under fixed frequency SPWM, d is the spreading width, xiIs the ith chaotic sequence value.
Further measuring common-mode EMI of the equipment by using the LISN, and obtaining an EMI frequency spectrum needing to be attenuated according to an electromagnetic compatibility standard and considering a design allowance;
wherein the common mode EMI can be obtained by the following formula:
Figure BDA0002256264730000041
wherein v isNIs the value of the voltage, v, measured on-line on N in the LISNLIs the voltage value measured on the L line in the LISN.
The magnitude of EMI that needs to be attenuated can be represented by the following equation:
Areq＝Aori-Astandard+6dB，
wherein A isreqIs the magnitude of EMI to be attenuated, AoriThe raw EMI amplitudes measured on the LISN are shown in FIG. 4, AstandardThe EMI standard amplitude representing CISPR 22Class A is shown in FIG. 5, and 6dB is the design margin, where the CISPR 22Class A standard is shown in FIG. 6. In addition, when the grid-connected three-phase inverter is modulated by using the fixed-frequency SPWM in the prior art, the original common-mode EMI spectrum of the grid-connected three-phase inverter under the fixed-frequency SPWM is shown in fig. 7, and the common-mode EMI spectrum after adding the common-mode EMI filter under the fixed-frequency SPWM is shown in fig. 8.
In step S102, a common-mode EMI path of the grid-connected three-phase inverter is analyzed to obtain a davinan or norton equivalent circuit, and an insertion loss curve of the common-mode EMI filter is obtained according to the equivalent circuit.
It can be understood that the grid-connected three-phase inverter common mode EMI path shown in fig. 9 is analyzed to obtain the thevenin or norton equivalent circuit thereof, and the insertion loss curve of the common mode EMI filter can be obtained according to the equivalent circuit, wherein the thevenin equivalent circuit of the grid-connected three-phase inverter common mode path is shown in fig. 10, and the common mode insertion loss curve obtained by adding the common mode EMI filter is shown in fig. 11.
Specifically, the insertion loss curve expression of the common-mode EMI filter is:
Figure BDA0002256264730000051
wherein ZCyRepresenting common-mode capacitance, RCMIs an LISN equivalent common mode test resistance, (R)CM+ZCM)//ZCyIs represented by (R)CM+ZCM) And ZCyParallel calculation of its value, ZsThe equivalent source impedance is expressed, which in the embodiment of the present invention can be expressed as:
Figure BDA0002256264730000052
wherein
Figure BDA0002256264730000053
Represents the equivalent parasitic capacitance of the point to the ground in the three-phase bridge arm,
Figure BDA0002256264730000054
the inductance value near the converter side in the LCL filtering is represented,
Figure BDA0002256264730000055
representing the inductance of the LCL filter on the side close to the network,
Figure BDA0002256264730000056
representing capacitive reactance, R, in the LCLCRepresenting the impedance between the neutral point of the grid and earth.
In step S103, a required inductance value and a required capacitance value are obtained according to the parameters of the tangent point of the insertion loss curve and the common mode EMI spectrum and the folding frequency expression of the common mode EMI filter.
Specifically, as shown in fig. 12, values of the common mode inductance and the common mode capacitance are obtained according to a tangent point of the insertion loss and the EMI spectrum to be attenuated and a transition frequency expression of the common mode EMI filter, where the transition frequency of the EMI filter is as follows:
Figure BDA0002256264730000057
wherein f istIs the frequency value of the tangent point, AtIs the EMI amplitude of the tangent point, frIs the intersection of the insertion loss curve at the tangent point with the frequency axis.
Further, in an embodiment of the present invention, the method further includes: the volumes of the inductors and capacitors are estimated based on the desired inductance values and the desired capacitance values.
It can be understood that, finally, the volumes of the inductor and the capacitor are estimated according to the inductance value or the capacitance value, as shown in fig. 13, compared with a grid-connected three-phase inverter using fixed-frequency SPWM modulation, the embodiment of the present invention can reduce the weight and the cost of the common-mode EMI filter while reducing the volume of the common-mode EMI filter.
Specifically, in the embodiment of the present invention, the common mode capacitance value is kept constant, the volume change of the common mode inductor is compared, and the inductance value and the inductor volume are linked:
Figure BDA0002256264730000061
in the embodiment of the invention, a ring inductor is used, wherein L is inductance value, N is winding turns, and ALIs the inductance, μ is the core permeability, h is the core thickness, d1Is the inner diameter of the magnet ring d2Is the outer diameter of the magnet ring d0Is the winding diameter and V is the inductor volume.
In the embodiment of the invention, d can be obtained according to the current magnitude02mm, further according to the frequency impedance characteristic of the magnetic ring in the Mn-Zn HF90 series, selecting proper magnetic ring parameters as shown in Table 2, wherein the required magnetic ring volume is about V under the fixed frequency SPWM1＝3126.9mm3The volume of the common mode inductor is about V under the chaotic SPWM2＝2146.7mm3It can be seen that using chaotic SPWM, the volume of the common mode inductor is reduced by about 31.35%. Table 2 is a parameter comparison table of common mode inductance under the fixed frequency SPWM and the chaotic SPWM.
TABLE 2
d0/mm d1/mm d2/mm h/mm V/mm3
Fixed frequency SPWM 2 19 31 13 3126.9
Chaotic SPWM 2 15 25 13 2146.7
Percent reduction — 21.05％ 19.35％ — 31.35％
In summary, the embodiment of the invention uses chaotic SPWM modulation and measures electromagnetic interference in a grid-connected three-phase inverter; on the basis of a common-mode EMI filter design method, the turning frequency of the required common-mode EMI filter is calculated according to the measured electromagnetic interference; and calculating the required inductance and capacitance values according to the required common-mode EMI filter breakover frequency. Compared with a grid-connected three-phase inverter modulated by fixed-frequency SPWM, the method provided by the embodiment of the invention can improve the turning frequency of the required common-mode EMI filter, thereby reducing the required inductance and capacitance value, reducing the volume, weight and cost of the common-mode EMI filter, and improving the power density of the grid-connected three-phase inverter.
According to the grid-connected three-phase inverter common-mode EMI filter optimization design method provided by the embodiment of the invention, compared with the traditional fixed-frequency SPWM modulation, due to the fact that the original EMI frequency spectrum amplitude is reduced due to the frequency spreading of the chaotic SPWM, namely the EMI amplitude needing to be suppressed is reduced, the turning frequency of the common-mode EMI filter is improved, the common-mode inductance or the common-mode capacitance is reduced, the volume of the common-mode inductance is reduced, the weight and the cost are reduced when the volume of the common-mode EMI filter is reduced under the same material, the result of optimizing the EMI filter is achieved, and the problems of reduction of the power density of equipment, increase of the weight and increase of the cost caused by.
Furthermore, the terms "first", "second" and "first" are used for descriptive purposes only and are not to be construed as indicating or implying relative importance or implicitly indicating the number of technical features indicated. Thus, a feature defined as "first" or "second" may explicitly or implicitly include at least one such feature. In the description of the present invention, "a plurality" means at least two, e.g., two, three, etc., unless specifically limited otherwise.
In the description herein, references to the description of the term "one embodiment," "some embodiments," "an example," "a specific example," or "some examples," etc., mean that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the invention. In this specification, the schematic representations of the terms used above are not necessarily intended to refer to the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples. Furthermore, various embodiments or examples and features of different embodiments or examples described in this specification can be combined and combined by one skilled in the art without contradiction.
Although embodiments of the present invention have been shown and described above, it is understood that the above embodiments are exemplary and should not be construed as limiting the present invention, and that variations, modifications, substitutions and alterations can be made to the above embodiments by those of ordinary skill in the art within the scope of the present invention.

Claims (5)

1. The grid-connected three-phase inverter common-mode EMI filter optimization design method is characterized by comprising the following steps:
chaotic SPWM modulation is used in a grid-connected three-phase inverter, and a common-mode EMI frequency spectrum required to be attenuated by a converter is obtained through a linear stable impedance network;
analyzing a common-mode EMI passage of the grid-connected three-phase inverter to obtain a Thevenin or Nonton equivalent circuit, and obtaining an insertion loss curve of a common-mode EMI filter according to the equivalent circuit;
and obtaining a required inductance value and a required capacitance value according to the parameters of the tangent point of the insertion loss curve and the common-mode EMI frequency spectrum and the frequency folding expression of the common-mode EMI filter.
2. The method of claim 1, further comprising:
and estimating the volumes of the inductor and the capacitor according to the required inductance value and the required capacitance value.
3. The method of claim 1, wherein the common mode EMI is derived by the following equation:
wherein v isNIs the value of the voltage, v, measured on-line on N in the LISNLIs the voltage value measured on the upper line of L in the LISN;
the EMI magnitude of the desired attenuation is expressed as:
Areq＝Aori-Astandard+6dB，
wherein A isreqIs the magnitude of EMI to be attenuated, AoriIs the raw EMI amplitude, A, measured on the LISNstandardRepresenting the EMI standard amplitude of CISPR 22Class A, 6dB is the design margin.
4. The method of claim 1, wherein the insertion loss curve is expressed by:
Figure FDA0002256264720000012
wherein Z isCyRepresenting common-mode capacitance, RCMIs an LISN equivalent common mode test resistance, (R)CM+ZCM)//ZCyIs represented by (R)CM+ZCM) And ZCyParallel calculation of its value, ZsRepresenting the equivalent source impedance.
5. The method of claim 2, wherein the inductance value is related to the volume of the inductor by the equation:
Figure FDA0002256264720000021
wherein L is inductance, N is number of turns of wire, ALIs the inductance, μ is the core permeability, h is the core thickness, d1Is the inner diameter of the magnet ring d2Is the outer diameter of the magnet ring d0Is the winding diameter and V is the inductor volume.
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