CN110504852B

CN110504852B - Single-phase soft switch charger topology with voltage decoupling function and modulation method thereof

Info

Publication number: CN110504852B
Application number: CN201910867754.XA
Authority: CN
Inventors: 胡长生; 徐德鸿; 王睿哲; 张军明; 梅营; 金佑燮
Original assignee: Zhejiang University ZJU; LG Electronics Shanghai Research and Development Center Co Ltd
Current assignee: Zhejiang University ZJU; LG Electronics Shanghai Research and Development Center Co Ltd
Priority date: 2019-09-14
Filing date: 2019-09-14
Publication date: 2021-01-05
Anticipated expiration: 2039-09-14
Also published as: CN110504852A

Abstract

The invention discloses a single-phase soft switching charger topology with active voltage decoupling and a modulation method thereof, wherein the topology comprises a power grid side unit power factor PWM (pulse-width modulation) rectifying circuit, a full-bridge phase-shift control DC/DC (direct current/direct current) converting circuit, an active direct current voltage decoupling circuit and a resonance branch circuit for realizing zero voltage soft switching of all switching tubes, and through the control of the active direct current voltage decoupling circuit, the capacitance capacity of a direct current bus is greatly reduced, and the power density of the charger is improved; the modulation mode comprises a PWM (pulse-width modulation) rectification circuit, a DC/DC (direct current/direct current) conversion circuit, an active direct current voltage decoupling circuit and a soft switching modulation method of a resonance branch circuit, and particularly synchronizes control signals of a bridge arm switching device of the PWM rectification circuit, control signals of the active direct current voltage decoupling circuit switching device and the rising edge of the control signals of the DC/DC conversion bridge arm switching device, realizes zero voltage switching-on of all switches in a switching period through the control of the resonance branch circuit, and improves the conversion efficiency of topology.

Description

Single-phase soft switch charger topology with voltage decoupling function and modulation method thereof

Technical Field

The invention relates to the technical field of converter modulation, in particular to a single-phase zero-voltage soft switch charger topology with active power decoupling and a modulation method thereof.

Background

In a conventional vehicle-mounted charger circuit composed of two stages of electric energy conversion circuits, because the characteristic of a PFC module at the front stage is to eliminate double power frequency ripples on a direct current bus between two stages, a large-capacity capacitor needs to be connected in parallel on the direct current bus, and the power density of the vehicle-mounted charger is low. Although the capacitance capacity of a capacitor on a direct current bus can be reduced by the conventional voltage decoupling circuit, the volume of a passive device introduced into the voltage decoupling circuit is large due to the fact that a switching device of the voltage decoupling circuit works in a hard switching mode, and therefore the conversion efficiency of the vehicle-mounted charger is low and the power density is not obviously improved. Therefore, the conventional single-phase charger topology with voltage decoupling works in a hard switching mode, and the problems that the volume of a passive device in a voltage decoupling circuit is large, the overall power density cannot be greatly improved, the conversion efficiency is low and the like exist.

Disclosure of Invention

The invention aims to overcome the defects in the existing charger topology, provides a single-phase zero-voltage soft switch charger topology with voltage decoupling and a modulation mode thereof, realizes the great reduction of the capacitance capacity of a direct current bus, and simultaneously realizes that a switching tube of a unit power factor PWM (pulse width modulation) rectification circuit, a switching tube of a phase-shift control DC/DC circuit, a switching tube of a voltage decoupling circuit and a switching tube of an auxiliary soft switch resonant circuit work in a zero-voltage switching-on mode, thereby improving the conversion efficiency and the power density of the charger.

In one aspect of the present invention, a single-phase soft-switching charger topology with active voltage decoupling is provided, as shown in fig. 1, and is characterized in that: the single-phase soft switching charger circuit with the source voltage decoupling function comprises four groups of bridge arms and a direct-current bus voltage decoupling branch, wherein the four groups of bridge arms are formed by two series-connected fully-controlled switches comprising anti-parallel diodes, and the direct-current bus voltage decoupling branch is formed. Wherein: the upper and lower switches and the anti-parallel diodes of the first bridge arm are respectively S_r1、D_r1And S_r3、D_r3The upper and lower switches and their anti-parallel diodes of the second bridge arm are respectively S_r2、D_r2And S_r4、D_r4The upper and lower switches and their anti-parallel diodes of the third bridge arm are respectively S_i1、D_i1And S_i3、D_i3Of 1 atThe upper and lower switches and the anti-parallel diodes of the four bridge arms are respectively S_i2、D_i2And S_i4、D_i4. The auxiliary switch of the resonance branch and the anti-parallel diode are S respectively_aux、D_auxThe resonance branch circuit also comprises a resonance inductor L_rAnd a clamp capacitor C_c. The direct current bus voltage decoupling circuit comprises a bridge arm and an inductor L which are formed by a group of two series-connected fully-controlled switches containing anti-parallel diodes_pdAnd an energy storage capacitor C_pdThe upper and lower switching devices and the anti-parallel diodes of the bridge arm are respectively S_d1、D_d1And S_d2、D_d2。

The drains of the switching devices on the first and second groups of bridge arms and the source of the lower switching device are respectively connected to the direct current positive bus and the negative bus, the middle points of the bridge arms are respectively connected with an alternating current power grid through an input filter circuit, and the unit power factor of the power grid current is realized in a PWM (pulse-width modulation) rectification mode. The drains of the upper switching devices and the source of the lower switching device of the third bridge arm and the fourth bridge arm are respectively connected to the direct current positive bus and the direct current negative bus, and the middle points of the bridge arms pass through a resonant leakage inductance L_kAnd the phase-shifting control circuit is connected with a primary side winding of the transformer and realizes DC/DC conversion according to phase-shifting control. The drain electrode of the switching device on the bridge arm and the source electrode of the lower switching device in the direct current bus voltage decoupling branch are also respectively connected to the direct current positive bus and the direct current negative bus, and the midpoint of the bridge arm passes through an inductor L_pdIs connected to an energy storage capacitor C_pdControlling the energy storage capacitor C by PWM_pdThe voltage decoupling of the direct current bus is realized by charging and discharging, and double power frequency ripples on the direct current bus are eliminated. Auxiliary switch and clamping capacitor C for resonance branch route_cConnected in series and then connected with a resonant inductor L_rOne end of the resonance branch is connected with the DC bus capacitor C in parallel_dcOne end of the positive electrode is connected with a positive bus, and a direct current bus capacitor C_dcThe negative pole of the direct current bus is connected with the negative bus of the direct current bus, and the switching devices of the first, second, third and fourth groups of bridge arms, the auxiliary switches on the resonance branch, the direct current bus voltage decoupling circuit and the switching devices in the resonance branch all work in a zero current switching-on mode by controlling the switching-off phase and the duty ratio of the switching devices of the resonance branch. Isolation transformer 2The secondary side winding output charges the battery through a rectifier bridge circuit and an output filter circuit.

In another aspect of the present disclosure, a modulation method for matching the topology of the single-phase soft switching charger with active voltage decoupling is provided, as shown in fig. 2, including a rectification modulation wave calculation module, a carrier signal generation module, a phase shift angle calculation module, a decoupling branch switching tube modulation wave calculation module, an auxiliary switching tube modulation wave calculation module, a current sector determination module, a first PWM modulation module, a second PWM modulation module, a third PWM modulation module, a ZVS pulse modulation module, a pulse rising edge synchronization control module, and a PWM pulse superposition modulation module. Main switch S of single-phase zero-voltage soft-switching charger circuit with active voltage decoupling by using above modules_r1～S_r4、S_i1～S_i4、S_d1～S_d2And an auxiliary switch S_auxAnd carrying out zero-voltage switching modulation. The output signals of the rectification modulation wave calculation module and the carrier signal generation module enter a first PWM (pulse-width modulation) module, and the first PWM module is used for generating an original driving signal v of an upper tube and a lower tube of a first bridge arm_sr1、v_sr3And original driving signals v of upper and lower tubes of a second bridge arm_sr2、v_sr4. The output signals of the phase shift angle calculation module and the carrier signal generation module enter a second PWM (pulse-width modulation) module, and the second PWM module is used for generating original control signals v of the third bridge arm switching tube and the fourth bridge arm switching tube_si1、v_si3、v_si2、v_si4. The output signals of the decoupling branch switch tube modulation wave calculation module and the carrier signal generation module enter a third PWM (pulse-width modulation) module, and the third PWM module is used for generating an original control signal v of the power decoupling branch switch tube_sd1、v_sd2. And the pulse rising edge synchronous control module determines the alignment mode of the main switching tube driving pulse rising edges of the first bridge arm and the second bridge arm, the switching tube driving pulse rising edges of the decoupling branch bridge arm and the main switching tube driving pulse rising edges of the third bridge arm and the fourth bridge arm according to the current sector judging module. The output signals of the auxiliary switch tube modulation wave calculation module and the carrier signal generation module enter a ZVS pulse modulation module, and a port 2 of the ZVS pulse modulation moduleIs output signal v_scWith the original control signal v_sr1、v_sr3、v_sr2、v_sr4、v_si1、v_si3、v_si2、v_si4、v_sd1、v_sd2Are input to a PWM pulse superposition modulation module together to generate switching tubes S respectively_r1～S_r4、S_i1～S_i4、S_d1～S_d2Control PWM signal v_{gs_Sr1}～v_{gs_Sr4}、v_{gs_Si1}～v_{gs_Si3}、v_{gs_Sd1}～v_{gs_Sd2}Realize to S_r1～S_r4、S_i1～S_i4、S_d1～S_d2And S_auxSoft switching modulation of zero voltage.

Compared with the prior art, the invention has the following beneficial effects:

according to the invention, zero voltage switching-on in a full working area can be realized by only using one resonance branch circuit, wherein the resonance branch circuit comprises a unit power factor PWM (pulse-width modulation) rectifying circuit, a phase-shifted full-bridge DC/DC circuit, an active power decoupling circuit and all switching tubes on the resonance branch circuit, and the conversion efficiency is high.

In addition, the invention has the additional effects that the switching frequency of the PWM rectifying circuit, the phase-shifted full-bridge DC/DC circuit and the active power decoupling branch circuit is fixed, thereby being beneficial to the optimization of passive devices in topology and improving the power density and the conversion efficiency of the charger.

Drawings

Fig. 1 is a single-phase zero-voltage soft-switching charger circuit with source power decoupling.

Fig. 2 is a generation of a single-phase zero-voltage soft-switching charger circuit modulation method with source power decoupling.

Fig. 3 is a schematic diagram of current sector division.

Fig. 4 shows an internal structure of the first PWM modulation module.

Fig. 5 shows the internal structure of the second PWM modulation module.

Fig. 6 shows the internal structure of the third PWM modulation module.

Fig. 7 shows the internal structure of ZVS (zero voltage) pulse modulation module.

Fig. 8 shows the internal structure of the pulse rising edge synchronous control module.

Fig. 9 shows the internal structure of the PWM pulse superposition modulation module.

Fig. 10 is a schematic diagram of the time when the main switching tube in the circuit needs to realize zero voltage turn-on in a power frequency period (the time of the driving rising edge marked by blue in the figure).

Fig. 11 is a waveform of a modulation signal in a triangular carrier period when a single-phase zero-voltage soft-switching charger circuit with source power decoupling operates in current sector I.

Fig. 12 is a timing diagram of the control of the switching pulses during a triangular carrier cycle when the single-phase zero-voltage soft-switching charger circuit with source power decoupling is operating in current sector I.

Fig. 13 to 29 are equivalent circuits of topology phase operation in one triangular carrier cycle when the single-phase zero-voltage soft-switching charger circuit with source power decoupling operates in the current I-th sector, and the operation conditions of other sectors are similar. Because the work of the rectifier, the active power decoupling branch and the phase-shifted full-bridge DC-DC converter are mutually independent, the duty ratio D of the rectifier_pwmActive power decoupling branch duty ratio D_pdThe phase shift angle values of the phase-shifted full-bridge DC-DC converter are independent, and the phase analysis is carried out by D_pd>(1-)>D_pwmFor example, the phase analysis is similar for other duty cycle relationships.

Fig. 30 shows the main voltage and current waveforms of a single-phase zero-voltage soft-switching charger circuit with source power decoupling during a triangular carrier period when the circuit is operating in the current I-th sector.

Detailed Description

The present invention will be described in detail with reference to the accompanying drawings.

Referring to fig. 1, the single-phase zero-voltage soft-switching vehicle-mounted charger circuit with source power decoupling comprises four sets of bridge arms formed by two series-connected fully-controlled switches including anti-parallel diodes and a direct-current bus voltage decoupling branch. Wherein: the upper and lower switches and the anti-parallel diodes of the first bridge arm are respectively S_r1、D _r14 and S_r3、D _r36, second bridgeThe upper and lower switches and their anti-parallel diodes of the arm are respectively S_r2、D _r25 and S_r4、D _r47, the upper switch, the lower switch and the anti-parallel diode of the third bridge arm are respectively S_i1、D _i116 and S_i3、D _i318, the upper and lower switches and the anti-parallel diodes of the fourth bridge arm are respectively S_i2、D _i217 and S_i4、D _i419. The auxiliary switch of the resonance branch and the anti-parallel diode are S respectively_aux、D _aux8, the resonance branch circuit also comprises a resonance inductor L _r10 and a clamping capacitance C _c9. The direct current bus voltage decoupling branch comprises a bridge arm and an inductor L, wherein the bridge arm and the inductor L are formed by a group of two series-connected fully-controlled switches comprising anti-parallel diodes _pd14 and an energy storage capacitor C _pd15, the upper and lower switching devices of the bridge arm and the anti-parallel diode thereof are S respectively_d1、D _d112 and S_d2、D _d213。

The drains of the switching devices on the first and second groups of bridge arms and the source of the lower switching device are respectively connected to the direct current positive bus and the negative bus, the middle points of the bridge arms are respectively connected with an alternating current power grid through an input filter circuit, and the unit power factor of the power grid current is realized in a PWM (pulse-width modulation) rectification mode. The drains of the upper switching devices and the source of the lower switching device of the third bridge arm and the fourth bridge arm are respectively connected to the direct current positive bus and the direct current negative bus, and the middle points of the bridge arms pass through a resonant leakage inductance L _k20 is connected with the primary side winding of the transformer, and DC/DC conversion is realized according to phase shift control. The drain electrode of the switching device on the bridge arm and the source electrode of the lower switching device in the direct current bus voltage decoupling branch are also respectively connected to the direct current positive bus and the direct current negative bus, and the midpoint of the bridge arm passes through an inductor L _pd14 are connected to an energy storage capacitor C _pd15, controlling the energy storage capacitor C through PWM _pd15, the voltage decoupling of the direct current bus is realized, and double power frequency ripples on the direct current bus are eliminated. Auxiliary switch and clamping capacitor C for resonance branch route _c9 are connected in series and then connected with a resonant inductor L _r10 are connected in parallel, one end of the resonant branch is connected with a DC bus capacitor C _dc11 positive pole connected to positive bus, one end connected to positive bus, DC bus capacitor C _dc11 negative pole and negative bus phase of DC busAnd the switching devices of the first, second, third and fourth groups of bridge arms, the auxiliary switch on the resonance branch and the switching devices in the direct current bus voltage decoupling branch are all switched on at zero current by controlling the switching-off phase and the duty ratio of the switching devices of the resonance branch. And the output of the secondary side winding of the isolation transformer charges a battery through a rectifier bridge circuit and an output filter circuit.

Referring to fig. 2, the modulation method of the single-phase zero-voltage soft-switching vehicle-mounted charger circuit with voltage decoupling includes a rectification modulation wave calculation module 29, a carrier signal generation module 30, a phase shift angle calculation module 31, a decoupling branch switching tube modulation wave calculation module 32, an auxiliary switching tube modulation wave calculation module 33, a current sector determination module 34, a first PWM modulation module 35, a second PWM modulation module 36, a third PWM modulation module 37, a ZVS pulse modulation module 38, a pulse rising edge synchronization control module 39, and a PWM pulse superposition modulation module 40. Main switch S of single-phase zero-voltage soft-switching charger circuit with active voltage decoupling by using above modules_r1～S_r4、S_i1～S_i4、S_d1～S_d2And an auxiliary switch S_auxAnd carrying out zero-voltage switching modulation. The output signals of the rectification modulation wave calculation module 29 and the carrier signal generation module 30 enter a first PWM modulation module 35, which is used for generating an original driving signal v of the upper and lower tubes of the first bridge arm_sr1、v_sr3And original driving signals v of upper and lower tubes of a second bridge arm_sr2、v_sr4. The output signals of the phase shift angle calculation module 31 and the carrier signal generation module 30 enter a second PWM modulation module 36, which is used for generating the original control signals v of the third and fourth bridge arm switching tubes_si1、v_si3、v_si2、v_si4. The output signals of the decoupling branch switch tube modulation wave calculation module 32 and the carrier signal generation module 30 enter a third PWM modulation module 37, and the third PWM modulation module is used for generating an original control signal v of the power decoupling branch switch tube_sd1、v_sd2. The pulse rising edge synchronous control module 39 determines the rising edge and the decoupling branch of the driving pulse of the main switching tube of the first bridge arm and the main switching tube of the second bridge arm according to the current sector judging module 34The rising edges of the driving pulses of the switching tubes of the bridge arms are aligned with the rising edges of the driving pulses of the main switching tubes of the third bridge arm and the fourth bridge arm.

Referring to fig. 3, the grid current i is defined according to fig. 1_gAnd decoupling branch inductive current i_pdThe positive direction of (2) can divide the current in a power grid power frequency cycle into four sectors. Sector I corresponds to grid current I_gA decoupling branch current i_pdIs more than or equal to zero, and the sector II corresponds to the power grid current i_gGreater than or equal to zero and decoupling branch current i_pdLess than zero, sector III corresponds to grid current i_gLess than zero, decoupling branch current i_pdIs more than or equal to zero, and the sector IV corresponds to the power grid current i_gLess than zero, decoupling branch i_pdLess than zero, determines the pulse alignment of the pulse rising edge synchronization control module 39.

Referring to fig. 4, the first PWM modulation module 35 includes a first inverter 52, a second comparator 53, a third comparator 54, a second inverter 55, a third inverter 56, a first rising edge delay module 57, a second rising edge delay module 58, a third rising edge delay module 59, and a fourth rising edge delay module 60. The triangular carrier generated by the carrier signal generation module 30 and the rectification modulation wave generated by the rectification modulation wave calculation module 29 pass through the second comparator and the first rising delay module to generate the original driving signal v on the first bridge arm_sr1The output of the second comparator passes through a second inverter and a second rising edge delay module to generate an original driving signal v of the lower tube of the first bridge arm_sr3. The output of the rectification modulation wave passing through the first inverter and the triangular carrier wave passing through the third comparator and the third rising edge time delay module generate an original driving signal v on the second bridge arm_sr2The output of the third comparator passes through a third inverter and a fourth rising edge delay module to generate an original driving signal v of a second bridge arm lower tube_sr4。

Referring to fig. 5, the second PWM modulation module 36 includes a fourth comparator 62, a fifth comparator 63, a fourth inverter 64, a fifth inverter 65, a fifth rising edge delay module 66, a sixth rising edge delay module 67, a first rising edge left shift module 68, and a second rising edge left shift module 69. Carrier signal generationFirst sawtooth carrier and phase-shifted modulated wave v generated by module 30₁The output of the fourth comparator and the fifth rising edge delay module is passed through, and the left translation module is translated for 0.5T by the first rising edge_sUpper tube pulse control signal v of width generating third bridge arm_si1. The output of the fourth comparator passes through the fourth phase inverter and the sixth rising edge delay module, and then is translated for 0.5T by the second rising edge left translation module_sLower tube pulse control signal v of width generation third bridge arm_si3。

Referring to fig. 6, the third PWM modulation block 37 includes a sixth comparator 70, a sixth inverter 71, a seventh rising edge delay block 72, and an eighth rising edge delay block 73. Triangular carrier and decoupling branch modulation wave v generated by carrier signal generation module 30_pdGenerating an original driving control signal v on the decoupling branch through a sixth comparator and a seventh rising edge delay module_sd1The output of the sixth comparator generates an original driving control signal v for the lower tube of the decoupling branch circuit through a sixth inverter and an eighth rising edge delay module_sd2。

Referring to fig. 7, the ZVS pulse modulation module 38 includes an eighth comparator 74, a seventh comparator 75, a first and gate 76, a seventh inverter 77, a ninth rising edge delay module 78, and a first falling edge advance module 79. The second sawtooth carrier and the ZVS modulated wave v generated by the carrier signal generation module 30₁The second sawtooth carrier and ZVS modulated wave v generated by the eighth comparator output and carrier signal generation module 30₂The output of the seventh comparator is processed by the first AND gate to generate a short-circuit pulse superposed signal v_scThe output of the first AND gate generates an auxiliary switching tube driving signal v through a seventh phase inverter, a ninth rising edge time delay module and a first falling edge advance module_{gs_saux}。

Referring to fig. 8, the pulse rising edge synchronization control module 39 includes third, fourth, fifth, and sixth rising edge synchronization left translation modules 80-83 corresponding to four current sectors. When the current sector judges that the input signal is the I-th sector I_gAnd i_pdOriginal driving pulse v of first and second bridge arms both greater than or equal to zero_sr1、v_sr3、v_sr2、v_sr4Original drive pulse v of decoupling branch_sd1～v_sd2The four switching period original driving pulses of the first bridge arm and the second bridge arm are simultaneously translated in the left direction by the same width through the output of the third rising edge synchronous left translation module, the two original driving pulses of the decoupling branch are simultaneously translated in the left direction by the same width, and v is obtained after translation_sr3And v_sd1Rising edge aligned 0.25T_sThe time of day. When the current is the sector II, the original driving pulse is output through the fourth rising edge synchronous left translation module, and the four driving pulses of the first bridge arm and the second bridge arm are translated synchronously and then are output_sr3After aligning 0.25Ts time and synchronously translating two driving pulses of the decoupling branch v_sd2Rising edge aligned 0.25T_sThe time of day. When the current is in the sector III, the original driving pulse is output through the fifth rising edge synchronous left translation module, and the four driving pulses of the first bridge arm and the second bridge arm are translated to v_sr1After aligning 0.75Ts time and translating two driving pulses of the decoupling branch v_sd2Rising edge aligned 0.75T_sThe time of day. When the current is in the sector IV, the original driving pulse is output through the sixth rising edge synchronous left translation module, and the four driving pulses of the first bridge arm and the second bridge arm are translated to v_sr1After aligning 0.75Ts time and translating two driving pulses of the decoupling branch v_sd1Rising edge aligned 0.75T_sThe time of day.

Referring to FIG. 9, the PWM pulse superposition modulation module 40 includes first to tenth OR gates 84 to 93. The driving pulses of the first, second, third and fourth bridge arms and the decoupling branch bridge arm modulated by the pulse rising edge synchronous control module are superposed with the short-circuit pulse superposed signal v generated by the ZVS pulse modulation module 38_scFinal main switch driving pulse signals v of a first bridge arm, a second bridge arm, a third bridge arm, a fourth bridge arm and a decoupling branch bridge arm are generated through superposition of an OR gate_{gs_Sr1}～v_{gs_Sr4}、v_{gs_Si1}～v_{gs_Si4}、v_{gs_Sd1}～v_gsRealize the pair S_r1～S_r4、S_i1～S_i4、S_d1～S_d2And S_auxSoft switching modulation of zero voltage.

The triangular carrier amplitudes +1 and-1 adopted by the first PWM modulation module and the third PWM modulation module have the frequency of f_sCarrier period of T_s. The frequency of the AC fundamental wave input by the voltage of the power grid is f_gThe period of the AC fundamental wave is T_g. The carrier frequency is an integral multiple of the fundamental frequency, and in an alternating current fundamental wave period, N carrier periods are shared:

the input carriers to the second PWM module and ZVS pulse modulation module 38 are of amplitudes 0 and V_c1Of a sawtooth carrier of frequency 2f_sWith a period of T_s/2. Modulation wave v of ZVS pulse modulation module₁＝0.5V_c1。

The phase shift angle calculation module 31 has an output phase shift angle (normalized by 180 ° in radian units) of

In the above formula V_busIs the voltage between the positive and negative buses of the bridge arm of the main switch, n is the ratio of the number of turns of the secondary side and the primary side of the phase-shifted full-bridge double-winding transformer, V_oTo output a load R _o28 average voltage across, I_oTo output a load R _o28, and the other symbols are as defined in fig. 1.

The output modulation wave of the decoupling branch switch tube modulation wave calculation module 32 is the modulation wave v in the kth switching period_pd(k) Is expressed as

In the above formula V_g、I_gFor the amplitude, C, of the network voltage 1 and the input filter inductance 2_pdThe capacitance value of the energy storage capacitor 15.

The function of the rising edge delay module is to delay and output the rising edge of the module input signal, and the output signal at the rest time is equal to the input signal. Said firstThe falling edge advancing module has the function of outputting the falling edge of the module input signal in advance, and the output signal at the rest time is equal to the input signal. The rising edge time delay of all rising edge time delay modules is t_d1The falling edge advance of the first falling edge advance module is t_d2. And the delay time satisfies T_r≤t_d1＜0.05T_s，T_r≤t_d2＜0.05T_sWherein T is_rFor the first resonance time, the expression is

In the above formula C_resThe capacitance value C of the parallel capacitor on the main switch tube of the first, second, third and fourth bridge arms and the active power decoupling branch_auxThe capacitance value of the capacitor connected in parallel with the auxiliary switch tube.

Referring to fig. 10, rectifier switching tube drive pulse v_{gs_Sr1}～v_{gs_Sr4}Active decoupling branch switching tube driving pulse v_gsd1、v_gsd2The rising edge, which is marked blue, is the moment at which the body diode of the switching tube of one bridge arm commutates to the other MOSFET of the same bridge arm. Phase-shifted full-bridge DC-DC converter hysteresis bridge arm switching tube driving pulse v_{gs_Si2}、v_{gs_S4}The rising edge labeled blue is the time when the resonant energy is not hard enough to turn on. Referring to fig. 11, the switching-on time marked as blue in the switching period is aligned, and zero-voltage switching-on is realized through the auxiliary branch circuit action.

Referring to FIG. 11, v_sr1、v_sr3、v_sr2、v_sr4Output signal waveforms v of port 2, port 3, port 4 and port 5 of the first PWM modulation module in a triangular carrier period_sd1、v_sd2The waveforms of the output signals of the

ports

2 and 3 of the third PWM modulation module in one period of the triangular carrier wave, respectively. v. of_{gs_Sc}、v_{gs_Saux}The output signal waveforms of the port 2 and the port 3 of the ZVS pulse modulation module are shown. v. of_{gs_Sr1}～v_{gs_Sr4}，v_{gs_Si1}～v_{gs_Si4},v_{gs_Sd1}～v_{gs_Sd2}Are respectively a main switch tube S_r1～S_r4、S_i1～S_i4、S_d1～S_d2The PWM control signal waveform of (1). The circuit is shown operating in the current I sector.

Referring to FIG. 12, v_{gs_Sr1}～v_{gs_Sr4}，v_{gs_Si1}～v_{gs_Si4},v_{gs_Sd1}～v_{gs_Sd2}Are respectively a main switch tube S_r1～S_r4、S_i1～S_i4、S_d1～S_d2In the current I sector, a driving signal timing chart of a triangular carrier period.

Referring to fig. 12 and fig. 13 to fig. 29, the working process of the circuit operating in a switching cycle in which the pulse control timing of the main switching tube is as shown in fig. 12 is analyzed and explained for the single-phase zero-voltage soft-switching charger circuit with voltage decoupling, taking the I-th sector of current as an example, and the circuit has 17 working states in one switching cycle. Fig. 13 to 29 are equivalent circuits of one switching cycle, and the waveforms of main voltage and current during operation are shown in fig. 30, and the reference direction of voltage and current of the circuits is shown in fig. 1. The phase analysis for the other sectors is similar. The specific phase analysis is as follows:

stage one (t)₀～t₁)：

As shown in fig. 13, at t₀Time auxiliary switch S_auxZero voltage turn-off, resonant inductor L_rThe series resonance occurs with the parallel capacitor of the main switch to make the main switch tube S_r2、S_r3、S_i1、S_i2Parallel capacitor C_r2、C_r3、C_i1、C_i2、C_d1Discharging while making the auxiliary switching tube S_auxParallel capacitor C_auxCharging, primary side current i of transformer_pThrough a switching tube S_i3And S_i4Forming a loop at an output voltage-V_oUnder the action of/n, i_pLinear down, transformer secondary side diode D₁And D₄Conducting and outputting the filter inductance current i_LoWith V_o/L_oSlope line of (2)Reduced, active power decoupling branch current i_pdThe linearity decreases. The phase-shifted full-bridge circuit is in a circulating current state, and the primary side of the transformer does not transmit energy to the secondary side. At t₁Time, main switch tube S_r2、S_r3、S_i1、S_i2、S_d1Parallel capacitor C_r2、C_r3、C_i1、C_i2、C_d1The voltage resonates to zero and the phase ends.

Stage two (t)₁～t₂)：

As shown in fig. 14, at t₁Diode D after time_r2、D_r3、D_i1、D_i2、D_d1Will be conducted to connect the capacitor C in parallel_r2、C_r3、C_i1、C_i2、C_d1Upper voltage is clamped to zero, resonant inductance L_rClamping the voltage across V_busResonant inductor current i_LrLinearly rising phase-shifted full-bridge circuit working state in same stage one (t)₀～t₁) And (5) the consistency is achieved. Active power decoupling branch current i_pdThe linearity decreases. At t₂At the moment, the main switch S_r1、S_r2、S_r3、S_i1、S_i2、S_d1、S_d2The zero voltage turns on and this phase ends.

Stage three (t)₂～t₃)：

As shown in fig. 15, at t₂After the moment, all the switching tubes S of the four main switching legs_r1～S_r4、S_i1～S_i4The circuit enters a direct-connection stage after being switched on, and the voltage V of the intermediate direct-current bus_dcMaking a resonant inductor current i_LrContinue with V_dc/L_rLinear rise in rate, resonant inductance L_rThe resonant energy is stored. The working state of the phase-shifted full-bridge circuit is in the same stage one (t)₀～t₁) And (5) the consistency is achieved.

Stage four (t)₃～t₄)：

As shown in fig. 16, at t₃Time, main switch tube S_r1、S_r2、S_i1、S_i4、S_d2Turn-off, resonant inductance L_rThe auxiliary switch tube S generates series resonance with the parallel capacitor of the main switch_auxParallel capacitor C_auxDischarging while making the main switching tube S_r1、S_r2、S_i1、S_i4、S_d2Parallel capacitor C_r1、C_r2、C_i1、C_i4、C_d2Charging at t₄Time of day, auxiliary switch tube S_auxParallel capacitor C_auxThe voltage resonates to zero. Because the main switch tube S_i4Turning off, reversing the polarity of the voltage applied to the primary side of the phase-shifted full-bridge double-winding transformer, reducing the primary and secondary currents of the transformer, and making the secondary current i of the transformer_sLess than the output filter inductor current i_LoDue to i_LoCan not suddenly change, then diode D₁～D₄At the same time, the secondary side of the transformer is short-circuited, and the output current starts to change from D₁、D₄To D₂、D₃Current conversion process of D₁、D₄Current reduction of D₂、D₃The current of (2) increases.

Stage five (t)₄～t₅)：

As shown in fig. 17, at t₄Diode D after time_auxWill be conducted to connect C_auxIs clamped to zero, the resonant inductance L_rThe voltage across is clamped at-V_ccBy means of a clamping capacitor C_c、S_auxLoop magnetic-releasing and resonance inductor L formed by parallel diodes_rCurrent with slope V_cc/L_rLinearly decreasing, active power decoupling branch current i_pdLinearly increasing; at t₅Time of day, auxiliary switch tube S_auxThe zero voltage turns on and this phase ends. Phase-shifted full-bridge primary and secondary current engineering state with same stage four (t)₃～t₄)。

Stage six (t)₅～t₆)：

As shown in fig. 18, at t₅Time of day, auxiliary switch S_auxZero voltage turn-on, resonant inductor L_rThe voltage across is clamped at-V_ccBy means of a clamping capacitor C_c、S_aThe formed loop discharges magnetism and resonance inductance L_rThe current continues with a slope V_cc/L_rLinearly decreasing, working state of active power decoupling branch is same as stage five, and current engineering state of phase-shifted full-bridge primary and secondary sides is same as stage four (t)₃～t₄) During the phases five and six, the primary side current of the transformer decreases linearly and changes direction, t₆Time i_p(t₆)＝-I₁When D is₂、D₃Is raised to be equal to the output filter inductor current i at that time_LoDiode D₁、D₄Is turned off by the current falling to zero, and this phase ends.

Stage seven (t)₆～t₇)：

As shown in FIG. 19, t₆After the moment, the primary side current ip of the transformer is larger than the output filter inductance current ni which is converted from the secondary side current of the transformer to the primary side_LoThe primary side current and the secondary side current are increased in an inverse linear manner, and the output filter inductance current is increased by a slope (nV)_bus-V_o)/L_oAnd the working state of the active power decoupling branch is in the same stage five. The phase-shifted full-bridge circuit power begins to be transferred from the primary side to the secondary side of the transformer. Resonant inductor L_rThe voltage across is clamped at-V_cc，L_rThe current continues with a slope V_cc/L_rThe linearity decreases.

Stage eight (t)₇～t₈)：

As shown in fig. 20, the main switch S_r3Zero voltage turn-off, grid input current i_gFor main switch S_r1Parallel capacitor C_r1Discharge to the main switch S_r3Parallel capacitor C_r3And (6) charging. Resonant inductor L_rThe voltage across is clamped at-V_cc，L_rThe current continues with a slope V_cc/L_rLinearly decreasing, the working state of the active power decoupling branch is in the same stage five, and the working state of the phase-shifted full-bridge circuit is in the same stage seven (t)₆～t₇)。

Stage nine (t)₈～t₉)：

As shown in fig. 21, tot₈Time, main switch tube S_r1Parallel capacitor C_r1Discharge to zero, main switch S_r1Anti-parallel diode D_r1Begins to conduct, the main switch S_r1The tube voltage is clamped to zero, the main switch S_r3The tube voltage is clamped to V_dc+V_cc，L_rThe current continues with a slope V_cc/L_rLinearly decreasing, the working state of the active power decoupling branch is in the same stage five, and the working state of the phase-shifted full-bridge circuit is in the same stage seven (t)₆～t₇)。

Stage ten (t)₉～t₁₀)：

As shown in FIG. 22, the main switching tube S_r1Zero voltage is switched on, the first bridge arm completes current conversion, L_rThe current continues with a slope V_cc/L_rThe linearity is reduced, the working state of the phase-shifted full-bridge circuit is in the same stage seven, and the working state of the active power decoupling branch circuit is in the same stage five.

Stage eleven (t)₁₀～t₁₁)：

As shown in fig. 23, at t₁₀Time, main switch tube S_i3Turn off when the primary side current i of the transformer is turned off_pRising negatively to a maximum i_p(t₁₀)＝-I_p. Inductance L of phase-shifted full-bridge circuit_Ξ(equivalent leakage inductance L from the primary side of the transformer_kAnd an output filter inductance L reduced to the primary side_o/n²Series connection) main switching tube S_i1、S_i3Parallel capacitor C_i1、C_i3Resonance occurs, C_i1Discharge, C_i3Charging at t₁₁Time of day, parallel capacitance C_i3Voltage on to V_Cc+V_dcAnd C is_i1The voltage on the active power decoupling branch is reduced to zero, the stage is ended, and the working state of the active power decoupling branch is the same as the stage five.

Stage twelve (t)₁₁～t₁₂)：

As shown in fig. 24, at t₁₁Time of day, diode D_i1And conducting. Primary side current i of transformer_pThrough diode D_i1And a switching tube S_i2Forming a loop at an output voltage-V_o/nUnder the action of (a) < i >_pReduced reverse linearity, transformer secondary side diode D₂And D₃Conducting and outputting the filter inductance current i_LoWith V_o/L_oThe slope of (c) decreases linearly. The phase-shifted full-bridge circuit is in a circulating current state, the primary side of the transformer does not transmit energy to the secondary side, and the working state of the active power decoupling branch circuit is in the same stage five.

Stage thirteen (t)₁₂～t₁₃)：

As shown in fig. 25, at t₁₂Time, main switch tube S_i1Zero voltage turn-on diode D_i1On, the primary side current i of the transformer_pThrough a switching tube S_i1And S_i2Forming a loop at an output voltage-V_oUnder the action of/n, i_pLinear down, diode D₂And D₃Conducting and outputting the filter inductance current i_LoWith V_o/L_oThe slope of (c) decreases linearly. The phase-shifted full-bridge circuit is in a primary side circulation state, the primary side of the transformer does not transmit energy to the secondary side, and the energy is transmitted at t₁₃Constantly, active power decoupling branch switch tube S_d1Zero voltage turn off, t₂To t₁₃Time-corresponding active power decoupling branch duty ratio 0.5D_pd T_s。

Stage fourteen (t)_13～t₁₄)：

As shown in fig. 26, at t₁₃Constantly, active power decoupling branch switch tube S_d1Zero voltage turn-off, pair C_d1Charging, to C_d2And (4) discharging. Phase-shifted full-bridge circuit and rectifier circuit working state same stage thirteen (t)₁₂～t₁₃)。

Stage fifteen (t)_14～t₁₅)：

As shown in fig. 27, at t₁₄Time of day, C_d2Discharge to zero, diode D_d2Conducting and active power decoupling branch current i_pdDescending phase-shift full-bridge circuit and rectifier circuit working state in same stage thirteen (t)₁₂～t₁₃)。

Stage fifteen (t)_15～t₁₆)：

As shown in fig. 28, at t₁₅Constantly, active power decoupling branch switch tube S_d2Zero voltage open, phase-shift full bridge circuit, rectifier circuit working state same stage thirteen (t)₁₂～t₁₃)。

Stage fifteen (t)_16～t₁₇/t₀)：

As shown in fig. 29, at t₁₆Constantly, active power decoupling branch switch tube S_d2Zero voltage turn-off, active power decoupling branch current i_pdDescending phase-shift full-bridge circuit and rectifier circuit working state in same stage thirteen (t)₁₂～t₁₃)。

Claims

1. A modulation method of a single-phase soft switching charger with active voltage decoupling is characterized in that: the method is that the working frequency of the switch device of the power factor correction circuit, the switch device of the DC/DC conversion circuit and the switch device in the DC bus voltage decoupling branch are the same, because the phase of the rising edge of the control signal of the switch device of the lagging bridge arm of the phase-shifted full-bridge DC/DC conversion circuit is changed, the rising edge of the PWM control signal of the switch device of the power factor correction circuit and the rising edge of the control signal of the switch device in the DC bus voltage decoupling branch are synchronous with the rising edge of the PWM signal controlled by the DC/DC conversion in the switching period, and the S is realized by controlling the phase and the duty ratio of the switch device of the resonance branch when the switch device is turned off_r1～S_r4、S_i1～S_i4、S_d1And S_d2And an auxiliary switch S_auxIs turned on at zero voltage by controlling S_d1And S_d2The duty ratio of the capacitor C_pdControlling charging and discharging, and eliminating double power frequency ripples on a direct current bus;

the method is realized by depending on a single-phase soft switching charger topology with active voltage decoupling, and the single-phase soft switching charger circuit with the active voltage decoupling comprises four groups of bridge arms, resonance branches and direct-current bus voltage decoupling branches, wherein the four groups of bridge arms are formed by two series-connected fully-controlled switches containing inverse diodes; wherein: upper and lower switches of first bridge arm and their inverseAnd the diodes are respectively S_r1、D_r1And S_r3、D_r3The upper and lower switches and their anti-parallel diodes of the second bridge arm are respectively S_r2、D_r2And S_r4、D_r4The upper and lower switches and their anti-parallel diodes of the third bridge arm are respectively S_i1、D_i1And S_i3、D_i3The upper and lower switches and their anti-parallel diodes of the fourth bridge arm are respectively S_i2、D_i2And S_i4、D_i4(ii) a The auxiliary switch of the resonance branch and the anti-parallel diode are S respectively_aux、D_auxThe resonance branch circuit also comprises a resonance inductor L_rAnd a clamp capacitor C_c(ii) a The direct current bus voltage decoupling branch comprises a bridge arm and an inductor L, wherein the bridge arm and the inductor L are formed by a group of two series-connected fully-controlled switches comprising anti-parallel diodes_pdAnd an energy storage capacitor C_pdThe upper and lower switching devices and the anti-parallel diodes of the bridge arm are respectively S_d1、D_d1And S_d2、D_d2；

The drain electrodes of the switching devices on the first and second groups of bridge arms and the source electrode of the lower switching device are respectively connected to a direct current positive bus and a direct current negative bus, the middle points of the bridge arms are respectively connected with an alternating current power grid through an input filter circuit, and the unit power factor of the power grid current is realized in a PWM (pulse-width modulation) rectification mode; the drains of the upper switching devices and the source of the lower switching device of the third bridge arm and the fourth bridge arm are respectively connected to the direct current positive bus and the direct current negative bus, and the middle points of the bridge arms pass through a resonant leakage inductance L_kThe transformer is connected with a primary side winding of the transformer, and DC/DC conversion is realized according to phase-shift control; the drain electrode of the switching device on the bridge arm and the source electrode of the lower switching device in the direct current bus voltage decoupling branch are also respectively connected to the direct current positive bus and the direct current negative bus, and the midpoint of the bridge arm passes through an inductor L_pdIs connected to an energy storage capacitor C_pdControlling the energy storage capacitor C by PWM_pdThe voltage decoupling of the direct current bus is realized by charging and discharging, and double power frequency ripples on the direct current bus are eliminated; the resonant branch circuit comprises an auxiliary switch containing a reverse parallel diode and a clamping capacitor C_cConnected in series and then connected with a resonant inductor L_rOne end of the resonance branch is connected with the DC bus capacitor C in parallel_dcIs connected with the positive pole of the anode, and one end of the anode is connected with the positive nutLine-connected, DC bus capacitor C_dcThe negative pole of the first, second, third and fourth groups of bridge arms, the auxiliary switch on the resonance branch and the switch device in the direct current bus voltage decoupling branch are all switched on at zero current by controlling the switching-off phase and duty ratio of the switch device of the resonance branch; the secondary side winding output of the isolation transformer charges the battery through the rectifier bridge circuit and the output filter circuit.

2. The method of modulating a single-phase soft-switching charger with source-voltage decoupling as claimed in claim 1, wherein: the method is realized based on the following modules: the device comprises a rectification modulation wave calculation module (29), a carrier signal generation module (30), a phase shift angle calculation module (31), a decoupling branch switching tube modulation wave calculation module (32), an auxiliary switching tube modulation wave calculation module (33), a current sector judgment module (34), a first PWM modulation module (35), a second PWM modulation module (36), a third PWM modulation module (37), a ZVS pulse modulation module (38), a pulse rising edge synchronous control module (39) and a PWM pulse superposition modulation module (40); the output signals of the rectification modulation wave calculation module (29) and the carrier signal generation module (30) enter a first PWM (pulse-width modulation) module (35), and the first PWM module is used for generating an original driving signal v of a first bridge arm upper and lower tube_sr1、v_sr3And original driving signals v of upper and lower tubes of a second bridge arm_sr2、v_sr4(ii) a The output signals of the phase shift angle calculation module (31) and the carrier signal generation module (30) enter a second PWM (pulse-width modulation) module (36), and the second PWM module is used for generating original control signals v of the third bridge arm switching tube and the fourth bridge arm switching tube_si1、v_si3、v_si2、v_si4(ii) a The output signals of the decoupling branch switch tube modulation wave calculation module (32) and the carrier signal generation module (30) enter a third PWM (pulse-width modulation) module (37), and the third PWM module is used for generating an original control signal v of the power decoupling branch switch tube_sd1、v_sd2(ii) a The pulse rising edge synchronous control module (39) determines the rising edges of the main switching tube driving pulses of the first bridge arm and the second bridge arm and the switching tube driving pulses of the decoupling branch bridge arm according to the current sector judging module (34)The rising edge of the impulse is aligned with the rising edges of the driving pulses of the main switching tubes of the third bridge arm and the fourth bridge arm; the output signals of the auxiliary switch tube modulation wave calculation module (33) and the carrier signal generation module (30) enter a ZVS pulse modulation module (38), and the ZVS pulse modulation module (38) outputs a signal v_scWith the original control signal v_sr1、v_sr3、v_sr2、v_sr4、v_si1、v_si3、v_si2、v_si4、v_sd1、v_sd2Are input into a PWM pulse superposition modulation module (40) together to respectively generate switching tubes S_r1～S_r4、S_i1～S_i4、S_d1～S_d2Control PWM signal v_{gs_Sr1}～v_{gs_Sr4}、v_{gs_Si1}～v_{gs_Si3}、v_{gs_Sd1}～v_{gs_Sd2}Realize to S_r1～S_r4、S_i1～S_i4、S_d1～S_d2And S_auxSoft switching modulation of zero voltage.

3. The method of modulating a single-phase soft-switching charger with source-voltage decoupling as claimed in claim 2, wherein: the first PWM modulation module (35) comprises a first inverter (52), a second comparator (53), a third comparator (54), a second inverter (55), a third inverter (56), a first rising edge delay module (57), a second rising edge delay module (58), a third rising edge delay module (59) and a fourth rising edge delay module (60); the triangular carrier generated by the carrier signal generation module (30) and the rectification modulation wave generated by the rectification modulation wave calculation module (29) generate an original driving signal v of the first bridge arm upper tube through a second comparator and a first rising time delay module_sr1The output of the second comparator passes through a second inverter and a second rising edge delay module to generate an original driving signal v of the lower tube of the first bridge arm_sr3The original driving signal v on the second bridge arm is generated by the output of the rectification modulation wave passing through the first inverter and the triangular carrier wave passing through the third comparator and the third rising edge time delay module_sr2The output of the third comparator passes through a third inverter and a fourth rising edge delay module to generate an original driving signal v of a second bridge arm lower tube_sr4。

4. The method of modulating a single-phase soft-switching charger with source-voltage decoupling as claimed in claim 2, wherein: the second PWM modulation module (36) comprises a fourth comparator (62), a fifth comparator (63), a fourth inverter (64), a fifth inverter (65), a fifth rising edge delay module (66), a sixth rising edge delay module (67), a first rising edge left translation module (68) and a second rising edge left translation module (69); a first sawtooth carrier wave and a phase-shift modulation wave v generated by a carrier signal generation module (30)₁The output of the fourth comparator and the fifth rising edge delay module is passed through, and the left translation module is translated for 0.5T by the first rising edge_sUpper tube pulse control signal v of width generating third bridge arm_si1(ii) a The output of the fourth comparator passes through the fourth phase inverter and the sixth rising edge delay module, and then is translated for 0.5T by the second rising edge left translation module_sLower tube pulse control signal v of width generation third bridge arm_si3A first sawtooth carrier wave and a phase-shift modulated wave v generated by a carrier signal generation module (30)₁A lower tube pulse control signal v of a fourth bridge arm is generated by a fifth comparator_si4The output of the fifth comparator generates a top tube pulse control signal v of the fourth bridge arm through a fifth inverter_si2。

5. The method of modulating a single-phase soft-switching charger with source-voltage decoupling as claimed in claim 2, wherein: the third PWM modulation module (37) comprises a sixth comparator (70), a sixth inverter (71), a seventh rising edge delay module (72) and an eighth rising edge delay module (73), and a triangular carrier wave and a decoupling branch modulation wave v generated by the carrier signal generation module (30)_pdGenerating an original driving control signal v on the decoupling branch through a sixth comparator and a seventh rising edge delay module_sd1The output of the sixth comparator generates an original driving control signal v for the lower tube of the decoupling branch circuit through a sixth inverter and an eighth rising edge delay module_sd2；

The output modulation wave of a decoupling branch switch tube modulation wave calculation module (32) isThe kth switching period, modulated wave v_pd(k) Is expressed as

In the above formula V_g、I_gThe current amplitude, C, of the network voltage (1) and the input filter inductance (2)_pdIs the capacitance value, V, of the energy storage capacitor (15)_dcIs the dc bus voltage.

6. The method of modulating a single-phase soft-switching charger with source-voltage decoupling as claimed in claim 2, wherein: the ZVS pulse modulation module (38) comprises an eighth comparator (74), a seventh comparator (75), a first AND gate (76), a seventh inverter (77), a ninth rising edge delay module (78) and a first falling edge advance module (79); a second sawtooth carrier wave and a ZVS modulation wave v generated by the carrier signal generation module (30)₁The output of the eighth comparator and the second sawtooth carrier and ZVS modulated wave v generated by the carrier signal generation module (30)₂The output of the seventh comparator is processed by the first AND gate to generate a short-circuit pulse superposed signal v_scThe output of the first AND gate generates an auxiliary switching tube driving signal v through a seventh phase inverter, a ninth rising edge time delay module and a first falling edge advance module_{gs_saux}。

7. The method of modulating a single-phase soft-switching charger with source-voltage decoupling as claimed in claim 2, wherein: the current sector judging module (34) divides the current in one power grid power frequency period into four sectors: sector I corresponds to grid current I_gA decoupling branch current i_pdIs more than or equal to zero, and the sector II corresponds to the power grid current i_gGreater than or equal to zero and decoupling branch current i_pdLess than zero, sector III corresponds to grid current i_gLess than zero, decoupling branch current i_pdIs more than or equal to zero, and the sector IV corresponds to the power grid current i_gLess than zero, decoupling branch i_pdLess than zero, determining pulse rising edge synchronizationControlling a pulse alignment mode of the module (39);

the pulse rising edge synchronous control module (39) comprises a third rising edge synchronous left translation module, a fourth rising edge synchronous left translation module, a fifth rising edge synchronous left translation module and a sixth rising edge synchronous left translation module (80-83) which correspond to four current sectors, and when the current sectors judge that an input signal is an I-th sector, original driving pulses v of a first bridge arm and a second bridge arm_sr1、v_sr3、v_sr2、v_sr4Original drive pulse v of decoupling branch_sd1～v_sd2The four switching period original driving pulses of the first bridge arm and the second bridge arm are simultaneously translated in the left direction by the same width through the output of the third rising edge synchronous left translation module, the two original driving pulses of the decoupling branch are simultaneously translated in the left direction by the same width, and v is obtained after translation_sr3And v_sd1Rising edge aligned 0.25T_sAt the moment, when the current is in the sector II, the original driving pulse is output through the fourth rising edge synchronous left translation module, and the four driving pulses of the first bridge arm and the second bridge arm are translated synchronously and then are output according to the v_sr3After aligning 0.25Ts time and synchronously translating two driving pulses of the decoupling branch v_sd2Rising edge aligned 0.25T_sAt the moment, when the current is the III sector, the original driving pulse is output through the fifth rising edge synchronous left translation module, and the four driving pulses of the first bridge arm and the second bridge arm are translated to v_sr1After aligning 0.75Ts time and translating two driving pulses of the decoupling branch v_sd2Rising edge aligned 0.75T_sAt the moment, when the current is in the IV sector, the original driving pulse is output through the sixth rising edge synchronous left translation module, and the four driving pulses of the first bridge arm and the second bridge arm are translated to v_sr1After aligning 0.75Ts time and translating two driving pulses of the decoupling branch v_sd1Rising edge aligned 0.75T_sThe time of day.

8. The method of modulating a single-phase soft-switching charger with source-voltage decoupling as claimed in claim 2, wherein: the PWM pulse superposition modulation module (40) comprises first to tenth OR gates (84-93); the driving pulses of the first, second, third and fourth bridge arms and the decoupling branch bridge arm which are modulated by the pulse rising edge synchronous control module are respectively superposed with the short-circuit pulse superposed signal v generated by the ZVS pulse modulation module (38)_scRespectively generating final main switch driving pulse signals v of a first bridge arm, a second bridge arm, a third bridge arm, a fourth bridge arm and a decoupling branch bridge arm through an OR gate in a superposition mode_{gs_Sr1}～v_{gs_Sr4}、v_{gs_Si1}～v_{gs_Si4}、v_{gs_Sd1}～v_gsRealize the pair S_r1～S_r4、S_i1～S_i4、S_d1～S_d2And S_auxSoft switching modulation of zero voltage.