CN108964474B - Three-mode rectification topological structure based on LLC resonant converter - Google Patents
Three-mode rectification topological structure based on LLC resonant converter Download PDFInfo
- Publication number
- CN108964474B CN108964474B CN201810918522.8A CN201810918522A CN108964474B CN 108964474 B CN108964474 B CN 108964474B CN 201810918522 A CN201810918522 A CN 201810918522A CN 108964474 B CN108964474 B CN 108964474B
- Authority
- CN
- China
- Prior art keywords
- mode
- load
- tube
- bridge
- transformer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
- H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
- H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The utility model provides a three mode rectification topological structure based on LLC resonant transformation ware, the transformer once inclines full-bridge structure and LLC resonant transformation ware that includes 4 MOSFET and constitutes, the converter includes resonant inductance, resonant capacitance and transformer excitation inductance, input and output side realize the half-bridge when light load and heavy load interconversion under the circumstances that does not adopt high frequency drive, the full-bridge, the interconversion that load and transformer break away from (no-load), do not use high frequency drive, reduce the voltage ripple, full load within range control bus voltage, adopt the purpose that the dead zone controller of electric current reaches current sharing. The transformer secondary side adopts a 3-mode adjustable device, and the transformer secondary side adopts the PWM controller to switch heavy load mode (full-bridge), light load mode (half-bridge) and no-load mode, adopts full-bridge rectification structure during the heavy load, adopts half-bridge rectification structure during the light load, realizes that the heavy load is to light load steady transition, output voltage ripple minimizing, synchronous switching once accomplish, improve synchronous rectification conversion efficiency's purpose greatly.
Description
Technical Field
The invention discloses a three-mode rectification topological structure based on an LLC resonant converter, and relates to the field of electric energy conversion.
Background
The LLC converter is widely applied to a switching power supply due to the unique topological characteristic, and compared with the traditional power frequency transformer, the LLC converter has the advantages of reducing weight, size and cost and improving electric energy quality. The resonance technology is a common attention of people as an optimization method for realizing soft switching, a resonance network is a basic conversion unit of the resonance network, and when resonance occurs, current or voltage in a circuit is periodically reduced to zero, so that a switching tube is switched on or off under the condition of zero current or zero voltage, the switching loss is reduced, and the purpose of soft switching is achieved.
The ideal synchronous rectifier should realize the same electrical function of a diode rectifier and reduce conduction loss, because the MOSFET conducts electricity bidirectionally after being turned on, which is different from a diode, a gate signal needs to be accurately controlled, and when a forward current (a source electrode flows to a drain electrode) exists under an ideal condition, the MOSFET is turned on, so that the influence on the circuit work caused by improper work is avoided.
Because the LLC circuit is a current type output circuit, the output is only clamped by the output voltage of the secondary side winding voltage of the filter capacitor transformer, the voltage polarity change is realized in a synchronous rectifier tube, the LLC circuit cannot adopt voltage control type self-driving and can only adopt current detection, and the LLC circuit is called a current control driving method. However, the LLC resonant converter also has the disadvantage that the voltage gain exceeds the specified range under light load, and the conventional method adopts a method of increasing the operating frequency of the switching tube to solve this problem, and the frequency is greatly increased to cause ZVS loss and increase output voltage ripple, which reduces efficiency and increases battery interference.
Under no-load working condition, the LLC is influenced by parasitic parameters, the gain curve upwarps, the output voltage rises and the LLC is not easy to control. When the output voltage rises to a limit value, the control signal of the switching tube is turned off, the converter enters a no-load mode, the output voltage drops, when the output voltage drops to the limit value, the control signal of the switching tube is normally given out, the converter normally operates, the voltage rises, and the process is repeated. The method has the consequences that the output voltage ripple is overlarge, larger electromagnetic interference is caused, and the stable operation of the system is not facilitated. Due to the narrow bandwidth, the LLC dynamic response speed is slow, and a novel control method needs to be provided to make up for the deficiency.
Disclosure of Invention
The invention aims to solve the technical problem that the existing full-bridge/half-bridge rectification technology is improved, and provides a three-mode rectification topology structure based on an LLC resonant converter. Therefore, the output voltage ripple can be reduced, and the system can operate stably.
The technical scheme adopted by the invention is as follows:
a three-mode rectification topology based on an LLC resonant converter, comprising:
the full-bridge structure composed of 4 MOS transistors Q1, Q2, Q3 and Q4 and the LLC resonant converter are positioned on the primary side of the transformer T0, and the LLC resonant converter comprises a resonant inductor L
rResonant capacitor C
rTransformer excitation inductance L
m；
A 3-mode switchable rectifier on the secondary side of the transformer T0, the 3-mode switchable rectifier including 4 switching tubes S1, S2, S3, S4 and an off-chip capacitor C
O；
Signal input terminal U
inThe positive electrode of the MOS tube Q2 and the source electrode of the MOS tube Q4 are respectively connected with the drain electrode of the MOS tube Q1 and the drain electrode of the MOS tube Q3, the source electrode of the MOS tube Q1 is connected with the drain electrode of the MOS tube Q2, the source electrode of the MOS tube Q3 is connected with the drain electrode of the MOS tube Q4, and the source electrodes of the MOS tube Q2 and the MOS tube Q4 are both connected with a signal input end U
in-a pole of (a); the source electrode of the MOS transistor Q1 is connected with a resonant capacitor C
rOne terminal, resonant capacitor C
rThe other end is connected with a transformer excitation inductor L
mOne end, transformer excitation inductance L
mThe other end is connected with the drain electrode of the MOS tube Q4;
the drain of the switch tube S1 is connected with the source of the switch tube S2, the drain of the switch tube S2 is connected with the drain of the switch tube S4, the source of the switch tube S4 is connected with the drain of the switch tube S3, and the source of the switch tube S3 is connected with the source of the switch tube S1;
the drain electrode of the switch tube S1 and the source electrode of the switch tube S4 are respectively connected with two ends of the secondary side of the transformer T0;
the source of the switch tube S3 and the drain of the switch tube S4 are respectively connected with the external capacitor C
OAt both ends of the same.
A three-mode rectification method based on an LLC resonant converter is characterized in that control signals of an MOS tube Q3 and an MOS tube Q4 on the primary side of a transformer T0 are adjusted by referring to traditional frequency control on the input side of a topological structure, and all switching tubes are controlled by traditional frequency under the condition of heavy load of the LLC resonant converter; when the LLC resonant converter is in light load condition, the switching tube control mode of the left arm is unchanged, MOS transistor Q3 control signal is set to 0, MOS transistor Q3 is turned off, MOS transistor Q4 control signal is set to 1, MOS transistor Q4 is turned on, i.e. the conversion from full bridge to half bridge at the primary side of transformer T0 is completed.
A three-mode rectification method based on an LLC resonant converter is characterized in that full-bridge/half-bridge conversion is carried out on the input side of a topological structure, a hysteresis controller is adopted to generate full-bridge half-bridge switching signals, bus voltage is controlled under the full-load condition, and a current dead zone controller is adopted to achieve the purpose of current equalization.
A three-mode rectification method based on an LLC resonant converter adopts a 3-mode switchable rectifier on the output side of a topological structure, and the rectifier is divided into a heavy-load mode, a light-load mode and a no-load mode, wherein the 3-mode switchable rectifier comprises 4 switching tubes S1, S2, S3 and S4 and an off-chip capacitor C
OThe heavy load, light load and no-load modes of the rectifier are adjusted by adopting Pulse Width Modulation (PWM).
The invention discloses a three-mode rectification topological structure based on an LLC resonant converter, which has the beneficial effects that: during light load, according to traditional frequency control, the control signal of the switching tube on the primary side of the LLC transformer is adjusted, the full bridge is converted into a half bridge, the effect of controlling the voltage of the direct current bus is realized before an LLC gain curve upwarps, and the purpose of stabilizing the output voltage is achieved on the basis of not improving the working frequency of the switching tube. The secondary side of the transformer adopts a three-mode switchable rectifier, and is different from the traditional rectifier in that only 4 synchronous rectifier tubes and one capacitor are used, and the pulse width modulation technology is adopted to realize the interconversion of a heavy-load mode, a light-load mode and a no-load mode, so that the aims of reducing voltage ripples, improving conversion efficiency and completing synchronous switching at one time are fulfilled.
Drawings
The invention is further illustrated by the following examples in conjunction with the accompanying drawings:
fig. 1 is a 3-mode switchable half-bridge/full-bridge LLC resonant converter.
Fig. 2(a) is a schematic diagram of an input side driving signal of the LLC resonant converter.
Fig. 2(b) is a schematic diagram of an input side driving signal of the LLC resonant converter.
Fig. 3(a) is a schematic view of the heavy load (1 mode) condition of the 3 mode adjustable rectifier.
Fig. 3(b) is a schematic view of a light-load (2-mode) working condition of the 3-mode adjustable rectifier.
Fig. 3(c) is a schematic diagram of no-load (3-mode) working condition of the 3-mode adjustable rectifier.
Fig. 4 is a schematic diagram of a control flow of a 3-mode switchable rectifier.
Fig. 5 is a schematic diagram of a PWM controller.
Fig. 6 shows the operating principle of the PWM controller.
Fig. 7 is a graph showing a resonance inductor current waveform and a transformer exciting inductor current waveform, respectively.
Fig. 8 is a diagram of the dc side output voltage waveform of the multi-mode rectifier.
Fig. 9 is a waveform diagram of the secondary side current of the transformer.
Fig. 10 is a waveform diagram of the output current when the rectifier is in a full-bridge state.
Fig. 11 is a waveform diagram of an output current in a half bridge state of a rectifier.
Detailed Description
A three-mode rectification topology based on an LLC resonant converter, comprising:
the full-bridge structure composed of 4 MOS transistors Q1, Q2, Q3 and Q4 and the LLC resonant converter are positioned on the primary side of the transformer T0, and the LLC resonant converter comprises a resonant inductor L
rResonant capacitor C
rTransformer excitation inductance L
m；
A 3-mode switchable rectifier on the secondary side of the transformer T0, the 3-mode switchable rectifier including 4 switching tubes S1, S2, S3, S4 and an off-chip capacitor C
O。
Signal input terminal U
inThe positive electrode of the MOS tube Q2 and the source electrode of the MOS tube Q4 are respectively connected with the drain electrode of the MOS tube Q1 and the drain electrode of the MOS tube Q3, the source electrode of the MOS tube Q1 is connected with the drain electrode of the MOS tube Q2, the source electrode of the MOS tube Q3 is connected with the drain electrode of the MOS tube Q4, and the source electrodes of the MOS tube Q2 and the MOS tube Q4 are both connected with a signal input end U
in-a pole of (a); the source electrode of the MOS transistor Q1 is connected with a resonant capacitor C
rOne terminal, resonant capacitor C
rThe other end is connected with a transformer excitation inductor L
mOne terminal, transformerExcitation inductance L
mThe other end is connected with the drain electrode of the MOS tube Q4; the drain of the switch tube S1 is connected with the source of the switch tube S2, the drain of the switch tube S2 is connected with the drain of the switch tube S4, the source of the switch tube S4 is connected with the drain of the switch tube S3, and the source of the switch tube S3 is connected with the source of the switch tube S1; the drain electrode of the switch tube S1 and the source electrode of the switch tube S4 are respectively connected with two ends of the secondary side of the transformer T0; the source of the switch tube S3 and the drain of the switch tube S4 are respectively connected with the external capacitor C
OAt both ends of the same.
According to the input side of the topological structure, the control signals of MOS tubes Q3 and Q4 on the primary side of the transformer of the LLC are adjusted by referring to the traditional frequency control, all the switching tubes are controlled by the traditional frequency control under the condition that the LLC resonant converter is in a heavy load, the control mode of the switching tube of the left bridge arm is unchanged when the LLC resonant converter is in a light load condition, the control signal of the MOS tube Q3 is set to be 0, the MOS tube Q3 is turned off, the control signal of the MOS tube Q4 is set to be 1, and the MOS tube Q4 is turned on, namely the conversion from the full bridge to the half bridge on the primary side of.
The input side of the topological structure is subjected to full-bridge/half-bridge conversion, a hysteresis controller is adopted to generate full-bridge half-bridge switching signals, bus voltage is controlled under the full-load condition, and the current flow equalization purpose is achieved by adopting a current dead zone controller.
The output side of the topological structure adopts a 3-mode switchable rectifier which is divided into a heavy-load mode (1 mode), a light-load mode (2 mode) and a no-load mode (3 mode), and is greatly different from the traditional heavy-load mode (1 mode) and no-load mode (3 mode), wherein the 3-mode switchable rectifier comprises 4 switching tubes S1, S2, S3 and S4 and an off-chip capacitor C
O. Pulse Width Modulation (PWM) is used to regulate the heavy, light and no load modes of the rectifier. The output voltage ripple can be obviously reduced, the switching loss is reduced, and the efficiency is improved.
The conventional power regulation divides the modes into heavy load (1 mode) and no load (3 mode), as shown in fig. 2(a) and 2 (b).
The three modes provided by the invention divide the rectifier into a heavy load mode (1 mode), a light load mode (2 mode) and a no-load mode (3 mode), the full-bridge/half-bridge structure carries out rectification, the output side can work in the no-load mode for a short time, and PW is utilizedThe M controller regulates the output voltage to control the input current, the three-mode rectifier can be periodically switched between heavy load (1 mode) and light load (2 mode), and comprises four on-chip transistors S1, S2, S3 and S4, and an off-chip capacitor C
O) As shown in fig. 1.
The switching on and off is realized by controlling the gate driving signal of the switching tube, and the specific implementation of the PWM controller will be described below. The invention adopts a 3-mode rectifier, and 2-mode (light load) is added between 1-mode (heavy load) and 3-mode (no load), so that the output voltage can be reduced to the minimum. Four equations are presented below:
I
O(1 mode) ═ I
max
I
O(2-mode) 1/2I
max
I
O(3 mode) ═ 0
I
max＝2I
ac/π
In the above formula I
maxTo the maximum output current, I
OTo output current, I
acIs the input alternating current.
Traditional rectifier output voltage ripple △ V
DCAt 0<I
o<1/2I
maxTime increase at 1/2I
max<I
o<I
maxTime reduction at 0 in a three-mode rectifier<I
o<1/4I
max、1/2I
max<I
o<3/4I
maxStep increase at 1/4I
max<I
o<1/2I
max、3/4I
max<I
o<I
maxThe stages are reduced, the output voltage ripple can be obviously reduced by switching the heavy load mode, the light load mode and the no-load mode, and meanwhile, the synchronous rectification switching is realized.
Schematic diagram and operation principle of the PWM controller are shown in fig. 5 and 6, respectively, the PWM controller senses the output voltage V
DCAnd comparing the voltage with a reference voltage, stabilizing the system by adopting fast transient response, and automatically switching the 3-mode rectifier into heavy load/light load: compensated output voltage V
EACompared with the two sawtooth wave signals Ramp1 and Ramp2, the two signals have the same amplitude and frequency, and as shown in fig. 6, the value range of the sawtooth wave Ramp1 is V
H(Heavy)～V
MID(Middle), the sawtooth wave Ramp2 takes on the value range V
MID(Middle)～V
L(Light)。
Heavy load (1/2I)
max<I
o<I
max) Mode (2): as shown in FIG. 5, the feedback loop will compensate for the output voltage V
EADriving to sawtooth wave Ramp1, comparing them, and reloading Q
HDetermining the PWM signal, as shown in FIG. 6, as a sawtooth wave<Compensated output voltage V
EAThe time rectifier works in 1 mode, sawtooth wave>Compensated output voltage V
EAThe rectifier works in a 2 mode, and the 3 mode rectifier working modes in the phase are 1 mode and 2 mode. 2 mode heavy duty cycle D
HBy compensating the output voltage V
EACompared with sawtooth wave Ramp1 to compensate output voltage V
EAThe range lower than the sawtooth wave Ramp1 is the heavy duty cycle D
H。
Light load (0)<I
o<1/2I
max) Mode (2): as shown in FIG. 5, the feedback loop will compensate for the output voltage V
EADriving to sawtooth wave Ramp2, comparing them, and making light-load quality factor Q
LDetermining the PWM signal, as shown in FIG. 6, as a sawtooth wave<Compensated output voltage V
EAThe time rectifier works in 2 mode, sawtooth wave>Compensated output voltage V
EAThe rectifier works in 3 modes, the 3-mode rectifier works in 2 and 3 modes in the phase, and the light-load duty ratio of the 2 mode is compensated by the output voltage V
EACompared with sawtooth wave Ramp2 to compensate output voltage V
EAThe range higher than the sawtooth wave Ramp2 is the light-load duty ratio D
L。
Intermediate load (V)
EA＝V
MID) Mode (2): determining the rectifier to work in a heavy load or light load mode, a heavy load quality factor Q
HOr light-load quality factor Q
LEqual to 1, the stable transition from heavy load to light load can be realized.
Example (b):
the invention relates to a multi-mode rectifier circuit, as shown in figure 1, the input voltage range of an LLC resonant converter is 360-400V, the rated input direct current voltage is 380V, the output direct current voltage is 33V, the rated output power is 900W, the number of primary and secondary turns of a transformer is respectively 16 turns,2 turns with turn ratio of 8, resonant capacitor C
r11nF, resonant inductance L
r36uH, excitation inductance L
mIt was 150 uH. The whole topological structure is divided into two parts of a primary side and a secondary side of the transformer, wherein the primary side comprises a full-bridge structure consisting of 4 MOS (metal oxide semiconductor) transistors Q1, Q2, Q3 and Q4 and an LLC (logical link control) resonant network (L)
r，C
r，L
m)。
As shown in fig. 2(a), when the LLC resonant converter is in a heavy load state, all switching tubes are controlled by the conventional frequency, and when the LLC resonant converter is in a no-load state, as shown in fig. 2(b), the switching tube control mode of the left arm is unchanged, the switching tube Q3 sets the control signal to "0", turns off the Q3, sets the control signal to "1" for Q4, and turns on the Q4.
Focusing on the embodiment of the output side, the output side adopts a 3-mode switchable rectifier, and comprises 4 synchronous rectifiers S1, S2, S3 and S4 and an off-chip capacitor C
OThe output voltage ripple is reduced, the electromagnetic interference is reduced, the synchronous rectification conversion efficiency is improved, and the system can stably run.
The operation principle of the present invention will be described below by taking a multi-mode rectifier as shown in fig. 3(a), 3(b), and 3(c) as an example.
In fig. 3(a), the mode 1 is a full-bridge structure, and there are two working states, ① when the voltage at the upper end of the secondary winding is positive, the switch tubes S1 and S4 are turned on, the secondary current passes through S1 and C
OAnd R
OS4 returns to the secondary winding, ② when the voltage at the lower end of the secondary winding is positive, the switch tubes S2 and S3 are conducted, and the secondary current passes through S3 and C
OAnd R
OS2 returns to the secondary winding again, the 2-mode switching tubes S1 and S2 have the same mode as the 1-mode switching tube, the switching tube S3 is disconnected, the S4 is normally closed, the switching tube is converted into a half-bridge structure, the structure has only one working state, and when the voltage at the upper end of the secondary winding is positive, the secondary current passes through the S1 and the C ①
OAnd R
OS4 returns to the secondary winding again, and when the voltage at the lower end of the secondary winding is positive, the secondary current does not pass through the load, and as shown in fig. 3(b), the negative half cycle of the ac waveform is cancelled, and only half of the input waveform is output. The 3 modes are that 4 switching tubes are all closed, the input current does not pass through a load end, and an output capacitor C
OIf the power supply is switched between the 1 mode and the 3 mode, the output capacitor is continuously charged in a plurality of resonant periods and continuously discharged in the next resonant periods, which results in a large output voltage ripple △ V
DC. The invention adopts a 3-mode rectifier, and 2-mode (light load) is added between 1-mode (heavy load) and 3-mode (no load), so that the output voltage can be reduced to the minimum.
FIG. 7 shows the resonant inductor current waveforms
And transformer excitation inductance current waveform
And judging the resonant frequency of the resonant converter by analyzing the current waveform.
Fig. 8 is a diagram of the dc side output voltage waveform of the multi-mode rectifier, and it can be seen from fig. 8 that the multi-mode rectifier can stabilize the output dc voltage to 33V.
FIG. 9 shows the secondary side current I of the transformer
acAnd (4) waveform diagrams.
FIG. 10 shows the output current I of the rectifier in the full bridge state
o_acAnd (4) waveform diagrams.
FIG. 11 shows the output current I of the rectifier in the half-bridge state
o_acWave diagram, when no load, the four synchronous rectifier tubes are all turned off, no current passes through, so there is no output current I of this mode
o_acThe simulation graphs verify the feasibility of the invention through the consistency of simulation waveform verification and theoretical analysis of fig. 3(a), 3(b) and 3(c), and the invention is suitable for DC-DC conversion occasions such as communication power supplies, LED driving power supplies and the like.
Claims (1)
1. A three-mode rectification topology based on an LLC resonant converter, comprising:
the full-bridge structure composed of 4 MOS transistors Q1, Q2, Q3 and Q4 and the LLC resonant converter are positioned on the primary side of the transformer T0, and the LLC resonant converter comprises a resonant inductor L
rResonant capacitor C
rTransformer excitation inductance L
m；
A 3-mode switchable rectifier on the secondary side of the transformer T0, the 3-mode switchable rectifier including 4 switching tubes S1, S2, S3, S4 and an off-chip capacitor C
O；
The method is characterized in that: signal input terminal U
inThe positive electrode of the MOS tube Q2 and the source electrode of the MOS tube Q4 are respectively connected with the drain electrode of the MOS tube Q1 and the drain electrode of the MOS tube Q3, the source electrode of the MOS tube Q1 is connected with the drain electrode of the MOS tube Q2, the source electrode of the MOS tube Q3 is connected with the drain electrode of the MOS tube Q4, and the source electrodes of the MOS tube Q2 and the MOS tube Q4 are both connected with a signal input end U
in-a pole of (a); the source electrode of the MOS transistor Q1 is connected with a resonant capacitor C
rOne terminal, resonant capacitor C
rThe other end is connected with a transformer excitation inductor L
mOne end, transformer excitation inductance L
mThe other end is connected with the drain electrode of the MOS tube Q4;
the drain of the switch tube S1 is connected with the source of the switch tube S2, the drain of the switch tube S2 is connected with the drain of the switch tube S4, the source of the switch tube S4 is connected with the drain of the switch tube S3, and the source of the switch tube S3 is connected with the source of the switch tube S1;
the drain electrode of the switch tube S1 and the source electrode of the switch tube S4 are respectively connected with two ends of the secondary side of the transformer T0;
the source of the switch tube S3 and the drain of the switch tube S4 are respectively connected with the external capacitor C
OBoth ends of (a);
the topological structure output side adopts a 3-mode switchable rectifier which is divided into a heavy-load mode, a light-load mode and a no-load mode, and the 3-mode switchable rectifier comprises 4 switching tubes S1, S2, S3 and S4 and an off-chip capacitor C
OThe heavy load, light load and no-load modes of the rectifier are adjusted by adopting Pulse Width Modulation (PWM);
the heavy-load mode is a full-bridge structure and has two working states, ① when the voltage at the upper end of the secondary winding is positive, the switch tubes S1 and S4 are conducted, the secondary current passes through S1 and C
OAnd R
OS4 returns to the secondary winding, ② when the voltage at the lower end of the secondary winding is positive, the switch tubes S2 and S3 are conducted, and the secondary current passes through S3 and C
OAnd R
OS2 returns to the secondary winding again;
the light-load mode switching tubes S1 and S2 are the same as the heavy-load mode, the switching tube S3 is disconnected, and the switching tube S4 is normally closed, so that the light-load mode switching tubes are converted into a half-bridge junctionWhen the voltage at the upper end of the secondary winding is positive, ① the secondary current passes through S1 and C
OAnd R
OS4, returning to the secondary winding again, when the voltage at the lower end of the secondary winding is positive, the secondary current does not pass through the load, the negative half cycle of the alternating current waveform is eliminated, and only half of the input waveform is output;
the no-load mode is that 4 switching tubes are all closed, the input current does not pass through a load end, and the output capacitor C
OWhen the load is powered to be in a no-load mode, such as switching between a 1 mode and a 3 mode, the output capacitor is continuously charged in several resonant periods and continuously discharged in the next several resonant periods, which results in a large output voltage ripple △ V
DC。
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201810918522.8A CN108964474B (en) | 2018-08-13 | 2018-08-13 | Three-mode rectification topological structure based on LLC resonant converter |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201810918522.8A CN108964474B (en) | 2018-08-13 | 2018-08-13 | Three-mode rectification topological structure based on LLC resonant converter |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN108964474A CN108964474A (en) | 2018-12-07 |
| CN108964474B true CN108964474B (en) | 2020-02-11 |
Family
ID=64469053
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201810918522.8A Active CN108964474B (en) | 2018-08-13 | 2018-08-13 | Three-mode rectification topological structure based on LLC resonant converter |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN108964474B (en) |
Families Citing this family (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN109703399B (en) | 2018-12-27 | 2021-05-18 | 台达电子企业管理（上海）有限公司 | Vehicle-mounted charging and discharging system and control method applicable to same |
| CN109921670B (en) * | 2019-03-28 | 2021-01-19 | 苏州汇川联合动力系统有限公司 | Inverter control method, inverter and readable storage medium |
| CN111224555B (en) * | 2020-04-23 | 2020-08-25 | 深圳市健网科技有限公司 | Wide-range output control method of LLC resonant conversion circuit |
| CN112087140B (en) * | 2020-07-31 | 2022-01-04 | 西安电子科技大学 | Multi-mode automatic switching two-stage resonance DC-DC converter |
| CN112467891B (en) * | 2020-09-30 | 2023-05-23 | 西南交通大学 | IPT system efficiency optimization method based on full-bridge half-bridge switching |
| CN112564489B (en) * | 2020-11-03 | 2022-05-20 | 广州金升阳科技有限公司 | Mode control method of switch converter and switch converter |
| CN113114041B (en) * | 2021-04-06 | 2022-09-06 | 上海科技大学 | LLC resonant converter with improved light-load performance |
| CN113452260A (en) * | 2021-07-06 | 2021-09-28 | 安徽工业大学 | Hybrid LLC resonant converter topological structure based on working mode switching and control method |
| US11664717B2 (en) | 2021-10-26 | 2023-05-30 | Aes Global Holdings Pte Ltd. | Power converter modulation sequence |
Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104094514A (en) * | 2011-11-24 | 2014-10-08 | 保罗·瓦尔有限公司和两合公司 | Controlled rectifier with b2 bridge and only one switching device |
| CN104600992A (en) * | 2014-12-15 | 2015-05-06 | 西安华为技术有限公司 | Direct current to direct current conversion circuit |
| CN104811047A (en) * | 2014-01-27 | 2015-07-29 | 伊顿制造（格拉斯哥）有限合伙莫尔日分支机构 | Bidirectional direct-current/direct-current converter and control method thereof |
| CN105141135A (en) * | 2015-08-31 | 2015-12-09 | 天津电气科学研究院有限公司 | Control method for multi-way parallel full-bridge LLC converter in cascading power supply system |
| CN105207484A (en) * | 2015-08-31 | 2015-12-30 | 天津电气科学研究院有限公司 | Novel full-bridge LLC no-load and loaded voltage control method |
| CN106787765A (en) * | 2017-02-06 | 2017-05-31 | 山东鲁能智能技术有限公司 | The system and method for realizing ultra-wide output voltage range based on LLC topologys |
| CN108258910A (en) * | 2017-12-25 | 2018-07-06 | 浙江大学 | A kind of full-bridge LLC resonant transform circuits and its wide range output control method |
Family Cites Families (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US8295068B2 (en) * | 2010-02-02 | 2012-10-23 | National Taipei University Of Technology | Shift full bridge power converting system and control method thereof |
| US9490704B2 (en) * | 2014-02-12 | 2016-11-08 | Delta Electronics, Inc. | System and methods for controlling secondary side switches in resonant power converters |
-
2018
- 2018-08-13 CN CN201810918522.8A patent/CN108964474B/en active Active
Patent Citations (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104094514A (en) * | 2011-11-24 | 2014-10-08 | 保罗·瓦尔有限公司和两合公司 | Controlled rectifier with b2 bridge and only one switching device |
| CN104811047A (en) * | 2014-01-27 | 2015-07-29 | 伊顿制造（格拉斯哥）有限合伙莫尔日分支机构 | Bidirectional direct-current/direct-current converter and control method thereof |
| CN104600992A (en) * | 2014-12-15 | 2015-05-06 | 西安华为技术有限公司 | Direct current to direct current conversion circuit |
| CN105141135A (en) * | 2015-08-31 | 2015-12-09 | 天津电气科学研究院有限公司 | Control method for multi-way parallel full-bridge LLC converter in cascading power supply system |
| CN105207484A (en) * | 2015-08-31 | 2015-12-30 | 天津电气科学研究院有限公司 | Novel full-bridge LLC no-load and loaded voltage control method |
| CN106787765A (en) * | 2017-02-06 | 2017-05-31 | 山东鲁能智能技术有限公司 | The system and method for realizing ultra-wide output voltage range based on LLC topologys |
| CN108258910A (en) * | 2017-12-25 | 2018-07-06 | 浙江大学 | A kind of full-bridge LLC resonant transform circuits and its wide range output control method |
Non-Patent Citations (2)
| Title |
|---|
| LLC Resonant Converter With Semiactive Variable-Structure Rectifier;Hongfei Wei, et al;《IEEE Transactions on Power Electronics》;20160531;第31卷(第5期);第3389-3394页 * |
| 并联全桥LLC谐振变换器直流母线电压控制方法;李国栋，等;《电力系统及其自动化学报》;20171015;第29卷(第10期);第60-64页 * |
Also Published As
| Publication number | Publication date |
|---|---|
| CN108964474A (en) | 2018-12-07 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN108964474B (en) | Three-mode rectification topological structure based on LLC resonant converter | |
| CN109889047B (en) | Two-stage DC-DC converter suitable for wide input and output voltage range | |
| CN110365205B (en) | High-efficiency totem-pole bridgeless PFC rectifier control method | |
| WO2021184603A1 (en) | Dcdc conversion circuit capable of pre-charging | |
| CN105305829B (en) | The unidirectional DC DC converters of current mode and symmetric double PWM add phase-shifting control method | |
| WO2023098218A1 (en) | Wide-range resonant soft-switching bidirectional direct-current converter, and control method therefor | |
| CN111010043B (en) | Full-bridge LLC resonant converter fixed-frequency control method | |
| WO2008113242A1 (en) | A switched dc-dc conversion system for isolating high frequency and a method thereof | |
| CN103441680B (en) | A kind of soft switching full-bridge direct-current converter reducing circulation loss | |
| CN112436728B (en) | High-efficiency control method of bidirectional resonant converter | |
| CN113489309B (en) | Bridgeless buck power factor correction converter with wide output voltage and control method | |
| CN114301300A (en) | Wide-range bidirectional resonant soft-switching direct-current converter and control method thereof | |
| WO2024060728A1 (en) | Bidirectional power conversion apparatus and control method therefor, and computer device and computer-readable storage medium | |
| WO2013075401A1 (en) | Power supply circuit | |
| CN110611444B (en) | Bridgeless integrated AC-DC (alternating current-direct current) rectifying circuit and rectifying method | |
| CN217087777U (en) | Wide-range resonant soft-switching bidirectional direct-current converter | |
| CN104065283B (en) | No bridge type PFC AC DC supply convertors | |
| TWI807472B (en) | Converter for a wide range of output voltage and control method thereof | |
| CN109698627B (en) | Full-bridge DC/DC converter based on switched capacitor and modulation strategy thereof | |
| CN110445387B (en) | Topological structure and control method of formation and grading power supply | |
| CN106787756B (en) | A kind of CL-FT-CL resonance DC converter | |
| CN109546861B (en) | Method for dynamically adjusting voltage conversion rate of LLC resonant cavity | |
| CN115811241A (en) | Single-stage bridgeless staggered parallel Boost-LLC AC-DC converter hybrid control method | |
| CN112366947A (en) | Control circuit of high-gain LLC resonant converter | |
| Wen et al. | The Hybrid Control Strategy for The Wide Input of The LLC Converter |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |