CN108880297B - Phase compensation device and method based on Vienna rectifier - Google Patents

Phase compensation device and method based on Vienna rectifier Download PDF

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CN108880297B
CN108880297B CN201810697120.XA CN201810697120A CN108880297B CN 108880297 B CN108880297 B CN 108880297B CN 201810697120 A CN201810697120 A CN 201810697120A CN 108880297 B CN108880297 B CN 108880297B
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CN108880297A (en
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吕建国
范林勇
阎亦然
胡文斌
季振东
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Nanjing University of Science and Technology
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Nanjing University of Science and Technology
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
    • H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
    • H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only

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Abstract

The invention discloses a phase compensation device and method based on a Vienna rectifier. The device comprises a Vienna rectifier, a digital processing control module and a driving circuit. The method comprises the following steps: sampling three-phase voltage at the alternating current side, and calculating compensation coefficients of all phases; sampling three-phase current at the alternating current side, and calculating a three-phase compensation signal; sampling the voltage of upper and lower capacitors on the direct current side, and calculating the output signal of the midpoint voltage control unit; adding the three-phase current at the alternating current side with the output signal of the midpoint voltage control unit and the three-phase compensation signal to obtain a modulation signal; sampling the voltage of an upper capacitor and a lower capacitor on the direct current side, and calculating the amplitude of a carrier signal to obtain a triangular carrier signal; the modulation signal and the triangular carrier signal are processed to obtain a pulse width modulation signal, and the Vienna rectifier switching tube is driven to work. The invention has low hardware cost, accurate control and wide application range, effectively solves the problem of phase shift between the alternating-current side voltage and the current of the Vienna rectifier when the input is unbalanced, and reduces the total harmonic distortion rate of the alternating-current side current.

Description

Phase compensation device and method based on Vienna rectifier
Technical Field
The invention belongs to the technical field of power electronic conversion, and particularly relates to a phase compensation device and method based on a Vienna rectifier.
Background
The Vienna rectifier is a three-level topology, and has the advantages of low voltage stress borne by power switches, small number of power switches, high power density, low input current harmonic content and good adaptability to various PFC control methods, so that the Vienna rectifier is widely applied to the research of power factor correction technology. Meanwhile, in recent years, many documents deeply research a three-phase PFC rectifier based on single-cycle control, a controller for single-cycle control generally does not need a multiplier, only needs to perform simple integration and addition and subtraction operation on input current, and can realize a switching element control waveform with constant modulation frequency by directly comparing the input current with a reference signal. The traditional single-period control can realize that the input current and the input voltage are in the same phase under the condition of balanced input, but under the condition of unbalanced input, the traditional single-period control can cause the input current and the input voltage to generate phase shift, and the target of unit power factor control cannot be achieved.
The unbalance of three-phase input alternating-current voltage is a special phenomenon in a rectifier power supply system, and can affect the normal operation of the rectifier power supply system, for example, the problems of output direct-current voltage low-frequency pulsation, input power low-frequency pulsation, input current distortion and the like can be caused. For the problems of unbalanced three-phase input ac voltage and phase compensation, document 1(Jin Aijuan, Li Hangtian, Li sharp, and improved one-cycle controlled three-phase PFC receiver under balanced control [ J ]. Transactions of Chinese electronic technical Society,2006,21(7): 115-. Document 2 (wegener. aviation intermediate frequency high power factor rectifier research [ D ]. nanjing aerospace university, 2014.) suppresses dc side fluctuations from unbalanced voltages by adding a resonant controller after the voltage regulator, but there is still a phase shift between the input current and the input voltage.
Disclosure of Invention
The invention aims to provide a Vienna rectifier-based phase compensation device and method which are simple and reliable in operation and accurate in control, and the device and method can realize zero phase difference of input voltage and current of each phase when input is unbalanced, realize unit power factor operation and reduce the total harmonic distortion rate of alternating current side current.
The technical solution for realizing the purpose of the invention is as follows: a phase compensation device based on a Vienna rectifier comprises the Vienna rectifier, a digital processing control module and a driving circuit, wherein the digital processing control module comprises a sampling unit, an orthogonal signal generator unit of a second-order generalized integrator, a direct current voltage stabilization control unit, a midpoint voltage control unit, a carrier generation unit, a sine pulse width modulation unit and a compensation coefficient calculation unit;
the sampling unit is used for respectively acquiring upper and lower capacitor voltage signals on the direct current side of the Vienna rectifier, three-phase voltage signals on the alternating current side of the Vienna rectifier and three-phase current signals on the alternating current side of the Vienna rectifier, and respectively sending the three-phase voltage signals to the compensation coefficient calculation unit, the orthogonal signal generator unit of the second-order generalized integrator, the midpoint voltage control unit and the direct current voltage stabilization control unit; the compensation coefficient calculation unit calculates a phase shift compensation coefficient of the voltage and the current on the AC side according to the three-phase voltage signals on the AC side obtained by sampling; the quadrature signal generator unit of the second-order generalized integrator lags the three-phase current signals obtained by sampling by 90 degrees, and multiplies the signals by respective phase shift compensation coefficients to obtain three-phase compensation signals; the midpoint voltage control unit obtains an output signal of the midpoint voltage control unit according to the sampled upper and lower capacitor voltage signals on the direct current side, adds the signal and the sampled three-phase current on the alternating current side respectively, and adds the three-phase compensation signal to obtain a modulation signal; the direct current voltage stabilization control unit obtains the amplitude of a carrier signal according to the sampled upper and lower capacitor voltages on the direct current side, and then sends the amplitude to the carrier generation unit to obtain a triangular carrier signal; and the modulation signal and the triangular carrier signal are sent to a sinusoidal pulse width modulation unit, and the output end of the sinusoidal pulse width modulation unit is connected to each switching tube of each phase of bridge arm in the Vienna rectifier through a driving circuit.
Further, the digital processing control modules are chips of TMS320F28335 and EPM 1270T.
A phase compensation method based on a Vienna rectifier comprises the following core control equations:
Figure BDA0001713850810000021
the method specifically comprises the following steps:
step 1, a sampling unit samples three-phase voltage e at an alternating current sidea、eb、ecAlternating side three-phase current ia、ib、icCapacitor voltage U on the DC sideC1Lower capacitor voltage U on the DC sideC2；
Step 2, detecting three-phase voltage e at alternating current sidea、eb、ecZero-crossing point of (d), and ea、eb、ecThe amplitude of (d);
step 3, according to the three-phase voltage e of the alternating current sidea、eb、ecZero crossing point of (d) and (e)a、eb、ecJudging whether the power grid changes in the operation process of the system, and calculating to obtain the phase shift angle alpha between the voltage and the current of each cross current side1、α2、α3According to
Figure BDA0001713850810000031
Separately determining the compensation coefficients ka、kb、kc；
Step 4, sampling three-phase current ia、ib、icAre respectively multiplied by sampling coefficients RsTo obtain iaRs、ibRs、icRsSending the signal to a quadrature signal generator unit of a second-order generalized integrator to obtain signals with phase lags by 90 degrees and multiplying the signals by a compensation coefficient k respectivelya、kb、kcObtaining a three-phase compensation signal-jkaiaRs、-jkbibRs、-jkcicRs；
Step 5, sampling the i obtained in the step 4aRs、ibRs、icRsAnd the middle pointOutput u of voltage control unitfAdd to obtain iaRs+uf、ibRs+uf、icRs+uf；
Step 6, the three-phase compensation signal-jk obtained in the step 4 is usedaiaRs、-jkbibRs、-jkcicRsAnd i obtained in step 5aRs+uf、ibRs+uf、icRs+ufAdding the three phases of modulation signals respectively to obtain three-phase modulation signals;
step 7, adding the sampled upper and lower capacitor voltages, sending the added voltages to a direct current voltage stabilization control unit to obtain a triangular carrier amplitude, and then obtaining a triangular carrier signal through a carrier generation unit;
and 8, connecting the three-phase modulation signal obtained in the step 6 with the triangular carrier signal obtained in the step 7 to generate a pulse width modulation signal, and controlling the switch tube of the Vienna rectifier to work through a driving circuit.
Further, the step 3 is based on the three-phase voltage e of the alternating sidea、eb、ecZero crossing point of (d) and (e)a、eb、ecThe amplitude value of the power grid is judged to be changed or not in the running process of the system, and the method specifically comprises the following steps:
step 3.1, sampling three-phase power grid voltage at the alternating current side, and calculating compensation coefficients of all phases;
step 3.2, setting the maximum allowable error angle of each phase
Figure BDA0001713850810000032
Measuring the zero crossing point of each phase voltage in the first power frequency period
Figure BDA0001713850810000033
Then, the zero crossing point of each phase voltage is detected in each power frequency period, and the zero crossing point of the kth period is set as
Figure BDA0001713850810000034
Will be compared with the zero crossing point of the previous cycle
Figure BDA0001713850810000035
Make a comparison if
Figure BDA0001713850810000036
Where x is a, b, c, the compensation coefficient k needs to be recalculateda、kb、kcSkipping to step 3.1; if it is
Figure BDA0001713850810000037
If the phase position of the grid voltage does not change between the kth period and the kth-1 period, the step 3.3 is carried out;
step 3.3, setting the maximum allowable error amplitude E of each phaseerroMeasuring the amplitude of the grid voltage in the kth period, comparing the amplitude with the amplitude of the kth-1 period, and determining if the amplitude is Exk-Ex(k-1)|<EerroIf x is a, b and c, the voltage of the power grid is not changed, and the next power frequency period is started; on the contrary, if | Exk-Ex(k-1)|>EerroIf the grid voltage changes, the compensation coefficient k needs to be recalculateda、kb、kcAnd skipping to step 3.1.
Further, the phase shift angle α between the voltage and the current at each cross current side is obtained by the calculation in step 31、α2、α3According to
Figure BDA0001713850810000041
Separately determining the compensation coefficients ka、kb、kcThe method comprises the following steps:
in each switching period, the three-phase grid voltage e of the alternating current side is obtained according to sampling of the sampling unita、eb、ecCalculating to obtain the zero sequence component e of the AC side three-phase grid voltage according to a symmetrical component methodo；
Defining the three-phase network voltage e on the AC sidea、eb、ecThe following were used:
Figure BDA0001713850810000042
wherein U isa、Ub、UcRespectively representing phase voltage amplitudes of a phase, b phase and c phase,
Figure BDA0001713850810000043
representing phase voltage initial phase angles of a phase, b phase and c phase respectively; omega represents the fundamental wave angular speed of the power grid, and t represents time;
according to the symmetrical component method, the zero sequence component e of the three-phase network voltage on the AC sideoComprises the following steps:
Figure BDA0001713850810000044
according to ex＝exno+eoAnd x is a, b and c, and obtaining a non-zero-sequence component e of the three-phase grid voltage on the alternating current sideano、ebno、ecnoComprises the following steps:
Figure BDA0001713850810000045
obtaining the initial phase angle of the non-zero sequence component of the network voltage according to the information of the three-phase network voltage at the AC side
Figure BDA0001713850810000046
Figure BDA0001713850810000047
Figure BDA0001713850810000051
Wherein:
Figure BDA0001713850810000052
then according to:
Figure BDA0001713850810000053
obtaining the phase angle offset of each phase;
finally according to
Figure BDA0001713850810000054
Respectively calculating the compensation coefficient k of each phasea、kb、kc。
Compared with the prior art, the invention has the remarkable advantages that: (1) the same phase of the input current and the input voltage is realized by sampling the three-phase voltage at the alternating current side and calculating the phase compensation coefficient of each phase, and the problem of phase shift between the voltage and the current at the alternating current side of the Vienna rectifier when the input is unbalanced is effectively solved; (2) the total harmonic distortion rate of the alternating current side current is reduced by introducing the midpoint voltage control unit, and the waveform quality is improved; (3) the method is suitable for the conditions of input balance and input unbalance, and has the advantages of simple and reliable operation, low hardware cost, accurate control and wide application range.
Drawings
Fig. 1 is a schematic structural diagram of a Vienna rectifier-based phase compensation device of the present invention.
Fig. 2 is a schematic diagram of a quadrature signal generator unit of the second-order generalized integrator.
Fig. 3 is a topology diagram of a Vienna rectifier.
Fig. 4 is a flowchart of the compensation coefficient calculation in the present invention.
Fig. 5 is a waveform diagram of an a-phase input voltage, an input current, and a modulation wave under conventional one-cycle control.
Fig. 6 is a graph of an input imbalance voltage waveform.
Fig. 7 is a waveform diagram of the a-phase input voltage, the input current and the modulation wave after the Vienna rectifier-based phase compensation method of the invention is used.
Fig. 8 is a graph comparing the magnitude of the phase shift angle between the a-phase voltage and the a-phase current at the ac side before and after the method of the present invention is used, wherein (a) is a graph showing the magnitude of the phase shift angle between the a-phase voltage and the a-phase current at the ac side when the input is unbalanced using the conventional single cycle control, and (b) is a graph showing the magnitude of the phase shift angle between the a-phase voltage and the a-phase current at the ac side when the input is unbalanced using the method of the present invention.
Fig. 9 is a comparison graph of the harmonic distribution of the ac side current before and after the method of the present invention, where (a) is the harmonic distribution of the ac side current before the control method of the present invention, and (b) is the harmonic distribution of the ac side current after the control method of the present invention.
Detailed Description
With reference to fig. 1, 2, and 3, the phase compensation apparatus based on a Vienna rectifier of the present invention includes a Vienna rectifier, a digital processing control module, and a driving circuit, wherein the digital processing control module includes a sampling unit, a Quadrature Signal Generator unit (SOGI-QSG) of a Second-Order Generalized Integrator, a dc voltage stabilization control unit, a midpoint voltage control unit, a carrier generation unit, a sine pulse width modulation unit, and a compensation coefficient calculation unit;
the quadrature signal generator unit (SOGI-QSG) of the second order generalized integrator is shown in fig. 2, where V is the input signal, V 'is the signal in phase with V, qV' is the signal lagging by V90 °, and ω is the fundamental angular velocity of the input signal.
The sampling unit is used for respectively acquiring upper and lower capacitor voltage signals on the direct current side of the Vienna rectifier, three-phase voltage signals on the alternating current side of the Vienna rectifier and three-phase current signals on the alternating current side of the Vienna rectifier, and respectively sending the three-phase voltage signals to the compensation coefficient calculation unit, the orthogonal signal generator unit of the second-order generalized integrator, the midpoint voltage control unit and the direct current voltage stabilization control unit; the compensation coefficient calculation unit calculates a phase shift compensation coefficient of the voltage and the current on the AC side according to the three-phase voltage signals on the AC side obtained by sampling; the quadrature signal generator unit of the second-order generalized integrator lags the three-phase current signals obtained by sampling by 90 degrees, and multiplies the signals by respective phase shift compensation coefficients to obtain three-phase compensation signals; the midpoint voltage control unit obtains an output signal of the midpoint voltage control unit according to the sampled upper and lower capacitor voltage signals on the direct current side, adds the signal and the sampled three-phase current on the alternating current side respectively, and adds the three-phase compensation signal to obtain a modulation signal; the direct current voltage stabilization control unit obtains the amplitude of a carrier signal according to the sampled upper and lower capacitor voltages on the direct current side, and then sends the amplitude to the carrier generation unit to obtain a triangular carrier signal; and the modulation signal and the triangular carrier signal are sent to a sinusoidal pulse width modulation unit, and the output end of the sinusoidal pulse width modulation unit is connected to each switching tube of each phase of bridge arm in the Vienna rectifier through a driving circuit.
As a specific example, the digital processing control modules are TMS320F28335 and EPM1270T chips.
The invention relates to a phase compensation method based on a Vienna rectifier, which specifically comprises the following steps:
step 1, in each switching period, a sampling unit of a digital processing control module respectively samples three-phase voltage e at an alternating current sidea、eb、ecAlternating side three-phase current ia、ib、icCapacitor voltage U on the DC sideC1Lower capacitor voltage U on the DC sideC2；
Step 2, detecting three-phase voltage e at alternating current sidea、eb、ecZero-crossing point of (d), and ea、eb、ecThe amplitude of (d);
step 3, according to the three-phase voltage e of the alternating current sidea、eb、ecZero crossing point of (d) and (e)a、eb、ecJudging whether the power grid changes in the operation process of the system, and calculating to obtain the phase shift angle alpha between the voltage and the current of each cross current side1、α2、α3According to
Figure BDA0001713850810000071
Separately determining the compensation coefficients ka、kb、kcThe method comprises the following steps:
step 3.1, firstly, judging the running state of the power grid, and calculating a compensation coefficient k according to the specific running state of the power grida、kb、kcWith reference to fig. 4, the specific steps are as follows:
step 3.1.1, sampling three-phase power grid voltage at the alternating current side, and calculating compensation coefficients of all phases;
step 3.1.2, setting the maximum allowable error angle of each phase
Figure BDA0001713850810000072
Measuring the zero crossing point of each phase voltage in the first power frequency period
Figure BDA0001713850810000073
Then, the zero crossing point of each phase voltage is detected in each power frequency period, and the zero crossing point of the kth period is set as
Figure BDA0001713850810000074
Will be compared with the zero crossing point of the previous cycle
Figure BDA0001713850810000075
Make a comparison if
Figure BDA0001713850810000076
Wherein x is a, b, c, and the compensation coefficient k is recalculateda、kb、kcSkipping to step 3.1.1; if it is
Figure BDA0001713850810000077
The phase of the grid voltage does not change between the kth period and the kth-1 period, and the step 1.3 is carried out;
step 3.1.3, setting the maximum allowable error amplitude E of each phaseerroMeasuring the amplitude of the grid voltage in the kth period, comparing the amplitude with the amplitude of the kth-1 period, and determining if the amplitude is Exk-Ex(k-1)|<Eerro(where x is a, b, c), the grid voltage is noIf the change occurs, entering the next power frequency period; on the contrary, if | Exk-Ex(k-1)|>EerroIf the grid voltage changes, the compensation coefficient k needs to be recalculateda、kb、kcAnd skipping to step 3.1.1.
Step 3.2, in each switching period, obtaining three-phase power grid voltage e on the alternating current side according to sampling of the sampling unita、eb、ecAnd calculating to obtain the zero sequence component e of the AC side three-phase grid voltage according to a symmetrical component methodo；
Defining the three-phase network voltage e on the AC sidea、eb、ecThe following were used:
Figure BDA0001713850810000081
wherein U isa、Ub、UcRespectively representing phase voltage amplitudes of a phase, b phase and c phase,
Figure BDA0001713850810000082
representing phase voltage initial phase angles of a phase, b phase and c phase respectively;
according to the symmetrical component method, the zero sequence component of the three-phase grid voltage at the alternating current side is as follows:
Figure BDA0001713850810000083
according to ex＝exno+eoThe non-zero-sequence component of the three-phase grid voltage on the alternating-current side is obtained by (x ═ a, b and c):
Figure BDA0001713850810000084
obtaining an initial phase angle of a non-zero-sequence component of the grid voltage according to the information of the three-phase grid voltage at the alternating current side:
Figure BDA0001713850810000085
wherein:
Figure BDA0001713850810000091
then according to:
Figure BDA0001713850810000092
obtaining the phase angle offset of each phase, and finally obtaining the phase angle offset according to ka＝tan(α1)、kb＝tan(α2)、kc＝tan(α3) Respectively calculating the compensation coefficient k of each phasea、kb、kc。
Step 4, sampling three-phase current ia、ib、icAre respectively multiplied by sampling coefficients RsTo obtain iaRs、ibRs、icRsSending the signal to a quadrature signal generator unit of a second-order generalized integrator to obtain signals with phase lags by 90 degrees and multiplying the signals by a compensation coefficient k respectivelya、kb、kcObtaining a three-phase compensation signal-jkaiaRs、-jkbibRs、-jkcicRs；
Step 5, sampling the i obtained in the step 4aRs、ibRs、icRsAnd the output u of the midpoint voltage control unitfAdd to obtain iaRs+uf、ibRs+uf、icRs+uf；
Step 6, the three-phase compensation signal-jk obtained in the step 4 is usedaiaRs、-jkbibRs、-jkcicRsAnd i obtained in step 5aRs+uf、ibRs+uf、icRs+ufRespectively added to obtain three-phase modulation signals；
Step 7, adding the sampled upper and lower capacitor voltages, sending the added voltages to a direct current voltage stabilization control unit to obtain a triangular carrier amplitude, and then obtaining a triangular carrier signal through a carrier generation unit;
and 8, connecting the three-phase modulation signal obtained in the step 6 with the triangular carrier signal obtained in the step 7 to generate a pulse width modulation signal, and controlling the switch tube of the Vienna rectifier to work through a driving circuit.
The core control equation for improving the one-cycle control at this time is as follows:
Figure BDA0001713850810000093
the modulation rule of the Vienna rectifier is: as shown in FIG. 5, taking phase A as an example, in the positive half cycle of the modulated wave, when the carrier wave is larger than the modulated wave, S is seta1、Sa2Conducting, the voltage of the A-phase bridge arm is 0, and when the carrier wave is less than the modulation wave, making Sa1、Sa2Turn off, the A phase bridge arm voltage is V DC2; in the negative half cycle of the modulated wave, when the carrier wave is smaller than the modulated wave, let Sa1、Sa2Conducting, the voltage of the A-phase bridge arm is 0, and when the carrier wave is greater than the modulation wave, making Sa1、Sa2Turn off, the A phase bridge arm voltage is-VDC/2. B. The modulation strategy of the C two phases is the same as that of the A phase.
Wherein VDCThe voltage is the voltage of a direct current bus at the output side of the Vienna rectifier.
Example 1
In this embodiment, a three-phase Vienna rectifying circuit is built by using a Simulink tool in MATLAB, and the input voltage is rectified by the three-phase Vienna rectifying circuit to obtain direct current. The electrical parameter settings during the simulation are as in table 1:
TABLE 1
Figure BDA0001713850810000101
Table 1 shows Simulink simulation parameters, in order to unbalance the input voltage, the amplitude of the B-phase of the input voltage is reduced by 20%, the phase of the C-phase is delayed by 30 °, fig. 6 is a waveform diagram of the input unbalanced voltage, the amplitude of the B-phase of the input voltage is reduced by 20%, the phase of the C-phase is delayed by 30 °, fig. 5 is a waveform diagram of the input voltage, the input current and the modulation wave of the a-phase under the conventional single-cycle control, and fig. 7 is a waveform diagram of the input voltage, the input current and the modulation wave of the a-phase after the control method of the present invention.
Fig. 8 is a schematic diagram of the phase shift angle between the voltage and the current on the front and rear ac sides using the control method of the present invention under the electrical parameters, wherein (a) is a waveform diagram under the conventional single-cycle control, and the phase shift angle is 14.1 °, and (b) is a waveform diagram of the voltage and the current after the control method of the present invention, and the phase shift angle is 4.4 °. Fig. 9 (a) and (b) show the total harmonic distortion of the grid-side current before and after the compensation control method of the present invention, wherein (a) is the ac-side current harmonic distribution diagram before the control method of the present invention is used, and (b) is the ac-side current harmonic distribution diagram after the control method of the present invention is used.
TABLE 2
Figure BDA0001713850810000102
It can be seen from table 2, fig. 8 and fig. 9 that the method can effectively solve the problem of phase shift between the voltage and the current of the alternating current side of the Vienna rectifier under the unbalanced power grid, and reduce the total harmonic distortion of the current of the alternating current side.
In summary, according to the phase compensation method based on the Vienna rectifier, the voltage and current phase offset angle is calculated by sampling the three-phase power grid voltage, so that the phase compensation coefficient of each phase is calculated; taking the three-phase current on the sampled alternating current side as a basic signal, delaying the basic signal by 90 degrees and respectively multiplying the basic signal by respective compensation coefficients to obtain three-phase compensation signals; adding the sampled three-phase current at the alternating current side with the output of the midpoint voltage control unit respectively, and then adding a three-phase compensation signal to obtain a modulation signal; sampling voltages of an upper capacitor and a lower capacitor on a direct current side, obtaining an amplitude value of a carrier signal through a direct current voltage stabilization control unit, and obtaining a triangular carrier signal through a carrier generation unit; the modulation signal and the triangular carrier signal are processed by the sine pulse width modulation unit to obtain a pulse width modulation signal, and then the Vienna rectifier switching tube is driven to work, so that alternating-current side voltage and current phase compensation is realized, the harmonic wave of the current is effectively reduced, the waveform quality is improved, the unit power operation of the three-phase Vienna rectifier is favorably realized, a certain theoretical basis is provided for the fields of active power factor correction and the like, and the method has great engineering application value.

Claims (5)

1. A phase compensation device based on a Vienna rectifier is characterized by comprising the Vienna rectifier, a digital processing control module and a driving circuit, wherein the digital processing control module comprises a sampling unit, a quadrature signal generator unit of a second-order generalized integrator, a direct current voltage stabilization control unit, a midpoint voltage control unit, a carrier generation unit, a sine pulse width modulation unit and a compensation coefficient calculation unit;
the sampling unit respectively collects voltage signals of an upper capacitor and a lower capacitor on the direct current side of the Vienna rectifier and sends the voltage signals to the midpoint voltage control unit on one hand and the direct current voltage stabilization control unit on the other hand; the sampling unit is also used for acquiring a three-phase voltage signal at the alternating current side of the Vienna rectifier and sending the three-phase voltage signal to the compensation coefficient calculation unit, and acquiring a three-phase current signal at the alternating current side of the Vienna rectifier and sending the three-phase current signal to the orthogonal signal generator unit of the second-order generalized integrator; the compensation coefficient calculation unit calculates a phase shift compensation coefficient of the voltage and the current on the AC side according to the three-phase voltage signals on the AC side obtained by sampling; the quadrature signal generator unit of the second-order generalized integrator lags the three-phase current signals obtained by sampling by 90 degrees, and multiplies the signals by respective phase shift compensation coefficients to obtain three-phase compensation signals; the midpoint voltage control unit obtains an output signal of the midpoint voltage control unit according to the sampled upper and lower capacitor voltage signals on the direct current side, adds the signal and the sampled three-phase current on the alternating current side respectively, and adds the three-phase compensation signal to obtain a modulation signal; the direct current voltage stabilization control unit obtains the amplitude of a carrier signal according to the sampled upper and lower capacitor voltages on the direct current side, and then sends the amplitude to the carrier generation unit to obtain a triangular carrier signal; and the modulation signal and the triangular carrier signal are sent to a sinusoidal pulse width modulation unit, and the output end of the sinusoidal pulse width modulation unit is connected to each switching tube of each phase of bridge arm in the Vienna rectifier through a driving circuit.
2. The Vienna rectifier based phase compensation device of claim 1, wherein the digital processing control modules are TMS320F28335 and EPM1270T chips.
3. A phase compensation method based on a Vienna rectifier is characterized in that a core control equation of the method is as follows:
Figure FDA0002692610640000011
the method specifically comprises the following steps:
step 1, a sampling unit samples three-phase voltage e at an alternating current sidea、eb、ecAlternating side three-phase current ia、ib、icCapacitor voltage U on the DC sideC1Lower capacitor voltage U on the DC sideC2；
Step 2, detecting three-phase voltage e at alternating current sidea、eb、ecZero-crossing point of (d), and ea、eb、ecThe amplitude of (d);
step 3, according to the three-phase voltage e of the alternating current sidea、eb、ecZero crossing point of (d) and (e)a、eb、ecJudging whether the power grid changes in the operation process of the system, and calculating to obtain the phase shift angle alpha between the voltage and the current of each cross current side1、α2、α3According to
Figure FDA0002692610640000021
Separately determining the compensation coefficients ka、kb、kc；
Step 4, sampling three-phase current ia、ib、icAre respectively multiplied by sampling coefficients RsTo obtain iaRs、ibRs、icRsSending the signal to a quadrature signal generator unit of a second-order generalized integrator to obtain signals with phase lags by 90 degrees and multiplying the signals by a compensation coefficient k respectivelya、kb、kcObtaining a three-phase compensation signal-jkaiaRs、-jkbibRs、-jkcicRs；
Step 5, sampling the i obtained in the step 4aRs、ibRs、icRsAnd the output u of the midpoint voltage control unitfAdd to obtain iaRs+uf、ibRs+uf、icRs+uf；
Step 6, the three-phase compensation signal-jk obtained in the step 4 is usedaiaRs、-jkbibRs、-jkcicRsAnd i obtained in step 5aRs+uf、ibRs+uf、icRs+ufAdding the three phases of modulation signals respectively to obtain three-phase modulation signals;
step 7, sampling the capacitor voltage U on the direct current sideC1The capacitor voltage U under the DC sideC2Adding, sending to a direct current voltage stabilization control unit to obtain a triangular carrier amplitude, and then obtaining a triangular carrier signal through a carrier generation unit;
and 8, connecting the three-phase modulation signal obtained in the step 6 with the triangular carrier signal obtained in the step 7 to generate a pulse width modulation signal, and controlling the switch tube of the Vienna rectifier to work through a driving circuit.
4. Vienna rectifier-based phase supplement of claim 3The compensation method is characterized in that the compensation method is carried out in step 3 according to three-phase voltage e on the alternating current sidea、eb、ecZero crossing point of (d) and (e)a、eb、ecThe amplitude value of the power grid is judged to be changed or not in the running process of the system, and the method specifically comprises the following steps:
step 3.1, sampling three-phase power grid voltage at the alternating current side, and calculating compensation coefficients of all phases;
step 3.2, setting the maximum allowable error angle of each phase
Figure FDA0002692610640000022
Measuring the zero crossing point of each phase voltage in the first power frequency period
Figure FDA0002692610640000023
Then, the zero crossing point of each phase voltage is detected in each power frequency period, and the zero crossing point of the kth period is set as
Figure FDA0002692610640000024
Will be compared with the zero crossing point of the previous cycle
Figure FDA0002692610640000025
Make a comparison if
Figure FDA0002692610640000026
Where x is a, b, c, the compensation coefficient k needs to be recalculateda、kb、kcSkipping to step 3.1; if it is
Figure FDA0002692610640000027
If the phase position of the grid voltage does not change between the kth period and the kth-1 period, the step 3.3 is carried out;
step 3.3, setting the maximum allowable error amplitude E of each phaseerroMeasuring the amplitude of the grid voltage in the kth period, comparing the amplitude with the amplitude of the kth-1 period, and determining if the amplitude is Exk-Ex(k-1)|<EerroWhere x is a, b, c, the grid voltage is unchanged, andentering the next power frequency period; on the contrary, if | Exk-Ex(k-1)|>EerroIf the grid voltage changes, the compensation coefficient k needs to be recalculateda、kb、kcAnd skipping to step 3.1.
5. The Vienna rectifier-based phase compensation method of claim 3, wherein the calculation in step 3 yields the phase shift angle α between the voltage and current on each cross current side1、α2、α3According to
Figure FDA0002692610640000031
Separately determining the compensation coefficients ka、kb、kcThe method comprises the following steps:
in each switching period, the three-phase grid voltage e of the alternating current side is obtained according to sampling of the sampling unita、eb、ecCalculating to obtain the zero sequence component e of the AC side three-phase grid voltage according to a symmetrical component methodo；
Defining the three-phase network voltage e on the AC sidea、eb、ecThe following were used:
Figure FDA0002692610640000032
wherein U isa、Ub、UcRespectively representing phase voltage amplitudes of a phase, b phase and c phase,
Figure FDA0002692610640000033
representing phase voltage initial phase angles of a phase, b phase and c phase respectively; omega represents the fundamental wave angular speed of the power grid, and t represents time;
according to the symmetrical component method, the zero sequence component e of the three-phase network voltage on the AC sideoComprises the following steps:
Figure FDA0002692610640000034
according to ex＝exno+eoAnd x is a, b and c, and obtaining a non-zero-sequence component e of the three-phase grid voltage on the alternating current sideano、ebno、ecnoComprises the following steps:
Figure FDA0002692610640000035
obtaining the initial phase angle of the non-zero sequence component of the network voltage according to the information of the three-phase network voltage at the AC side
Figure FDA0002692610640000036
Figure FDA0002692610640000037
Figure FDA0002692610640000041
Wherein:
Figure FDA0002692610640000042
then according to:
Figure FDA0002692610640000043
obtaining the phase angle offset of each phase;
finally according to
Figure FDA0002692610640000044
Respectively calculating the compensation coefficient k of each phasea、kb、kc。
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