CN108306508B - High boost type direct current conversion circuit with power factor correction function - Google Patents
High boost type direct current conversion circuit with power factor correction function Download PDFInfo
- Publication number
- CN108306508B CN108306508B CN201810130718.0A CN201810130718A CN108306508B CN 108306508 B CN108306508 B CN 108306508B CN 201810130718 A CN201810130718 A CN 201810130718A CN 108306508 B CN108306508 B CN 108306508B
- Authority
- CN
- China
- Prior art keywords
- transistor
- voltage
- half cycle
- electrically connected
- diode
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Images
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J9/00—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting
- H02J9/04—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source
- H02J9/06—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems
- H02J9/061—Circuit arrangements for emergency or stand-by power supply, e.g. for emergency lighting in which the distribution system is disconnected from the normal source and connected to a standby source with automatic change-over, e.g. UPS systems for DC powered loads
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/5387—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters in a bridge configuration
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/30—Systems integrating technologies related to power network operation and communication or information technologies for improving the carbon footprint of the management of residential or tertiary loads, i.e. smart grids as climate change mitigation technology in the buildings sector, including also the last stages of power distribution and the control, monitoring or operating management systems at local level
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y04—INFORMATION OR COMMUNICATION TECHNOLOGIES HAVING AN IMPACT ON OTHER TECHNOLOGY AREAS
- Y04S—SYSTEMS INTEGRATING TECHNOLOGIES RELATED TO POWER NETWORK OPERATION, COMMUNICATION OR INFORMATION TECHNOLOGIES FOR IMPROVING THE ELECTRICAL POWER GENERATION, TRANSMISSION, DISTRIBUTION, MANAGEMENT OR USAGE, i.e. SMART GRIDS
- Y04S20/00—Management or operation of end-user stationary applications or the last stages of power distribution; Controlling, monitoring or operating thereof
- Y04S20/20—End-user application control systems
Landscapes
- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Business, Economics & Management (AREA)
- Emergency Management (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a high-boost direct-current conversion circuit with power factor correction, which relates to the technical field of high-boost direct-current conversion circuits; the voltage-boosting direct-current conversion circuit comprises a voltage input control unit and a voltage temporary storage unit, wherein the voltage input control unit can be electrically connected to the high-voltage end and the battery, the voltage temporary storage unit is electrically connected to a voltage input path control unit, and the voltage temporary storage unit is discharged after receiving and storing the voltage of the high-voltage end according to the control of the voltage input control unit on the output/input path of the voltage of the high-voltage end when the voltage-boosting direct-current conversion circuit is in the on-line mode and is discharged after receiving and storing the voltage of the high-voltage end when the voltage-boosting direct-current conversion circuit is in the battery mode; the invention can reduce the whole system and the cost of the system as no booster circuit is needed.
Description
Technical Field
The invention belongs to the technical field of high-boost direct-current conversion circuits, and particularly relates to a high-boost direct-current conversion circuit with power factor correction.
Background
The uninterrupted power supply system is a voltage modulation device frequently used in electrical equipment, and is used for receiving commercial power from the uninterrupted power supply system, providing the commercial power to a carried battery and outputting the commercial power to other electrical equipment, and when the commercial power which is originally supplied is not expected to stop supplying power, the commercial power can be directly switched to the battery for supplying power, and the battery outputs power to other electrical equipment, so that unnecessary damage to the electrical equipment caused by sudden power failure is avoided.
However, in the conventional uninterruptible power system, a boost circuit (Push-Pull) connected to the battery is required to boost the voltage output by the battery through the boost circuit to reach the voltage value for driving the electrical equipment, but the conventional boost circuit needs to be additionally provided with a coil structure, so that the system volume is increased, and the cost is increased.
Therefore, how to simplify the circuit structure in the power-down system to reduce the overall volume of the system and reduce the system cost is an important problem focus.
Disclosure of Invention
The invention provides a high-boost direct current conversion circuit with power factor correction, which solves the problems of additionally arranging a boost circuit, reducing the whole volume of a system and reducing the cost of the system.
The invention relates to a high-boost direct current conversion circuit with power factor correction, which is used for a switching type power supply device, wherein the switching type power supply device comprises an on-line mode and a battery mode, and is electrically connected to a high-voltage end and a battery in a conducting manner.
The beneficial effects of the invention are as follows: the high boosting type direct current conversion circuit with the power factor correction can add the voltage temporary storage unit to the original boosting circuit, and the total output value of the voltage is improved through the charge/discharge of the voltage temporary storage unit.
Description of the drawings:
for ease of illustration, the invention is described in detail by the following detailed description and the accompanying drawings.
FIG. 1 is a circuit diagram of a high boost DC conversion circuit with PFC according to the present invention;
FIG. 2 is a circuit diagram of the high boost DC conversion circuit of FIG. 1 during a first positive half cycle;
FIG. 3 is a circuit diagram of the high boost DC conversion circuit of FIG. 1 during a second positive half cycle;
FIG. 4 is a circuit diagram of the high boost DC conversion circuit of FIG. 1 during a first on-line negative half cycle;
FIG. 5 is a circuit diagram of the high boost DC conversion circuit of FIG. 1 during a second on-line negative half cycle;
FIG. 6 is a schematic circuit diagram of the high boost DC conversion circuit of FIG. 1 during the positive half cycle of the first battery;
FIG. 7 is a schematic circuit diagram of the high boost DC conversion circuit of FIG. 1 during the positive half cycle of the second battery;
FIG. 8 is a schematic diagram of the high boost DC conversion circuit of FIG. 1 during the negative half cycle of the first battery;
FIG. 9 is a schematic diagram of the high boost DC conversion circuit of FIG. 1 during the negative half cycle of the second battery;
FIG. 10 is a circuit diagram of another high boost DC conversion circuit with PFC according to the present invention;
FIG. 11 is a schematic circuit diagram of the inverter of FIG. 10 during a first positive half cycle of inversion;
fig. 12 is a circuit schematic of the inverter of fig. 10 during a second inverting positive half cycle;
FIG. 13 is a schematic circuit diagram of the inverter of FIG. 10 during a first negative half cycle of inversion;
fig. 14 is a circuit schematic of the inverter of fig. 10 at a second negative half cycle of inversion.
In the figure: l-high voltage terminal; an N-ground terminal; VB-battery; 1-a boost type direct current conversion circuit; 11-a voltage input control unit; 12-a voltage temporary storage unit; a 2-inverter; q1-a first transistor; q2-a second transistor; q3-third transistor; q4-fourth transistor; q5-fifth transistor; q6-sixth transistors; q7-seventh transistor; q8-eighth transistors; d1-a first diode; d2—a second diode; d3-a third diode; d4—fourth diode; d5—fifth diode; d6-sixth diode; l1-a first inductor; l2-a second inductor; c1-a first capacitance; c2-a second capacitance; a C3-third capacitor; and C4-fourth capacitance.
The specific embodiment is as follows:
for the purpose of making the objects, technical solutions and advantages of the present invention more apparent, the present invention is described below by means of specific embodiments shown in the accompanying drawings. It should be understood that the description is only illustrative and is not intended to limit the scope of the invention. In addition, in the following description, descriptions of well-known structures and techniques are omitted so as not to unnecessarily obscure the present invention.
The specific implementation mode adopts the following technical scheme: for a switched power supply (UPS) having an on-line mode and a battery mode USP.
As shown in fig. 1, the switching power supply device has an on-line mode and a battery mode, and is electrically connected to a high voltage terminal L and a battery VB, wherein the boost dc conversion circuit 1 includes a voltage input control unit 11 and a voltage temporary storage unit 12. The voltage input control unit 11 is electrically connected to the high voltage terminal L and the battery VB, and when the battery VB is in an on-line mode, the voltage input control unit 11 is configured to control an output/input path of the high voltage terminal voltage of the high voltage terminal; in the battery mode, the voltage input control unit 11 controls the output/input path of the battery voltage of the battery.
The voltage temporary storage unit 12 is electrically connected to the voltage input path control unit 11, and is configured to receive and store the high voltage terminal voltage and then discharge the high voltage terminal voltage according to the control of the voltage input control unit 11 on the output/input path of the high voltage terminal voltage when the voltage temporary storage unit is in an on-line mode, so as to increase the total output value of the high voltage terminal voltage; in the battery mode, the voltage temporary storage unit 12 receives and stores the battery voltage and discharges the battery voltage according to the control of the voltage input control unit 11 on the output/input path of the battery voltage, so as to increase the total output value of the battery voltage.
The voltage input control unit 11 includes a first transistor Q1, a second transistor Q2, a third transistor Q3, a fourth transistor Q4, a fifth transistor Q5, a sixth transistor Q6, a first diode D1, a second diode D2, a third diode D3, a fourth diode D4, a fifth diode D5, a sixth diode D6, and a first inductor L1; each transistor is provided with an input end, an output end and a control end respectively; the diode is respectively provided with an input end and an output end; the voltage register unit 12 includes a first capacitor C1, a second capacitor C2 and a third capacitor C3, wherein each of the transistors may be an N-type transistor (N-Channel MOSFET) in this example.
The output end of the first diode D1 may be electrically connected to the high voltage end L and one end of the first inductor L1; the input end of the first diode D1 may be electrically connected to a voltage positive end of the battery VB and the input end of the second diode D2, and the output end of the second diode D2 may be electrically connected to one end of the first capacitor C1 and the input end of the sixth diode D6; the other end of the first capacitor C1 is electrically connected to the other end of the first inductor L1, the input end Q11 of the first transistor Q1 and the input end Q41 of the fourth transistor Q4; the output terminal Q12 of the first transistor Q1 may be electrically connected to the output terminal Q22 of the second transistor Q2; the input terminal Q21 of the second transistor Q2 may be electrically connected to the input terminal of the third diode D3, the input terminal of the fourth diode D4, and the output terminal of the sixth diode D6. The output end of the third diode D3 may be electrically connected to one end of the second capacitor C2; the other end of the second capacitor C2 is electrically connected to the output terminal Q32 of the third transistor Q3, one end of the third capacitor C3, and the ground terminal N; the input terminal Q31 of the third transistor Q3 may be electrically connected to the output terminal of the fourth diode D4. The other end of the third capacitor C3 is electrically connected to the input end of the fifth diode D5; the output terminal of the fifth diode D5 may be electrically connected to the output terminal Q62 of the sixth transistor Q6 and the output terminal Q42 of the fourth transistor Q4; the input terminal Q61 of the sixth transistor Q6 is electrically connected to the ground terminal N. The output terminal Q42 of the fourth transistor Q4 is electrically connected to the input terminal Q51 of the fifth transistor Q5. The output terminal Q52 of the fifth transistor Q5 may be electrically connected to the voltage negative terminal of the battery VB.
The online mode in this example has a first online positive half cycle, a second online positive half cycle, a first online negative half cycle, and a second online negative half cycle; the battery mode has a first battery positive half-cycle, a second battery positive half-cycle, a first battery negative half-cycle, and a second battery negative half-cycle.
As shown in fig. 2, when the switching power supply 1 is in the first positive half cycle, the control terminals of the fourth transistor Q4 and the sixth transistor Q6 are driven to be conductive by the driving signal, and the first transistor Q1, the second transistor Q2, the third transistor Q3 and the fifth transistor Q5 are not conductive;
as shown in fig. 3, when the switching power supply 1 is in the second positive line half cycle, the control ends of the first transistor Q1 and the second transistor Q2 are driven to be conductive by the driving signal, and the third transistor Q3, the fourth transistor Q4, the fifth transistor Q5 and the sixth transistor Q6 are not conductive;
as shown in fig. 4, when the switching power supply 1 is in the first line negative half cycle, the control terminals of the fourth transistor Q4 and the sixth transistor Q6 are driven to be conductive by the driving signal, and the first transistor Q1, the second transistor Q2, the third transistor Q3 and the fifth transistor Q5 are not conductive;
as shown in fig. 5, when the switching power supply 1 is in the second line negative half cycle, the control end of the fourth transistor Q4 is driven to be conductive by the driving signal, and the first transistor Q1, the second transistor Q2, the third transistor Q3, the fifth transistor Q5 and the sixth transistor Q6 are non-conductive;
as shown in fig. 6, when the switching power supply 1 is in the positive half cycle of the first battery, the control terminals of the fourth transistor Q4 and the fifth transistor Q5 are driven to be conductive by the driving signal, and the first transistor Q1, the second transistor Q2, the third transistor Q3 and the sixth transistor Q6 are not conductive;
as shown in fig. 7, when the switching power supply 1 is in the positive half cycle of the second battery, the control terminals of the fifth transistor Q5 and the sixth transistor Q6 are driven to be conductive by the driving signal, and the first transistor Q1, the second transistor Q2, the third transistor Q3 and the fourth transistor Q4 are not conductive;
as shown in fig. 8, when the switching power supply 1 is in the negative half cycle of the first battery, the control terminals of the fourth transistor Q4 and the fifth transistor Q5 are driven to be conductive by the driving signal, and the first transistor Q1, the second transistor Q2, the third transistor Q3 and the sixth transistor Q6 are not conductive; as shown in fig. 9, when the switching power supply 1 is in the negative half cycle of the second battery, the control terminals of the third transistor Q3 and the fifth transistor Q5 are driven to be conductive by the driving signal, and the first transistor Q1, the second transistor Q2, the fourth transistor Q4 and the sixth transistor Q6 are not conductive.
In another embodiment of the present invention, a high boost dc conversion circuit with power factor correction is shown in fig. 10, wherein the switching power supply 1 further includes an Inverter 2 (Inverter). In this example, the inverter 2 includes a seventh transistor Q7, an eighth transistor Q8, a second inductor L2, and a fourth capacitor C4, where each transistor has an input terminal, an output terminal, and a control terminal, and each transistor may be an N-type transistor (N-Channel MOSFET) in this example. The input terminal Q71 of the seventh transistor Q7 may be electrically connected to the output terminals of the second capacitor C2 and the third diode D3, and the output terminal Q72 of the seventh transistor Q7 may be electrically connected to the input terminal Q81 of the eighth transistor Q8 and one end of the second inductor L2; the other end of the second inductor L2 may be electrically connected to one end of the fourth capacitor C4. The other end of the fourth capacitor C4 is electrically connected to the ground terminal N; the output terminal Q82 of the eighth transistor Q8 is electrically connected to the input terminal of the third capacitor C3 and the fifth diode D5.
In addition, the inverter 2 in this example has a first inversion positive half cycle, a second inversion positive half cycle, a first inversion negative half cycle, and a second inversion negative half cycle.
As shown in fig. 11, when the inverter 2 is in the first positive half cycle, the control terminal of the seventh transistor Q7 is driven by a driving signal to be conductive, and the eighth transistor Q8 is not conductive;
as shown in fig. 12, when the inverter 2 is in the second positive half cycle, the control terminal of the eighth transistor Q8 is driven by the driving signal to be conductive, and the seventh transistor Q7 is not conductive;
as shown in fig. 13, when the inverter 2 is in the first negative half cycle, the control terminal of the eighth transistor Q8 is driven by the driving signal to be conductive, and the seventh transistor Q7 is not conductive;
as shown in fig. 14, when the inverter 2 is in the second negative half cycle, the control terminal of the seventh transistor Q7 is driven by the driving signal to be conductive, and the eighth transistor Q8 is not conductive.
The invention provides a high boost type direct current conversion circuit with power factor correction, which can share the direct current conversion circuit with a boost circuit, and charge/discharge the input voltage through each capacitor of a voltage temporary storage unit so as to improve the total output value of the output voltage.
Claims (7)
1. A high boost DC conversion circuit with power factor correction is characterized in that: the switching type power supply device is provided with an on-line mode and a battery mode, and is electrically connected to a high voltage end and a battery, and comprises a voltage input control unit, wherein the voltage input control unit is electrically connected to the high voltage end and the battery; the voltage temporary storage unit is electrically connected to the voltage input path control unit, and is used for receiving and storing the high-voltage end voltage and then discharging according to the control of the voltage input control unit on the output/input path of the high-voltage end voltage in the on-line mode, and is used for receiving and storing the battery voltage and then discharging according to the control of the voltage input control unit on the output or input path of the battery voltage in the battery mode;
the voltage input control unit comprises a first transistor, a second transistor, a third transistor, a fourth transistor, a fifth transistor, a sixth transistor, a first diode, a second diode, a third diode, a fourth diode, a fifth diode, a sixth diode and a first inductor, each transistor is respectively provided with an input end, an output end and a control end, each diode is respectively provided with an input end and an output end, the voltage temporary storage unit comprises a first capacitor, a second capacitor and a third capacitor, wherein the output end of the first diode is electrically connected to a high voltage end and one end of the first inductor, the input end of the first diode is electrically connected to the voltage positive end of the battery and the input end of the second diode, the output end of the second diode is electrically connected to one end of the first capacitor and the input end of the sixth diode, the other end of the first capacitor is electrically connected to the other end of the first inductor, the input end of the first transistor and the input end of the fourth transistor, the output end of the first transistor is electrically connected to the output end of the second transistor, the input end of the second transistor is electrically connected to the input end of the third diode, the input end of the fourth diode and the output end of the sixth diode, the output end of the third diode is electrically connected to one end of the second capacitor, the other end of the second capacitor is electrically connected to the output end of the third transistor, one end of the third capacitor and the ground, the input end of the third transistor is electrically connected to the output end of the fourth diode, the other end of the third capacitor is electrically connected to the input end of the fifth diode, the output end of the fifth diode is electrically connected to the output end of the sixth transistor and the output end of the fourth transistor, the input end of the sixth transistor is electrically connected to the ground, the output end of the fourth transistor is electrically connected to the input end of the fifth transistor, and the output end of the fifth transistor is electrically connected to the voltage negative end of the battery.
2. The high boost dc conversion circuit with power factor correction according to claim 1, wherein: the on-line mode has a first on-line positive half cycle, a second on-line positive half cycle, a first on-line negative half cycle, and a second on-line negative half cycle, and the battery mode has a first battery positive half cycle, a second battery positive half cycle, a first battery negative half cycle, and a second battery negative half cycle.
3. The high boost dc conversion circuit with power factor correction according to claim 2, wherein: the control ends of the fourth transistor and the sixth transistor are driven to be conducted by a driving signal when the switching power supply device is in a first line positive half cycle, the control ends of the first transistor, the second transistor and the fifth transistor are driven to be conducted by the driving signal when the switching power supply device is in a second line positive half cycle, the control ends of the first transistor, the second transistor, the third transistor and the sixth transistor are driven to be conducted by the driving signal when the switching power supply device is in a first line negative half cycle, the control ends of the fourth transistor, the third transistor and the fifth transistor are driven to be conducted when the switching power supply device is in a second line negative half cycle, the control ends of the fourth transistor, the third transistor, the fifth transistor and the sixth transistor are driven to be conducted when the switching power supply device is in a second line positive half cycle, the control ends of the fourth transistor, the fifth transistor and the fifth transistor are driven to be conducted when the switching power supply device is in a first line negative half cycle, the control ends of the fourth transistor, the fourth transistor and the fifth transistor are driven to be conducted when the switching power supply device is in a second line negative half cycle, the control ends of the fourth transistor and the fifth transistor are driven to be conducted when the fourth line negative half cycle, the control ends of the fourth transistor and the fourth transistor are driven to be conducted when the fourth line negative half cycle, the fourth transistor is driven to be conducted, the fourth transistor and the fourth transistor is driven to be conducted and the fifth transistor are driven to be non-negative. When the switching power supply device is in the negative half cycle of the second battery, the control ends of the third transistor and the fifth transistor are driven by the driving signal to be conducted, and the first transistor, the second transistor, the fourth transistor and the sixth transistor are not conducted.
4. The high boost dc conversion circuit with power factor correction according to claim 1, wherein: the switching power supply device also comprises an inverter which is respectively and electrically connected with the voltage input control unit and the voltage temporary storage unit.
5. The high boost dc conversion circuit with power factor correction according to claim 4, wherein: the inverter comprises a seventh transistor, an eighth transistor, a second inductor and a fourth capacitor, wherein each transistor is respectively provided with an input end, an output end and a control end, the input end of the seventh transistor is electrically connected to the output ends of the second capacitor and the third diode, the output end of the seventh transistor is electrically connected to the input end of the eighth transistor and one end of the second inductor, the other end of the second inductor is electrically connected to one end of the fourth capacitor, the other end of the fourth capacitor is electrically connected to the ground, and the output end of the eighth transistor is electrically connected to the input ends of the third capacitor and the fifth diode.
6. The high boost dc conversion circuit with power factor correction according to claim 5, wherein: the inverter has a first inversion positive half cycle, a second inversion positive half cycle, a first inversion negative half cycle, and a second inversion negative half cycle.
7. The high boost dc conversion circuit with power factor correction of claim 6, wherein: when the inverter is in a first inversion positive half cycle, the control end of the seventh transistor is driven by a driving signal to be conducted, the eighth transistor is not conducted, when the inverter is in a second inversion positive half cycle, the control end of the eighth transistor is driven by the driving signal to be conducted, the seventh transistor is not conducted, when the inverter is in a first inversion negative half cycle, the control end of the eighth transistor is driven by the driving signal to be conducted, the seventh transistor is not conducted, when the inverter is in a second inversion negative half cycle, the control end of the seventh transistor is driven by the driving signal to be conducted, and the eighth transistor is not conducted.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201810130718.0A CN108306508B (en) | 2018-02-08 | 2018-02-08 | High boost type direct current conversion circuit with power factor correction function |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201810130718.0A CN108306508B (en) | 2018-02-08 | 2018-02-08 | High boost type direct current conversion circuit with power factor correction function |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN108306508A CN108306508A (en) | 2018-07-20 |
| CN108306508B true CN108306508B (en) | 2023-06-27 |
Family
ID=62864756
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201810130718.0A Active CN108306508B (en) | 2018-02-08 | 2018-02-08 | High boost type direct current conversion circuit with power factor correction function |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN108306508B (en) |
Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102904329A (en) * | 2011-07-29 | 2013-01-30 | 富泰华工业（深圳）有限公司 | Power supply management circuit |
Family Cites Families (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101685973B (en) * | 2008-09-26 | 2013-03-20 | 力博特公司 | Uninterrupted power supply |
| US8884464B2 (en) * | 2011-08-29 | 2014-11-11 | Schneider Electric It Corporation | Twin boost converter with integrated charger for UPS system |
| CN102593945A (en) * | 2012-02-20 | 2012-07-18 | 华为技术有限公司 | Uninterruptible power supply circuit |
| CN105529815A (en) * | 2014-09-29 | 2016-04-27 | 力博特公司 | Single cell set online UPS circuit and control method thereof |
-
2018
- 2018-02-08 CN CN201810130718.0A patent/CN108306508B/en active Active
Patent Citations (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN102904329A (en) * | 2011-07-29 | 2013-01-30 | 富泰华工业（深圳）有限公司 | Power supply management circuit |
Also Published As
| Publication number | Publication date |
|---|---|
| CN108306508A (en) | 2018-07-20 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| WO2007053247B1 (en) | Led bias current control using adaptive fractional charge pump | |
| US10778106B2 (en) | Power conversion system | |
| TW201445853A (en) | Power supply apparatus | |
| CN109494978B (en) | Integrated circuit of power supply switching circuit and power supply switching controller | |
| CN110855170A (en) | Photovoltaic inverter and capacitor discharge circuit | |
| US11505075B2 (en) | Vehicle including fuel cell, battery-charging method for the vehicle, and recording medium having recorded therein program for executing the method | |
| CN108306508B (en) | High boost type direct current conversion circuit with power factor correction function | |
| CN108462390B (en) | Boosting module for uninterruptible power system | |
| CN219513804U (en) | Photovoltaic inverter and auxiliary power supply device | |
| TWI612752B (en) | A Boost Modules For Uninterruptible Power Systems | |
| US20230048383A1 (en) | Synchronous rectification sampling control circuit, method and chip | |
| TWI689160B (en) | A high step-up dc converter with power factor correction | |
| CN114204801A (en) | BUCK circuit | |
| CN219181229U (en) | Charging circuit, charge pump chip and terminal equipment | |
| CN213027530U (en) | Dual-power supply circuit and dual-power supply device | |
| US20200266816A1 (en) | Power supply circuits | |
| CN111463883B (en) | Solar cell charging control circuit | |
| CN220535427U (en) | Charging control system and vehicle | |
| CN216216605U (en) | Motor drive circuit and electrical equipment | |
| US20230253879A1 (en) | Charger, a multiplexing current conversion circuit and an uninterruptible power supply including the same | |
| CN211352550U (en) | Starting load capacity enhancement auxiliary circuit and power supply | |
| CN214959289U (en) | MCU power management circuit, MCU and portable equipment | |
| CN209627235U (en) | Voltage conversion circuit and electronic device | |
| CN220421663U (en) | Be applied to urea metering pump's slow start control circuit and power module | |
| CN108566112A (en) | A kind of three-level current transformer driving circuit with negative pressure bootstrapping |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |