CN108039821B - Current stress optimization two-phase shift control method of double-active full-bridge DC-DC converter - Google Patents
Current stress optimization two-phase shift control method of double-active full-bridge DC-DC converter Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/3353—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
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Abstract
The invention discloses a current stress optimization two-phase shift control method of a double-active full-bridge DC-DC converter, which comprises the following steps: constructing a state average space equation of the output voltage according to an average model of the output voltage of the dual-active full-bridge DC-DC converter, then carrying out discretization treatment on a differential term of the output voltage in the state average space equation of the output voltage to obtain a predicted value of the output voltage of the converter, and obtaining an internal phase shift quantity of the converter under a current stress optimization control strategy by combining a Lagrange function and a power model of the dual-active full-bridge DC-DC converter under dual phase shift controlD 1Constructing an evaluation function from the predicted output voltage and the reference voltageJTo the evaluation functionJCarrying out derivation treatment to obtain the external phase shift quantity of the double-active full-bridge DC-DC converter under the current stress optimization double phase shift prediction control strategyD 2. The method has the advantages of fast dynamic response, high efficiency, simple control process, easy digital realization and the like, and has strong practicability.
Description
Technical Field
The invention relates to the technical field of power electronics, in particular to a current stress optimization two-phase shift control method of a double-active full-bridge DC-DC converter.
Background
The double-active full-bridge DC-DC converter has the advantages of high power density, electrical isolation, bidirectional energy flow, easy realization of soft switching and the like, and is widely applied to the technical fields of electric automobiles, photovoltaic power generation, uninterruptible power supplies, energy storage and the like.
At present, there are two common control modes for the dual-active full-bridge DC-DC converter:
the method is simple and easy to realize, but the voltage regulating range is limited because the effective value of the full-bridge inversion output alternating voltage is only lower than the input direct voltage. In addition, the method controls the dynamic characteristics of the down-converter to be poor.
Under the control method, the converter system has small inertia, fast dynamic response and easy realization of soft switching. However, in the single-phase-shift control, since the control amount is only the phase shift amount between the square wave voltages output by the two H-bridges, the converter mainly transfers energy through the leakage inductance (or the series auxiliary inductance) of the transformer. Therefore, when the input voltage is not matched with the output voltage, the inductive current stress of the converter can be greatly increased, and the excessive current stress can cause the loss increase of the converter, the efficiency reduction and even the damage of the switching device. In order to reduce the current stress, various current stress optimization methods are proposed, and although the proposed optimization methods can effectively reduce the current stress, the control structures of the optimization methods are complex, and meanwhile, the power control of the converter is only realized through the traditional PI control, so that the dynamic response of the converter is slow.
Disclosure of Invention
In view of the above problems, an object of the present invention is to provide a current stress optimized dual phase shift control method for a dual-active full-bridge DC-DC converter, which can solve the problems of slow dynamic response, complex control structure, etc. in the current stress optimized control algorithm. The technical scheme is as follows:
a current stress optimization two-phase shift control method of a double-active full-bridge DC-DC converter comprises the following steps:
s1: according to an average model of the output voltage of the double-active full-bridge DC-DC converter, a state average space equation of the output voltage of the converter is constructed:
wherein, C2Is an output side capacitor, UoIs output voltage, f is switching frequency, L is auxiliary inductor, R is load resistor, UinIs the input voltage of the converter, D1、D2Respectively an inner phase shift quantity and an outer phase shift quantity of the converter under the control of the double phase shift;
s2: discretizing the state average space equation of the output voltage of the converter, and calculating to obtain a predicted value of the output voltage of the converter in the next control period according to the state average space equation of the output voltage of the converter after discretization:
wherein, Uo(tk)、Uin(tk)、io(tk) Are each tkSampling output voltage, input voltage and output current of a time converter; u shapeo(tk+1) Is tk+1The converter output voltage predicted at the moment;
s3: according to the Lagrange function and a power model of the converter under the dual phase shift control, calculating to obtain an internal phase shift D of the converter under a current stress optimization control strategy1：
Wherein p is0K is the voltage conversion ratio;
s4: and (3) constructing an evaluation function J according to the predicted output voltage and the reference output voltage:
wherein, Uo *(tk) At t for the converterkA reference output voltage at a time;
the evaluation function J is solvedConducting processing, and calculating to obtain an external phase shift D of the converter under the current stress optimization dual phase shift prediction control strategy2：
Wherein, Delta Uo(tk) Is tkThe output voltage of the time converter passes through the output value of the outer ring proportional-integral controller.
Further, the method for constructing the state average space equation of the output voltage of the dual-active full-bridge DC-DC converter comprises the following steps:
according to the symmetry of the waveforms of the output voltage of the H bridge and the inductive current, the working state of the converter is divided into four stages in a half cycle; and respectively establishing a state equation of the output voltage for each working state:
wherein iL1,iL2,iL3,iL4Respectively representing the average value, T, of the inductor current in each stagehsHalf of the switching period;
and constructing a state average space equation of the output voltage according to the state equation of the output voltage in four stages and an equivalent time average principle.
Furthermore, the method for obtaining the predicted output voltage of the dual-active full-bridge DC-DC converter comprises the following steps: and (3) performing discrete processing on the differential term of the output voltage in the state average space equation of the output voltage of the converter by adopting an Euler forward method to obtain the predicted output voltage of the converter in the next control period.
Furthermore, the optimized external phase shift quantity of the converter under the current stress optimization dual phase shift prediction control strategy is obtained
D2The method comprises the following steps:
constructing an objective function by using the square of the difference between the output voltage of the double-active full-bridge DC-DC converter and the reference voltage, deriving the objective function to make the derivative of the objective function zero to obtain an external phase shift quantity, and compensating the external phase shift quantity to obtain an external phase shift quantity D of the double-active full-bridge DC-DC converter2：
Wherein the content of the first and second substances,a1is an intermediate variable and has no physical meaning.
Further, the lagrangian function is defined as:
E＝Imax+λ(p0-p*)
wherein E represents a Lagrangian function, λ is a Lagrangian multiplier, p*For a given power of the converter; i ismaxIs the per unit value of the current stress of the converter.
The invention has the beneficial effects that: according to the state average space model of the output voltage of the double-active full-bridge DC-DC converter, the output voltage of the converter in the next control period is predicted, an evaluation function J is established according to the square of the difference between the predicted output voltage and the reference voltage, and the evaluation function J is differentiated to enable the derivative of the evaluation function J to be zero, so that the optimized phase shift amount is obtained. Meanwhile, due to the influence of factors such as the tube voltage drop of the switching tube, dead time, control delay and the like, the optimized phase shift quantity is compensated, and the final phase shift control quantity is obtained; the current stress optimization control method provided by the invention can quickly respond to sudden changes of the load resistance and the input voltage of the converter; the method has the advantages of fast dynamic response, high efficiency, simple control process, easy digital implementation and the like, and has strong practicability.
Drawings
Fig. 1 is a topology structure diagram of a dual active full bridge DC-DC converter.
FIG. 2 shows a dual phase shift control method (D is more than or equal to 0) for a dual-active full-bridge DC-DC converter1≤D2Not more than 1) voltage and inductive current waveform diagrams at two sides of the transformer.
FIG. 3 shows a dual phase shift control method (D is more than or equal to 0) for a dual-active full-bridge DC-DC converter2≤D1Not more than 1) voltage and inductive current waveform diagrams at two sides of the transformer.
Fig. 4 is a control flow chart of the dual-active full-bridge DC-DC converter under the current stress optimization dual phase shift prediction control method.
Fig. 5 is a voltage-current waveform diagram of a dual-active full-bridge DC-DC converter at the time of starting under a conventional current stress optimization control method.
Fig. 6 is a voltage and current waveform diagram of a dual-active full-bridge DC-DC converter during starting under a current stress optimization dual-phase shift prediction control method.
Fig. 7 is a voltage-current waveform diagram of a dual-active full-bridge DC-DC converter during load switching under a conventional current stress optimization control method.
Fig. 8 is a voltage and current waveform diagram of the dual-active full-bridge DC-DC converter during load switching under the current stress optimization dual-phase shift prediction control method.
Fig. 9 is a waveform diagram of the dual-active full-bridge DC-DC converter during input voltage switching under the conventional current stress optimization control method.
Fig. 10 is a waveform diagram of the input voltage switching of the dual-active full-bridge DC-DC converter under the current stress optimization dual-phase shift prediction control method.
Detailed Description
The invention is described in further detail below with reference to the figures and specific embodiments. In this embodiment, a detailed description is given to a current stress optimization dual phase shift prediction control method for a dual-active full-bridge DC-DC converter according to a topology structure diagram of the dual-active full-bridge DC-DC converter shown in fig. 1.
Firstly, a state average space model of the output voltage of the converter and a state differential equation thereof are constructed according to an average model of the output voltage of the dual-active full-bridge DC-DC converter.
As shown in FIG. 2, when the dual-active full-bridge DC-DC converter is under dual phase shift control, the phase shift satisfies 0 ≦ D1≤D2When the relation is less than or equal to 1, the double-active full-bridge converter has eight working states in total according to the voltage and current waveform diagram of the converter under the control of the double phase shift. Because of the symmetry of the output voltage of the H bridge and the waveform of the inductive current, the modeling is only carried out in a half period, and the state equation of the output voltage is as follows:
wherein, UoFor the output voltage, R is the load resistance, C2Is an output side capacitance, ThsIs half of the switching period, iL1、iL2And iL4Respectively, the average value of the inductor current in the time period, D1Is the amount of internal phase shift of the converter, D2Is the amount of external phase shift.
Each differential equation in the above only represents the relationship between the output voltage, the inductor current and the load current in the operating state, and in order to establish a differential equation that can represent the characteristics of the converter in the whole switching period, the inductor current value at each time is required:
wherein iL(t0)、iL(t1)、iL(t2)、iL(t3)、iL(t4) Are respectively shown at t0、t1、t2、t3、t4The value of the inductance current at the moment; n is the transformer transformation ratio; l is an auxiliary inductor; f is the switching frequency; k is a voltage conversion ratio.
Further, according to the value of the inductance current at each moment, an average value of the inductance current of the dual-active full-bridge DC-DC converter in each period is obtained:
and (3) combining the formula (1), the formula (2) and the formula (3), and deriving a state average space equation of the output voltage of the double-active full-bridge DC-DC converter:
referring to FIG. 3, when the amount of phase shift satisfies 0. ltoreq. D1≤D2When the relation is less than or equal to 1, the state average space equation of the output voltage of the double-active full-bridge DC-DC converter can be obtained in the same way:
and carrying out discrete processing on the state average space equation, and constructing a functional relation between the predicted output voltage and the sampled output voltage. The differential term of the output voltage in the formula (4) reflects the variation trend of the output voltage to a certain extent, and the euler forward method is adopted to carry out discretization processing on the formula (4) respectively to obtain:
and further obtaining the predicted output voltage of the dual-active full-bridge DC-DC converter in the next control period:
wherein, Uo(tk) Is shown at tkThe output voltage of the time converter, namely the sampling voltage; u shapeo(tk+1) Indicating the predicted value at t based on the current sample information and the circuit parameters of the converterk+1The output voltage of the time instant converter.
Similarly, according to the formula (5), D is more than or equal to 02≤D1Obtaining a predicted value of the output voltage of the double-active full-bridge DC-DC converter under the condition that the voltage is not more than 1:
an evaluation function is constructed by the square of the difference between the predicted value of the output voltage and the reference value:
in order to control the stability of the output voltage of the dual-active full-bridge DC-DC converter, according to the predicted output voltage derived by the equations (7) and (8), the square of the difference between the predicted value and the reference value of the output voltage is defined as an evaluation function J:
as can be seen from equation (9), the smaller the evaluation function, the closer the output voltage of the converter at the next time point is to the reference voltage, and in order to minimize the evaluation function, the following is derived:
wherein the content of the first and second substances,
due to the influence of factors such as actual switch tube voltage drop, dead time, control delay and the like, the theoretical model and the actual physical model have deviation, so that the output voltage of the converter is inaccurate, phase shift compensation needs to be added, and the external phase shift D under the current stress optimization double phase shift prediction control method for the double-active full-bridge DC-DC converter is obtained2：
Wherein, Delta Uo(tk) Is tkThe output voltage of the time converter passes through the output value of an outer ring proportional-integral (PI) controller.
Similarly, when the converter satisfies D is more than or equal to 02≤D1When the relation is less than or equal to 1, obtaining an external phase shift D for predicting and controlling the stress optimization of the dual-active full-bridge DC-DC converter2：
Constructing a Lagrangian function: d is more than or equal to 01≤D2≦ 1 for example, define the Lagrangian function as:
E＝Imax+λ(p0-p*) (13)
wherein E represents a Lagrangian function, λ is a Lagrangian multiplier, p*A given power for a dual active full bridge DC-DC converter; i ismaxIs the per unit value of the current stress of the converter.
Equations (6) and (7) are substituted into equation (13), and the lagrangian function is derived:
removing lambda in the formula (14) to obtain an external phase shift D2Amount of phase shift D1The relation between:
combining the formula (11), the formula (12) and the formula (15), the optimized internal phase shift D of the converter under the current stress optimization control is obtained1：
Referring to table 1, the criteria of the working modes of the dual-active full-bridge DC-DC converter and the minimum current stress sum calculated in each mode are givenOptimum phase shift amount D of1And D2。
TABLE 1
Referring to fig. 4, the input voltage, the output voltage and the output current of the dual-active full-bridge DC-DC converter are sampled in real time, the state average space equation of the output voltage of the converter is combined, the output voltage of the converter in the next control period is predicted, an evaluation function J of the output voltage is established, and the optimized phase shift amount is obtained by deriving the evaluation function.
Referring to fig. 5 and 6, in the conventional current stress optimization control algorithm, 323ms is required for the output voltage of the converter to reach a steady state; under the control strategy of the invention, the output voltage of the converter only needs 44ms to reach a stable state, and the output voltage response is rapid and far smaller than and superior to the traditional current stress optimization control algorithm.
Referring to fig. 7 and 8, when the load resistance suddenly changes, in the conventional current stress optimization control algorithm, 168ms is required for the output voltage to return to the stable state, while under the control strategy of the present invention, the load voltage and the current are always stable, and the dynamic response is rapid.
Referring to fig. 9 and 10, when the input voltage suddenly changes, in the conventional current stress optimization control algorithm, 379ms is required for the input voltage to reach a stable state, while under the control strategy of the present invention, the output voltage of the converter rapidly responds and is always stable.
The current stress optimization double phase shift prediction control method can quickly respond to the load resistance of the double-active full-bridge DC-DC converter and the sudden change of the input voltage, has the advantages of quick dynamic response, high efficiency, simple control process, easy digital realization and the like, and has strong practicability.
Claims (4)
1. A current stress optimization two-phase shift control method of a double-active full-bridge DC-DC converter is characterized by comprising the following steps:
s1: according to an average model of the output voltage of the double-active full-bridge DC-DC converter, a state average space equation of the output voltage of the converter is constructed:
wherein, C2Is an output side capacitor, UoIs output voltage, f is switching frequency, L is auxiliary inductor, R is load resistor, UinIs the input voltage of the converter, D1、D2Respectively an inner phase shift quantity and an outer phase shift quantity of the converter under the control of the double phase shift;
s2: discretizing the state average space equation of the output voltage of the converter, and calculating to obtain a predicted value of the output voltage of the converter in the next control period according to the state average space equation of the output voltage of the converter after discretization:
wherein, Uo(tk)、Uin(tk)、io(tk) Are each tkSampling output voltage, input voltage and output current of a time converter; u shapeo(tk+1) Is tk+1The converter output voltage predicted at the moment;
s3: according to the Lagrange function and a power model of the converter under the dual phase shift control, calculating to obtain an internal phase shift D of the converter under a current stress optimization control strategy1：
Wherein p is0K is the voltage conversion ratio;
s4: and (3) constructing an evaluation function J according to the predicted output voltage and the reference output voltage:
wherein, Uo (t)k) At t for the converterkA reference output voltage at a time;
the evaluation function J is subjected to derivation processing, and the external phase shift D of the converter under the current stress optimization dual phase shift prediction control strategy is obtained through calculation2：
Wherein, Delta Uo(tk) Is tkThe output voltage of the time converter passes through the output value of the outer ring proportional-integral controller.
2. The method for current stress optimized two-phase shift control of a dual-active full-bridge DC-DC converter according to claim 1, wherein the method for constructing the state-averaged space equation of the output voltage of the dual-active full-bridge DC-DC converter comprises:
according to the symmetry of the waveforms of the output voltage of the H bridge and the inductive current, the working state of the converter is divided into four stages in a half cycle; and respectively establishing a state equation of the output voltage for each working state:
wherein iL1,iL2,iL3,iL4Respectively representing the average value, T, of the inductor current in each stagehsHalf of the switching period;
and constructing a state average space equation of the output voltage according to the state equation of the output voltage in four stages and an equivalent time average principle.
3. The method for current stress optimized two-phase shift control of a dual-active full-bridge DC-DC converter according to claim 1, wherein: the method for obtaining the predicted output voltage of the double-active full-bridge DC-DC converter comprises the following steps: and (3) performing discrete processing on the differential term of the output voltage in the state average space equation of the output voltage of the converter by adopting an Euler forward method to obtain the predicted output voltage of the converter in the next control period.
4. The method of current stress optimized two-phase shift control for a dual active full-bridge DC-DC converter according to claim 1, wherein the lagrangian function is defined as:
E＝Imax+λ(p0-p*)
wherein E represents a Lagrangian function, λ is a Lagrangian multiplier, p*For a given power of the converter, ImaxIs the per unit value of the current stress of the converter.
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| CN109039082B (en) * | 2018-07-09 | 2020-07-07 | 东南大学 | Backflow power optimization method suitable for modular multilevel direct current transformer |
| CN109004836B (en) * | 2018-07-09 | 2020-07-24 | 东南大学 | Frequency conversion optimization control method suitable for modular multilevel direct current transformer |
| CN109002671A (en) * | 2018-09-29 | 2018-12-14 | 国网四川省电力公司电力科学研究院 | A kind of modeling method of bidirectional DC-DC converter |
| CN109861545B (en) * | 2019-02-19 | 2019-12-20 | 合肥工业大学 | Direct power control method of double-active-bridge direct current converter based on energy closed loop |
| CN111817570B (en) * | 2020-07-17 | 2021-07-13 | 国网辽宁省电力有限公司电力科学研究院 | DAB converter wide-range regulation and control method based on multi-mode model prediction |
| CN112054694B (en) * | 2020-09-16 | 2021-08-27 | 广东电网有限责任公司电力科学研究院 | Bidirectional converter optimization control method and device based on minimum current stress |
| CN115149818B (en) * | 2022-07-27 | 2024-05-03 | 山东大学 | Current-free bias magnetic quick start control method and system based on expansion phase shift modulation |
| CN115800766B (en) * | 2023-01-30 | 2023-05-05 | 广东电网有限责任公司肇庆供电局 | Model reference self-adaptive control method and device based on double active bridge converters |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103997216A (en) * | 2014-05-23 | 2014-08-20 | 西安交通大学 | Modeling method of bidirectional full-bridge direct current converter under unilateral bridge PWM |
| CN105048821A (en) * | 2015-08-25 | 2015-11-11 | 西南交通大学 | Load current feedforward control method of increasing full-bridge isolation DC-DC convertor output voltage dynamic response |
| CN105099200A (en) * | 2015-07-11 | 2015-11-25 | 中国矿业大学(北京) | Alternating-current phasor analysis method and modeling method for phase-shifting control dual active bridge direct-current converters |
| CN105391299A (en) * | 2015-12-24 | 2016-03-09 | 西安理工大学 | Single strategy model prediction control method of Buck converter |
Family Cites Families (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US9584029B2 (en) * | 2014-06-02 | 2017-02-28 | Utah State University | Multi-mode control for a DC-to-DC converter |
-
2017
- 2017-12-05 CN CN201711266394.5A patent/CN108039821B/en active Active
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103997216A (en) * | 2014-05-23 | 2014-08-20 | 西安交通大学 | Modeling method of bidirectional full-bridge direct current converter under unilateral bridge PWM |
| CN105099200A (en) * | 2015-07-11 | 2015-11-25 | 中国矿业大学(北京) | Alternating-current phasor analysis method and modeling method for phase-shifting control dual active bridge direct-current converters |
| CN105048821A (en) * | 2015-08-25 | 2015-11-11 | 西南交通大学 | Load current feedforward control method of increasing full-bridge isolation DC-DC convertor output voltage dynamic response |
| CN105391299A (en) * | 2015-12-24 | 2016-03-09 | 西安理工大学 | Single strategy model prediction control method of Buck converter |
Non-Patent Citations (2)
| Title |
|---|
| Modulation strategy for a Dual Active Bridge converter using Model Predictive Control;Ousseynou Yade等;《2015 IEEE International Symposium on Predictive Control of Electrical Drives and Power Electronics (PRECEDE)》;20160204;第15-20页 * |
| 模块化多电平变换器模型预测控制;何志兴等;《中国电机工程学报》;20160305;第36卷(第5期);第1366-1375页 * |
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