CN107947670B - A kind of power factor control method of direct current biasing type motor - Google Patents
A kind of power factor control method of direct current biasing type motor Download PDFInfo
- Publication number
- CN107947670B CN107947670B CN201711346511.9A CN201711346511A CN107947670B CN 107947670 B CN107947670 B CN 107947670B CN 201711346511 A CN201711346511 A CN 201711346511A CN 107947670 B CN107947670 B CN 107947670B
- Authority
- CN
- China
- Prior art keywords
- axis
- shaft current
- current
- value
- motor
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Active
Links
Classifications
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P21/00—Arrangements or methods for the control of electric machines by vector control, e.g. by control of field orientation
- H02P21/22—Current control, e.g. using a current control loop
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P2201/00—Indexing scheme relating to controlling arrangements characterised by the converter used
- H02P2201/15—Power factor Correction [PFC] circuit generating the DC link voltage for motor driving inverter
Abstract
The invention discloses a kind of power factor control methods of direct current biasing type motor, comprising: (1) determines the relational expression for needing to meet between d shaft current, q shaft current and 0 shaft current under the premise of meeting the power factor of motor is 1；(2) under the premise of d shaft current, q shaft current and 0 shaft current meet above-mentioned relation formula, d shaft current value, q shaft current value and the 0 shaft current value when motor torque maximum for enabling to output are calculated；(3) using the d shaft current value being calculated in step (2), q shaft current value and 0 shaft current value as the given value of current value of the given value of current value of d axis, the given value of current value of q axis and 0 axis, and target value of the motor as d shaft current value, q shaft current value and 0 shaft current value is inputted, carry out no error following.The size that the present invention can make direct current biasing type motor no matter load remains that power factor is 1, while exporting maximum torque.
Description
Technical field
The invention belongs to alternating current generator driving and control fields, more particularly, to a kind of function of direct current biasing type motor
Rate factor control method.
Background technique
Direct current biasing type motor is a kind of New-type electric machine developed on the basis of stator excitation synchronous motor, this
The phase current of motor also contains DC component other than alternating component.It, can be flexible by changing the size of DC bias current
Ground adjusts the air-gap field of motor, therefore has excellent speed adjusting performance.
Currently, the drive control of direct current biasing type motor is generallyd use maximum torque per ampere control method, that is, is controlled
The virtual value that d shaft current processed remains zero, q shaft current is equal with the virtual value of 0 shaft current.This method effectively increases directly
The operational efficiency of eccentrically arranged type motor is flowed, but the shortcomings that this control method are as follows: when loading increase, power factor is reduced, right
Inverter capacity requirement improves, while also resulting in the reduction of grid power transmission efficiency, limits this motor in high power work
The application of occasion.
Summary of the invention
In view of the drawbacks of the prior art, it is an object of the invention to solve to direct current biasing type motor using torque capacity electricity
Stream is than control method, and when so that load increasing, power factor is reduced, and improves to inverter capacity requirement, while also resulting in electricity
The reduction of net power transmission efficiency limits this motor the application of high power work occasion the technical issues of.
To achieve the above object, the present invention provides a kind of power factor control method of direct current biasing type motor, comprising:
(1) it determines under the premise of meeting the power factor of motor is 1, between d shaft current, q shaft current and 0 shaft current
The relational expression for needing to meet；
(2) under the premise of d shaft current, q shaft current and 0 shaft current meet above-mentioned relation formula, calculating enables to defeated
D shaft current value, q shaft current value and 0 shaft current value when motor torque maximum out；
(3) using the d shaft current value being calculated in step (2), q shaft current value and 0 shaft current value as d axis
The given value of current value of given value of current value, the given value of current value of q axis and 0 axis, and motor is inputted as d shaft current value, q shaft current
The target value of value and 0 shaft current value carries out no error following.
Optionally, the step (1) includes:
If the power factor of motor remains 1, current phasor is overlapped with voltage vector at this time, d shaft current, q shaft current with
And 0 shaft current meet following relational expression:
Wherein, udAnd uqRespectively d shaft voltage and q shaft voltage；id、iq、i0Respectively d axis, q axis, 0 shaft current；LsFor electricity
The phase inductance of machine, L0For the zero axle inductance of motor；
It is obtained by above formula: Ls(id 2+iq 2)=L0i0iq。
Optionally, the step (2) includes:
Electric machine phase current virtual value isIt can indicate are as follows:
The electromagnetic torque T of motoreIt can indicate are as follows:
Wherein, npFor the number of pole-pairs of motor, in order to keep in the case where same d axis, q axis and 0 shaft current virtual value
Power factor is 1, while exporting maximum motor torque, be can be obtained:
T is calculated according to above formulaeD axis, q axis, 0 shaft current given value i when maximumd*、iq*、i0* it is respectively as follows:
Wherein, is *For electric machine phase current given value, when motor stabilizing is run, electric machine phase current given value is *With motor phase
Current effective value isIt is essentially equal.
Optionally, the step (3) includes:
(3-1) is by motor speed given value ωe* with motor speed value of feedback ωeDifference DELTA ωrSpeed regulator is sent into,
Speed regulator output armature current given value is*, by adjusting is*, so that ωe* with ωeDifference be always zero, i.e. ωeBegin
ω is followed eventuallye* variation and change.
(3-2) is by motor rotor position signal θeAnd A, B, C phase current signal ia、ib、icIt is sent into the rotational coordinates
Conversion module obtains d axis, q axis, 0 axis DC current signal by rotating coordinate transformation module, and anti-respectively as d shaft current
Feedback value id, q shaft current value of feedback iq, 0 shaft current value of feedback i0。
(3-3) is by armature supply given value is* with motor speed value of feedback ωeIt is sent into distributing switch, the electric current distribution
Device determines d axis, q axis, 0 shaft current given value i according to step (2)d*、iq*、i0*。
(3-4) by d axis, q axis, 0 shaft current given value respectively in step (3-2) d axis, q axis, 0 shaft current feedback
After being worth relatively, d shaft current deviation Δ i is obtainedd, q shaft current deviation Δ iq, 0 shaft current deviation Δ i0, it is respectively fed to d axis, q axis, 0
Shaft current adjuster obtains d axis, q axis, 0 axis given voltage ud*、uq*、u0*, made by adjusting d axis, q axis, 0 axis given voltage
Obtain Δ id、Δiq、Δi0It is always zero, i.e., to id*、iq*、i0* no error following is carried out.
(3-5) is by ud*、uq* with θeIt is sent into the first given voltage phase shift block, defines ud* with uq* the voltage vector synthesized is
us*, by us* it is decomposed into phase under synchronous rotating frame and lags behind us* 30 degree, size areVoltage vector u againα1*、
uβ1*；Meanwhile ud*、uq* with θeIt is also fed into the second given voltage phase shift block, by us* it is decomposed into phase under synchronous rotating frame
Lag behind us* 150 degree, size areVoltage vector u againα2*、uβ2*。
(3-6) is by uα1*、uβ1*、u0* it inputs the first pulse width modulator, carries out space vector pulse width modulation, generate the respectively
A1, B1, C1 phase pwm signal PWM1-PWM6 of one current transformer；U simultaneouslyα2*、uβ2*、u0* the second pulse width modulator is inputted, is carried out empty
Between Vector Pulse Width Modulation, generate A2, B2, C2 phase pwm signal PWM7-PWM12 of the second current transformer respectively；First current transformer
A phase, B phase, C phase end voltage u is exported respectivelya1、ub1、uc1；Second current transformer exports A phase, B phase, C phase end voltage u respectivelya2、
ub2、uc2.The output voltage collective effect of two current transformers is in the A phase, B phase, C phase winding both ends of direct current biasing type motor, driving
Motor stabilizing operation.
PWM1-PWM6 is sent into the first current transformer by (3-7), while PWM7-PWM12 is sent into the second current transformer, pulse width
Modulated signal drives current transformer to generate output voltage, acts on direct current biasing main track current motor phase winding, generation corresponds to
Input the sinusoidal current signal with direct current biasing of pwm signal, it is final realize d shaft current, q shaft current, the indifference of 0 shaft current with
Track.
In general, through the invention it is contemplated above technical scheme is compared with the prior art, have below beneficial to effect
Fruit:
The maximum torque per ampere control method of existing direct current biasing type motor there are shortcomings, one of them be exactly with
The increase of load, motor power factor reducing, the power factor control method provided through the invention, so that direct current biasing
The size no matter type motor loads, moderate holding power factor is 1, and exports maximum torque.So that the power of inverter
It is fully used, while improving the power transmission efficiency of power grid, be suitable for direct current biasing type motor in high power work occasion
Application.
Detailed description of the invention
Fig. 1 is the power factor control method flow chart of direct current biasing type motor provided by the invention；
Fig. 2 is the structure chart of direct current biasing type motor；
Fig. 3 is phase current waveform when direct current biasing type motor operates normally；
Fig. 4 is power factor controlling system block diagram provided by the invention；
Fig. 5 is the three dimensional vector diagram of direct current biasing type sinusoidal current motor.
Specific embodiment
In order to make the objectives, technical solutions, and advantages of the present invention clearer, with reference to the accompanying drawings and embodiments, right
The present invention is further elaborated.It should be appreciated that the specific embodiments described herein are merely illustrative of the present invention, and
It is not used in the restriction present invention.As long as in addition, technical characteristic involved in the various embodiments of the present invention described below
Not constituting a conflict with each other can be combined with each other.
Fig. 1 is the power factor control method flow chart of direct current biasing type motor provided by the invention, as shown in Figure 1, packet
Include following steps:
(1) it determines under the premise of meeting the power factor of motor is 1, between d shaft current, q shaft current and 0 shaft current
The relational expression for needing to meet；
(2) under the premise of d shaft current, q shaft current and 0 shaft current meet above-mentioned relation formula, calculating enables to defeated
D shaft current value, q shaft current value and 0 shaft current value when motor torque maximum out；
(3) using the d shaft current value being calculated in step (2), q shaft current value and 0 shaft current value as d axis
The given value of current value of given value of current value, the given value of current value of q axis and 0 axis, and motor is inputted as d shaft current value, q shaft current
The target value of value and 0 shaft current value carries out no error following.
As shown in Fig. 2, direct current biasing type motor includes stator 10, rotor 20 and winding 30 and shaft, casing, end
Other universal architecture parts of the motors such as lid, position coder.The motor uses concentratred winding, and the current waveform in every phase winding is such as
Shown in Fig. 3.The phase current waveform of this motor includes simple alternating current component and DC component, and simple alternating current component is for generating rotation
Turn magnetic potential, DC component is for generating rotating excitation field.
Direct current biasing type motor power factor control method block diagram provided by the invention, as shown in Figure 4.The control method packet
Include speed regulator 1, distributing switch 2, d shaft current adjuster 3a, q shaft current adjuster 3b, 0 shaft current adjuster 3c,
One given voltage phase shift block 4a, the second given voltage phase shift block 4b, the first pulse-width modulator 5a, the second pulse-width modulator
5b, the first current transformer 6a, the second current transformer 6b, direct current biasing sinusoidal current motor 7, velocity sensor 8 and rotational coordinates become
Block 9 is changed the mold, pulse-width modulator 1 indicates that the first pulse-width modulator, pulse-width modulator 2 indicate the second pulse-width modulator.
Specifically includes the following steps:
(3-1) is by motor speed given value ωe* with motor speed value of feedback ωeDifference DELTA ωrIt is sent into speed regulator
1,1 output armature current given value i of speed regulators*, by adjusting is*, so that ωe* with ωeDifference be always zero, i.e.,
ωeAlways ω is followede* variation and change.
(3-2) is by motor rotor position signal θeAnd A, B, C phase current signal ia、ib、icIt is sent into the rotational coordinates
Conversion module 9 obtains d, q, 0 axis DC current signal by rotating coordinate transformation module 9, and feeds back respectively as d shaft current
Value id, q shaft current value of feedback iq, 0 shaft current value of feedback i0。
(3-3) armature supply given value is* with motor speed value of feedback ωeIt is sent into distributing switch 2, the electric current distribution
D shaft current given value i is obtained by calculation according to unity power factor control principle in deviced*, q shaft current given value iq*, 0 axis electricity
Flow given value i0* as the control amount of mixed excitation electric machine, direct current biasing sinusoidal current motor is controlled.
The power factor controlling principle of lower surface analysis direct current biasing type motor, when negligible resistance pressure drop, direct current biasing type electricity
Steady state voltage equation of the machine in dq0 synchronous rotating frame are as follows:
Wherein, ud、uq、u0Respectively d axis, q axis, 0 shaft voltage；id、iq、i0Respectively d axis, q axis, 0 shaft current；LsFor electricity
The phase inductance of machine, L0For zero axle inductance；ωeFor angular rate；
The three dimensional vector diagram of direct current biasing type sinusoidal current motor is as shown in Figure 5, wherein orthogonal d axis, q axis are rotation
Coordinate system, orthogonal α axis, β axis are rest frame.usFor udWith uqSynthesized voltage vector, i.e., motor space voltage arrow
Amount；usFor idWith iqResultant current vector, i.e. the Space current vector of motor；For usAnd isBetween angle, i.e. motor
Power-factor angle.In order to make the power factor of motor remain 1, i.e.,ThenCurrent phasor and voltage are sweared at this time
Amount is overlapped, and is had:
It is obtained by above formula:
Ls(id 2+iq 2)=L0i0iq
When motor stabilizing is run, electric machine phase current given value is *With electric machine phase current virtual value isIt is essentially equal, and motor
Phase current virtual value can indicate are as follows:
The electromagnetic torque T of motoreIt can indicate are as follows:
Wherein, npFor the number of pole-pairs of motor.It is 1 in the case where same current effective value, keep power factor, together
When export maximum motor torque, obtained by above-mentioned three formulas simultaneous:
T is calculated according to above formulaeD axis, q axis, 0 shaft current given value when maximum are as follows:
(3-4) by d axis, q axis, 0 shaft current given value respectively in step (3-2) d axis, q axis, 0 shaft current feedback
After being worth relatively, d shaft current deviation Δ i is obtainedd, q shaft current deviation Δ iq, 0 shaft current deviation Δ i0, it is respectively fed to d axis, q axis, 0
Shaft current adjuster obtains d axis, q axis, 0 axis given voltage ud*、uq*、u0*, made by adjusting d axis, q axis, 0 axis given voltage
Obtain Δ id、Δiq、Δi0It is always zero, i.e., to id*、iq*、i0* no error following is carried out.
(3-5) is by ud*、uq* with θeIt is sent into the first given voltage phase shift block 4a, by the voltage under synchronous rotating frame
Resolution of vectors is that phase lags behind 30 degree of synthesized voltage vector under synchronous rotating frame, and size is synthesized voltage vectorTimes
Voltage vector uα1*、uβ1*；Meanwhile ud*、uq* with θeIt is also fed into the second given voltage phase shift block 4b, by synchronously rotating reference frame
Voltage vector under system is decomposed into phase under synchronous rotating frame and lags behind 150 degree of synthesized voltage vector, and size is synthesis electricity
Press vectorVoltage vector u againα2*、uβ2*。
(3-6) is by uα1*、uβ1*、u0* the first pulse width modulator 5a is inputted, is carried out space vector pulse width modulation (SVPWM), point
A1, B1, C1 phase pwm signal PWM1-PWM6 of the first current transformer are not generated；U simultaneouslyα2*、uβ2*、u0* the second pulsewidth modulation is inputted
Device 5b carries out space vector pulse width modulation (SVPWM), generates A2, B2, C2 phase pwm signal PWM7- of the second current transformer respectively
PWM12。
(7) PWM1-PWM6 is sent into the first current transformer 6a, while PWM7-PWM12 is sent into the second current transformer 6b.Pulse is wide
It spends modulated signal driving current transformer and generates output voltage, act on direct current biasing main track current motor phase winding, generate correspondence
In the sinusoidal current signal with direct current biasing of input pwm signal, the no error following of d, q, 0 shaft current are finally realized.
As it will be easily appreciated by one skilled in the art that the foregoing is merely illustrative of the preferred embodiments of the present invention, not to
The limitation present invention, any modifications, equivalent substitutions and improvements made within the spirit and principles of the present invention should all include
Within protection scope of the present invention.
Claims (3)
1. a kind of power factor control method of direct current biasing type motor characterized by comprising
(1) it determines under the premise of meeting the power factor of motor is 1, is needed between d shaft current, q shaft current and 0 shaft current
The relational expression of satisfaction；If the power factor of motor remains 1, current phasor is overlapped with voltage vector at this time, d shaft current, q axis electricity
Stream and 0 shaft current meet following relational expression:
Wherein, udAnd uqRespectively d shaft voltage and q shaft voltage；id、iq、i0Respectively d axis, q axis, 0 shaft current；LsFor motor
Phase inductance, L0For the zero axle inductance of motor；
It is obtained by above formula: Ls(id 2+iq 2)=L0i0iq；
(2) it under the premise of d shaft current, q shaft current and 0 shaft current meet above-mentioned relation formula, calculates and enables to output
D shaft current value, q shaft current value and 0 shaft current value when motor torque maximum；
(3) using the d shaft current value being calculated in step (2), q shaft current value and 0 shaft current value as the electric current of d axis
The given value of current value of given value, the given value of current value of q axis and 0 axis, and input motor as d shaft current value, q shaft current value with
And 0 shaft current value target value, carry out no error following.
2. the power factor control method of direct current biasing type motor according to claim 1, which is characterized in that the step
(2) include:
Electric machine phase current virtual value isIt can indicate are as follows:
The electromagnetic torque T of motoreIt can indicate are as follows:
Wherein, npFor the number of pole-pairs of motor, in order to keep power in the case where same d axis, q axis and 0 shaft current virtual value
Factor is 1, while exporting maximum motor torque, be can be obtained:
T is calculated according to above formulaeD axis, q axis, 0 shaft current given value i when maximumd*、iq*、i0* it is respectively as follows:
Wherein, is *For electric machine phase current given value, when motor stabilizing is run, electric machine phase current given value is *Have with electric machine phase current
Valid value isIt is essentially equal.
3. the power factor control method of direct current biasing type motor according to claim 2, which is characterized in that the step
(3) include:
(3-1) is by motor speed given value ωe* with motor speed value of feedback ωeDifference DELTA ωrIt is sent into speed regulator, speed
Adjuster exports is*, by adjusting is*, so that ωe* with ωeDifference be always zero, i.e. ωeAlways ω is followede* variation and
Variation；
(3-2) is by motor rotor position signal θeAnd A, B, C phase current signal ia、ib、icIt is sent into rotating coordinate transformation module,
D axis, q axis, 0 axis DC current signal are obtained by rotating coordinate transformation module, and respectively as d shaft current value of feedback id, q axis
Current feedback values iq, 0 shaft current value of feedback i0；
(3-3) is by is* with motor speed value of feedback ωeIt is sent into distributing switch, the distributing switch determines d according to step (2)
Axis, q axis, 0 shaft current given value id*、iq*、i0*；
(3-4) by d axis, q axis, 0 shaft current given value respectively in step (3-2) d axis, q axis, 0 shaft current value of feedback ratio
After relatively, d shaft current deviation Δ i is obtainedd, q shaft current deviation Δ iq, 0 shaft current deviation Δ i0, it is respectively fed to d axis, q axis, 0 axis electricity
Throttle regulator obtains d axis, q axis, 0 axis given voltage ud*、uq*、u0*, make Δ by adjusting d axis, q axis, 0 axis given voltage
id、Δiq、Δi0It is always zero, i.e., to id*、iq*、i0* no error following is carried out；
(3-5) is by ud*、uq* with θeIt is sent into the first given voltage phase shift block, defines ud* with uq* the voltage vector synthesized is us*,
By us* it is decomposed into phase under synchronous rotating frame and lags behind us* 30 degree, size areVoltage vector u againα1*、
uβ1*；Meanwhile ud*、uq* with θeIt is also fed into the second given voltage phase shift block, by us* it is decomposed into phase under synchronous rotating frame
Lag behind us* 150 degree, size areVoltage vector u againα2*、uβ2*；
(3-6) is by uα1*、uβ1*、u0* the first pulse width modulator is inputted, space vector pulse width modulation is carried out, first is generated respectively and becomes
Flow A1, B1, C1 phase pwm signal PWM1-PWM6 of device；U simultaneouslyα2*、uβ2*、u0* the second pulse width modulator is inputted, space arrow is carried out
Pulsewidth modulation is measured, generates A2, B2, C2 phase pwm signal PWM7-PWM12 of the second current transformer respectively；
PWM1-PWM6 is sent into the first current transformer by (3-7), while PWM7-PWM12 is sent into the second current transformer, pulse width modulation
Signal drives current transformer to generate output voltage, acts on direct current biasing main track current motor phase winding, generates and corresponds to input
The sinusoidal current signal with direct current biasing of pwm signal, the final no error following for realizing d shaft current, q shaft current, 0 shaft current.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201711346511.9A CN107947670B (en) | 2017-12-15 | 2017-12-15 | A kind of power factor control method of direct current biasing type motor |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN201711346511.9A CN107947670B (en) | 2017-12-15 | 2017-12-15 | A kind of power factor control method of direct current biasing type motor |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN107947670A CN107947670A (en) | 2018-04-20 |
| CN107947670B true CN107947670B (en) | 2019-06-11 |
Family
ID=61943444
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN201711346511.9A Active CN107947670B (en) | 2017-12-15 | 2017-12-15 | A kind of power factor control method of direct current biasing type motor |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN107947670B (en) |
Families Citing this family (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN110022103B (en) * | 2019-03-07 | 2020-07-10 | 华中科技大学 | Direct torque control device and method for direct current bias sinusoidal current motor |
| CN110247607B (en) * | 2019-06-13 | 2021-04-20 | 华中科技大学 | Open winding control system and control method for switched reluctance motor |
Family Cites Families (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101847874B (en) * | 2010-05-12 | 2012-06-13 | 华中科技大学 | Wattless current tracking method of static var compensator based on power balance |
| CN104852657B (en) * | 2015-05-14 | 2017-04-12 | 浙江大学 | Control method for suppressing current zero-crossing fluctuation of bus-shared single-side controllable open-winding permanent-magnet motor system |
| CN106533310B (en) * | 2016-12-30 | 2018-09-25 | 华中科技大学 | A kind of direct current biasing sinusoidal current electric machine controller |
-
2017
- 2017-12-15 CN CN201711346511.9A patent/CN107947670B/en active Active
Also Published As
| Publication number | Publication date |
|---|---|
| CN107947670A (en) | 2018-04-20 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN101969289B (en) | Gain adjustment for improving torque linearity of motor during working in field weakening zone | |
| CN110224648B (en) | Permanent magnet synchronous motor parameter identification and position sensorless control method and system | |
| CN101399515B (en) | System and method for controlling torque ripples in synchronous machines | |
| CN105515479B (en) | A kind of durface mounted permanent magnet synchronous generator field weakening control method | |
| CN102891647B (en) | Method and the field weakening control loop of accuracy is weakened for controlling magnetic field in integrated permanent magnets motor | |
| CN102197583B (en) | A method and a controlling arrangement for controlling an AC generator | |
| US5751069A (en) | Heat engine generator control system | |
| CN107623469B (en) | A kind of the weak magnetic control device and method of direct current biasing sinusoidal current motor | |
| CN101383582B (en) | Electric excitation synchronous motor control method based on torque angle sine value linear control | |
| CN107565871A (en) | Control for generator is arranged | |
| CN107070335B (en) | Double PWM permanent magnetism power-driven system torque feed forward control methods and its control device | |
| Han et al. | Dual-electrical-port control of cascaded doubly-fed induction machine for EV/HEV applications | |
| CN109818541B (en) | Memory motor winding multiplexing control method and system for flux linkage observation | |
| CN102780433A (en) | Instantaneous torque control method of brushless direct-current motor based on direct-current control | |
| CN109194218B (en) | Control device, control method and system of direct-current bias type hybrid excitation motor | |
| CN105391360A (en) | Optimal efficiency control method of electric vehicle under electroghermal constraint, controller, and system | |
| CN106533310A (en) | Direct current bias sinusoidal current motor controller | |
| CN107947670B (en) | A kind of power factor control method of direct current biasing type motor | |
| CN101582675B (en) | Space vector modulated method for linearly regulating speed of torque angle of permanent magnet flux switching motor | |
| US8901896B2 (en) | System and method for non-sinusoidal current waveform excitation of electrical generators | |
| CN106787979B (en) | Generator rotor angle self-stabilization rear feed compensating control method in high-speed brushless DC electromotor | |
| CN110061676A (en) | A kind of bearing-free permanent magnet synchronous motor controller based on flux observer | |
| CN103929110B (en) | Using the M phase magneto control methods of dutycycle direct solution pulsewidth modulation | |
| CN109600088B (en) | Harmonic current injection device and method of three-phase inverter | |
| CN108777558A (en) | A kind of brushless dual-feed motor feedforward current control system, feedforward current controller and its design method |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| PB01 | Publication | ||
| PB01 | Publication | ||
| SE01 | Entry into force of request for substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| GR01 | Patent grant | ||
| GR01 | Patent grant |