CN105099254A - Control method of direct current-alternating current inverter - Google Patents
Control method of direct current-alternating current inverter Download PDFInfo
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- CN105099254A CN105099254A CN201510355880.9A CN201510355880A CN105099254A CN 105099254 A CN105099254 A CN 105099254A CN 201510355880 A CN201510355880 A CN 201510355880A CN 105099254 A CN105099254 A CN 105099254A
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Abstract
The invention provides a control method of a direct current-alternating current inverter. The method comprises the following steps: (a) taking a switching period (Te), level jump time (tau1) and high level time (T1) as control variables; (b) dividing the switching period into three time periods, namely [0, tau1], [tau1, tau1+T1] and [tau1+T1, Te], and listing expressions of current variation of an inductor and voltage variation of a capacitor in each time period; (c) respectively adding the current variation of the inductor and the voltage variation of the capacitor in the three time periods to obtain the expression of the current variation of the inductor and the voltage variation of the capacitor within one switching period; (d) deriving a relational expression of the level jump time and the high level time from the expression in the step (c); and (e) calculating the level jump time and the high level time from the relational expression to carry out control. According to the method, the response recovery time and amplitude of the direct current-alternating current inverter in the condition of sudden change of load can be greatly improved; and the total harmonic distortion of an output sine signal is effectively reduced.
Description
Technical field
The present invention relates to DC-AC conversion field, refer to a kind of control method of DC-AC inverter specifically.
Background technology
DC-AC inverter is one of industrial modal power supply changeover device, and it is widely used in the fields such as new forms of energy, electrical network, automotive electronics and uninterrupted power supply.The digital control method of this type of power supply is a focus direction of power electronics research.Compared to analog control method, digital control method is more paid close attention to because having overprogram, better anti-noise ability and being subject to researcher to advantages such as service condition are insensitive.
Although from nineteen nineties, digital control method is applied to DC-AC inverter gradually, and performance shows advantage.But analog controller still has the call for a long time, for DC-AC inverter, the digital control method market share is less.Along with the development of microelectronic technique, the restriction in cost and size is broken gradually, and digital control method is also subject to the favor of designer because of its superior performance.The study hotspot of digital control method mainly concentrates on that the automatic stabilisation of inverter is run at present, system-level integrated, real-time effective monitoring and optimization and can improve mapping and reduce the aspect such as nonlinear Control of total harmonic distortion.
DC-AC inverter is generally controlled by switch periods and high level time two control variables.As shown in Figure 1, in a switch periods, the situation of change of two control signals (pwm signal 1 of solid line and the pwm signal 2 of dotted line) is as follows: two signal dutyfactors are identical, i.e. T
1=T
2; And level bound-time is different first in the cycle of two signals, i.e. τ
2> τ
1.The variable quantity of inductive current within this cycle is identical, i.e. Δ I
l1=Δ I
l2; And the increment Delta V of capacitance voltage under signal 1 drives
c1be greater than Δ V
c2.Fig. 1 discloses a phenomenon: the pulse width modulating signal of same duty cycle, different high level bound-time is to capacitance voltage, and the control effects of the output voltage namely in the present invention is different.In circuit parameter, the value of τ can affect the change of output voltage, thus affects the reliability of circuit, steady-state characteristic and transient response.
Summary of the invention
For the problems referred to above, the present invention proposes the control method that a kind of transient response and total harmonic distortion are all better than the DC-AC inverter of prior art, described DC-AC inverter is driven by pulse width modulating signal (d), and comprise the filter circuit be made up of inductance and electric capacity, the method comprises:
A. by switch periods (T
e), level bound-time (τ
1), high level time (T
1) as the control variables of described control method;
B. by a switch periods (T
e) be divided into [0; τ
1], [τ
1; τ
1+ T
1], [τ
1+ T
1; T
e] three time periods, list the expression formula of the current change quantity of inductance in each time period, the voltage variety of electric capacity;
C. the current change quantity of the inductance of each time period of described three time periods, the voltage variety of electric capacity are added respectively and, obtain the expression formula of the current change quantity of a switch periods internal inductance and the voltage variety of electric capacity;
D. level bound-time (τ is derived from the expression formula step c
1), high level time (T
1) relational expression;
E. level bound-time (τ is calculated from described relational expression
1), high level time (T
1), thus with switch periods (T
e), level bound-time (τ
1), high level time (T
1) control.
Wherein, described switch periods (T
e) be cycle of pulse width modulating signal (d), level bound-time (τ
1) be to the time producing level saltus step first from switch periods, high level time (T
1) be in switch periods, produce the time that level jumps to level rebound first.
Wherein, the current change quantity of a switch periods internal inductance is recorded by the current sensor be applied on DC-AC inverter.
Wherein, in a switch periods, the voltage variety of electric capacity obtains for the register storing the capacitance voltage difference between two adjacent switch cycles by increasing.
The present invention changes the generation pattern of pulse width modulating signal in prior art, a switch periods is divided into three parts, by switch periods, level bound-time, high level time three control variables control, compared to the method that the control method of DC-AC inverter in prior art is only controlled by switch periods and high level time two control variables, the present invention changes three control variables into by two control variables, the pulse width modulating signal of the different high level bound-time of same duty cycle can be embodied accurately to the different control effects of capacitance voltage, therefore the method compared with prior art greatly can accelerate DC-AC inverter responds recovery time and amplitude when load changing, and effectively reduce the total harmonic distortion exporting sinusoidal signal.
Accompanying drawing explanation
By reading the detailed description done non-limiting example done with reference to the following drawings, other features, objects and advantages of the present invention will become more obvious:
Fig. 1 is same duty cycle, different high level bound-time affects schematic diagram to state variable;
Fig. 2 is the flow chart of the control method of a kind of DC-AC inverter that the present invention proposes;
Fig. 3 is the block diagram of the control system of the DC-AC inverter that the present invention proposes;
Fig. 4 is the Controlling model structure chart of DC-AC inverter;
Fig. 5 is the oscillogram of pulse width modulating signal;
Fig. 6 is according to the analogous diagram of embodiments of the invention to total harmonic distortion.In accompanying drawing, same or analogous Reference numeral represents same or analogous parts.
Fig. 7 is the analogous diagram changed load transient according to embodiments of the invention.
Embodiment
For making the object, technical solutions and advantages of the present invention clearly, below in conjunction with accompanying drawing, embodiments of the invention are described in detail.
Be described below in detail embodiments of the invention, the example of described embodiment is shown in the drawings, and wherein same or similar label represents same or similar element or has element that is identical or similar functions from start to finish.Being exemplary below by the embodiment be described with reference to the drawings, only for explaining the present invention, and can not limitation of the present invention being interpreted as.
Disclosing hereafter provides many different embodiments or example is used for realizing different structure of the present invention.Of the present invention open in order to simplify, hereinafter the parts of specific examples and setting are described.Certainly, they are only example, and object does not lie in restriction the present invention.In addition, the present invention can in different example repeat reference numerals and/or letter.This repetition is to simplify and clearly object, itself does not indicate the relation between discussed various embodiment and/or setting.
Below with reference to Fig. 2 ~ Fig. 4, the present invention is described.
As shown in Figure 2, the invention provides a kind of control method of DC-AC inverter.This DC-AC inverter is driven by pulse width modulating signal d, and this DC-AC inverter has the filter circuit be made up of inductance L and electric capacity C, and this control method comprises:
A. by switch periods T
e, level bound-time τ
1, high level time T
1as the control variables of described control method, wherein switch periods T
ethe cycle of pulse width modulating signal d, level bound-time τ
1to the time producing level saltus step first from switch periods, high level time T
1in switch periods, produce the time that level jumps to level rebound first;
B. by switch periods T
ebe divided into [0; τ
1], [τ
1; τ
1+ T
1], [τ
1+ T
1; T
e] three time periods, for wherein each time period, respectively by the variable quantity switch periods T of the voltage of the variable quantity of the electric current of inductance L, electric capacity C
e, level bound-time τ
1, high level time T
1, and to represent with the curtage of inductance L and electric capacity C;
C. the variable quantity of the variable quantity of the electric current of the inductance L of each time period of described three time periods, the voltage of electric capacity C is added respectively and, obtain the variable quantity switch periods T of the voltage of electric capacity C in the variable quantity of the electric current of a switch periods internal inductance L, a switch periods
e, level bound-time τ
1, high level time T
1, and the expression of curtage with inductance L and electric capacity C;
D. at given switch periods T
ewhen, in the variable quantity, a switch periods of the electric current of a switch periods internal inductance L variable quantity of the voltage of electric capacity C expression, derive level bound-time τ
1, high level time T
1by the relational expression of the variable quantity of the voltage of electric capacity C in inductance L and the curtage of electric capacity C, the variable quantity of the electric current of a switch periods internal inductance L, a switch periods;
E. level bound-time τ is calculated from described relational expression
1, high level time T
1, thus with switch periods T
e, level bound-time τ
1, high level time T
1control.
Fig. 3 is the block diagram of the control system of DC-AC inverter in one embodiment of the present of invention, next, is described in detail in conjunction with an embodiment the method that the present invention proposes.
As shown in Figure 4, a basic DC-AC inverter is driven by pulse width modulating signal d, controls conducting or the shutoff of power switch pipe.Filtering device in circuit is made up of inductance L and electric capacity C, and by load R
lthe change of resistance produces disturbance, to output voltage V
ohave an impact.State variation important in this circuit comprises inductive current I
lwith capacitance voltage V
c.Also capacitance current I will be used in explanation of the present invention
cwith load current I
othis Two Variables.
First, the single order discrete-time state-space model setting up the DC-AC inverter shown in Fig. 4 is needed.It should be noted that in ensuing design, have ignored the equivalent series resistance (ESR) of electric capacity, therefore output voltage V
ocan be considered and capacitance voltage V
cequal.Suppose at a switch periods T
ein, load current I
oonly have very little change, namely the variable quantity of load current levels off to 0 (Δ I
o(k) ≈ 0), then at a switch periods T
ein, input variable can be assumed to be constant.Based on above hypothesis and analysis, the single order discrete-time state-space model of DC-AC inverter can be expressed as:
Wherein,
for the state variable of this single order discrete-time state-space model, i.e. the variate-value of a kth switch periods, x (k+1) is then the variate-value of kth+1 switch periods; U (k) is output variable, works as IGBT
1during conducting,
work as IGBT
2during conducting,
inverter behavioral trait is by analyzing the description of discrete-time state-space.The controller target that the present invention proposes is exactly make inductive current and capacitance voltage equal reference current and the voltage in switch periods most end moment in next switch periods.
Then by switch periods T
e, level bound-time τ
1, high level time T
1as the control variables of described control method.
As shown in Figure 5, be the waveform pattern of pulse width modulating signal in described fast transient response method.The target of existing feedback controller is that the variable duty ratio of generation one carrys out regulation output signal.And the present invention changes the generation pattern of pulse width modulation, by a switch periods T
ebe divided into three parts, by Two Variables τ
1and T
1control.Wherein, τ
1the time of high level is produced, i.e. level bound-time first in control cycle; T
1control duty ratio.That is, the pulse width modulating signal controlled by cycle and high level time Two Variables in the past, changes into by τ
1, T
1and T
ethree Variable Control.
Fig. 1 explains and adopts new pulse width modulating signal to inductive current I
lwith capacitance voltage V
cthe impact of two state variables.As shown in Figure 1, in a switch periods, the situation of change of two control signals (pwm signal 1 of solid line and the pwm signal 2 of dotted line) is as follows: two signal dutyfactors are identical, i.e. T
1=T
2; And level bound-time is different first in the cycle of two signals, i.e. τ
2> τ
1.The variable quantity of inductive current within this cycle is identical, i.e. Δ I
l1=Δ I
l2; And the increment Delta V of capacitance voltage under signal 1 drives
c1be greater than Δ V
c2.Apparent, Fig. 5 discloses a phenomenon: the pulse width modulating signal of same duty cycle, different high level bound-time is to capacitance voltage, and the control effects of the output voltage namely in the present invention is different.In circuit parameter, the value of τ can affect the change of output voltage.The present invention just carries out the design of control algolithm based on this phenomenon, restrain faster when target is load changing, and lower total harmonic distortion.
Next, τ will be inquired in detail
1, T
1and T
ethe relation of three variablees and DC-AC inverter.
First, analyze for inductive current situation of change in Fig. 1, namely a switch periods internal inductance current change quantity is solved.As shown in Figure 4, a switch periods T
eby variable τ
1and T
1be divided into 3 time periods, and the current change quantity of all current periods be defined as:
ΔI
i(k)＝I
i(k+1)-I
i(k)
Therefore the variation delta I of two adjacent periods inductive currents
lk () can be expressed as 3 time periods [0; τ
1], [τ
1; τ
1+ T
1], [τ
1+ T
1; T
e] summation of variable quantity:
Above 3 sections of current change quantities are added, the inductive current total variation of a switch periods can be obtained:
From above formula, the variation delta I of inductive current
l(k) and T
1with capacitance voltage V
ck () is relevant.Adopt prediction algorithm, the T in next cycle
1value can be expressed as:
Next, analyze for capacitance voltage situation of change in Fig. 5, namely voltage variety in a switch periods is solved.Still analyze according to above 3 time periods, respective capacitance current can be expressed as:
Wherein I
ck () is the capacitance current of start time in cycle,
with
be respectively τ
1and T
1the rate of change of capacitance current in time period.The present invention defines Δ V
c(k+1)=V
c(k+1)-V
c(k), then in a switch periods, the variable quantity of capacitance voltage can be expressed as following 3 sections of variable quantity sums:
Be
Wherein
Next period tau can be back-calculated to obtain by above formula
1expression formula as follows:
Comprehensive above-mentioned conclusion, the control variables T of circuit
1and τ
1determined by following variable:
By above formula, the Controlling model of fast transient response method of the present invention can be set up.Inductive current variation delta I
l(k) and capacitance current I
ck () obtains by the current sensor be applied on DC-AC inverter.In the present invention, Δ V
c(k+1) be defined as:
ΔV
C(k+1)＝V
C(k+1)-V
C(k)
This variable realizes two adjacent periods voltage differences by a controller inside increase register and obtains.
at time period τ
1the rate of change of capacitance current in (k).And provide following two deductions: 1) output current I
ok () changes very little in adjacent periods.2) at τ
1k in () time period, the pass of electric capacity and inductance current potential is V
l(k)=-E-V
c(k).Based on above deduction, can derive and obtain:
By above-mentioned analysis, this fast transient response controller is to the controling parameter τ of the DC-AC inverter of constant switch periods
1, T
1and T
ecan direct-coupling voltage and induced current be passed through, and carry out calculating acquisition according to the method described above.
That is, the present invention is by switch periods T
ebe divided into [0; τ
1], [τ
1; τ
1+ T
1], [τ
1+ T
1; T
e] three time periods, for wherein each time period, respectively by the variable quantity switch periods T of the voltage of the variable quantity of the electric current of inductance L, electric capacity C
e, level bound-time τ
1, duty ratio T
1, and to represent with the curtage of inductance L and electric capacity C.Then, the variable quantity of the variable quantity of the electric current of the inductance L of each time period of described three time periods, the voltage of electric capacity C is added respectively and, obtain the variable quantity switch periods T of the voltage of electric capacity C in the variable quantity of the electric current of a switch periods internal inductance L, a switch periods
e, level bound-time τ
1, high level time T
1, and the expression of curtage with inductance L and electric capacity C.At given switch periods T
ewhen, in the variable quantity, a switch periods of the electric current of a switch periods internal inductance L variable quantity of the voltage of electric capacity C expression, derive level bound-time τ
1, duty ratio T
1by the relational expression of the variable quantity of the voltage of electric capacity C in inductance L and the curtage of electric capacity C, the variable quantity of the electric current of a switch periods internal inductance L, a switch periods.Due to the curtage of inductance L and electric capacity C, the variable quantity of the electric current of a switch periods internal inductance L, in a switch periods, the variable quantity of the voltage of electric capacity C all can be surveyed, the such as variable quantity of the electric current of a switch periods internal inductance (L), inductance (L) can be recorded by the current sensor be applied on DC-AC inverter with the electric current of electric capacity (C), in a switch periods, the variable quantity of the voltage of electric capacity (C) obtains for the register storing the capacitance voltage difference between two adjacent switch cycles by increasing, therefore can in the hope of level bound-time τ
1, high level time T
1.
When three control variables are all obtained or be known, just can control with these three control variables.
Finally, for verifying above-mentioned control method, the present invention implements on a DC-AC inverter, functional with this algorithm of method validation emulated.The sine wave AC voltage of 363V input direct voltage is converted to effective value by this inverter to be 200V frequency be 50Hz.Default switch frequency 20KHz, filter inductance L=1.547mH, filter capacitor C=10 μ F.Fig. 6 is output voltage (a) and the time dependent situation of inductive current (b) of this control method, and total harmonic distortion THD value (c).In figure (a), VcCons is reference output voltage, and in figure (b), ILCons is inductive current, and in figure (c), THD refers to total harmonic distortion.THD value of the present invention is 0.104%, far below most of inverter (being greater than 2%).The quick response of inductive current also can illustrate superiority of the present invention equally.
The present invention greatly can accelerate DC-AC inverter responds recovery time and amplitude when load changing, and effectively reduces the total harmonic distortion exporting sinusoidal signal.
Above-described embodiment is the present invention's preferably execution mode; but embodiments of the present invention are not restricted to the described embodiments; change, the modification done under other any does not deviate from Spirit Essence of the present invention and principle, substitute, combine, simplify; all should be the substitute mode of equivalence, be included within protection scope of the present invention.
Claims (4)
1. a control method for DC-AC inverter, described DC-AC inverter is driven by pulse width modulating signal, and comprises the filter circuit be made up of inductance and electric capacity, and the method comprises:
A. by switch periods (T
e), level bound-time (τ
1), high level time (T
1) as the control variables of described control method;
B. by switch periods (T
e) be divided into [0; τ
1], [τ
1; τ
1+ T
1], [τ
1+ T
1; T
e] three time periods, list the expression formula of the current change quantity of inductance in each time period, the voltage variety of electric capacity;
C. the current change quantity of the inductance of each time period of described three time periods, the voltage variety of electric capacity are added respectively and, obtain the expression formula of the current change quantity of a switch periods internal inductance and the voltage variety of electric capacity;
D. level bound-time (τ is derived from the expression formula step c
1), high level time (T
1) relational expression;
E. level bound-time (τ is calculated from described relational expression
1), high level time (T
1), thus with switch periods (T
e), level bound-time (τ
1), high level time (T
1) control.
2. control method according to claim 1, wherein said switch periods (T
e) be cycle of pulse width modulating signal (d), level bound-time (τ
1) be to the time producing level saltus step first from switch periods, high level time (T
1) be in switch periods, produce the time that level jumps to level rebound first.
3. control method according to claim 1, the current change quantity of one of them switch periods internal inductance is recorded by the current sensor be applied on DC-AC inverter.
4. control method according to claim 1, in one of them switch periods, the voltage variety of electric capacity obtains for the register storing the capacitance voltage difference between two adjacent switch cycles by increasing.
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|---|---|---|---|
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| TWI626459B (en) * | 2016-08-17 | 2018-06-11 | 財團法人工業技術研究院 | Sensorless measurement method and device for filter capacitor current by using a state observer |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103715872A (en) * | 2014-01-03 | 2014-04-09 | 深圳市金宏威技术股份有限公司 | Power supply and pulse width modulation generating method and device |
| CN104362850A (en) * | 2014-11-19 | 2015-02-18 | 中国科学院微电子研究所 | Control method for voltage-reduction direct-current to direct-current converter |
-
2015
- 2015-06-24 CN CN201510355880.9A patent/CN105099254A/en active Pending
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103715872A (en) * | 2014-01-03 | 2014-04-09 | 深圳市金宏威技术股份有限公司 | Power supply and pulse width modulation generating method and device |
| CN104362850A (en) * | 2014-11-19 | 2015-02-18 | 中国科学院微电子研究所 | Control method for voltage-reduction direct-current to direct-current converter |
Non-Patent Citations (3)
| Title |
|---|
| BO LI等: "A digital direct controller for buck converter", 《2014 12TH IEEE INTERNATIONAL CONFERENCE ON SOLID-STATE AND INTEGRATED CIRCUIT TECHNOLOGY》 * |
| BO LI等: "A Digital Dual-State-Variable Predictive Controller for High Switching Frequency Buck Converter With Improved Σ-Δ DPWM", 《IEEE TRANSACTIONS ON INDUSTRIAL INFORMATICS》 * |
| BO LI等: "An FPGA prototype of current and voltage predictive controller for high switching frequency buck converter", 《IECON 2012 - 38TH ANNUAL CONFERENCE ON IEEE INDUSTRIAL ELECTRONICS SOCIETY》 * |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| TWI626459B (en) * | 2016-08-17 | 2018-06-11 | 財團法人工業技術研究院 | Sensorless measurement method and device for filter capacitor current by using a state observer |
| US10103647B2 (en) | 2016-08-17 | 2018-10-16 | Industrial Technology Research Institute | Sensorless measurement method and device for filter capacitor current by using a state observer |
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Application publication date: 20151125 |