CN104617771A - Switching power converter system and control method thereof - Google Patents
Switching power converter system and control method thereof Download PDFInfo
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- CN104617771A CN104617771A CN201510101176.0A CN201510101176A CN104617771A CN 104617771 A CN104617771 A CN 104617771A CN 201510101176 A CN201510101176 A CN 201510101176A CN 104617771 A CN104617771 A CN 104617771A
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- error amplification
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- power converter
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
Abstract
The invention provides a switching power converter system. The system consists of a switching power converter, a feedback circuit, an error amplifying circuit, a first capacitor, a ripple generating circuit and a constant on-time control circuit. The error amplifying circuit forms a first error amplifying signal and a current error amplifying signal according to a feedback signal and a reference signal; the first capacitor converts the current error amplifying signal into a voltage cross-conduction amplifying signal. A second error amplifying signal is generated by superposing a ripple signal and the voltage cross-conduction amplifying signal. The first error amplifying signal is compared with the second error amplifying signal to generate a constant on-time control signal to control the switching power converter system, so that the switching power converter system is smaller in output ripples, higher in transient response, and higher in output precision.
Description
Technical field
The present invention relates to circuit field.The present invention more specifically but be not limited to relate to switch power converter system and control method.
Background technology
In field of switch power, the switch power converter system of constant on-time control model switches due to its superior load transient response, simple internal structure and level and smooth mode of operation, is widely used in the industry.
Constant on-time type switch power converter of the prior art uses the ripple on feedback voltage to compare usually, in order to trigger internal timer, completes the setting of constant on-time.But the ripple on feedback voltage depends on output voltage.When the ripple of output voltage is less, the ripple on feedback voltage is also less, and transient response can be brought slow, and control precision reduces, and antijamming capability such as to weaken at the problem.And when the ripple of output voltage is larger, can cause damage to load life again.
Therefore, how while guarantee transient response performance and output accuracy, reduce ripple to the impact of load as far as possible, become the test of the switch power converter system to constant on-time control model.
Summary of the invention
The present invention considers one or more problem of the prior art, proposes a kind of switch power converter system and control circuit thereof and control method.
A first aspect of the present invention, proposes a kind of switch power converter system, it is characterized in that, described switch power converter system comprises: switch power converter, there is power switch, by turning on and off of described power switch, an input voltage is converted to an output voltage; Feedback circuit, receives described output voltage, generates feedback signal; Error amplifying circuit, couples described feedback circuit, according to described feedback signal and a reference signal, forms the first error amplification signal at the first output, forms current error amplifying signal at the second output; First electric capacity, be couple between the second output of described error amplifying circuit and system reference ground, described current error amplifying signal is converted to a voltage mutual conductance amplifying signal, wherein, when described output voltage changes, changing in the opposite direction of described first error amplification signal and described current error amplifying signal; Ripple signal generator, produce a ripple signal, described ripple signal superposes with described mutual conductance amplifying signal, generates the second error amplification signal; Comparator, receives and compares, at output production burst signal described first error amplification signal and described second error amplification signal; Constant on-time control circuit, receives described pulse signal, according to described pulse signal, exports constant on-time control signal to switch power converter, for the power switch in control switch power supply changeover device at output.
In one embodiment, described ripple signal generator comprises the RC network be made up of ripple resistance and ripple capacitances in series, the wherein first end receiving key signal of ripple resistance, the first end of ripple electric capacity couples the second end of ripple resistance, second end of ripple electric capacity is couple to the first electric capacity, output ripple signal, superposes generation second error amplification signal with voltage mutual conductance amplifying signal.
In another embodiment, described error amplifying circuit comprises: operational amplifier, has in-phase input end, inverting input and an output, inverting input receives described feedback signal, and in-phase input end receives described reference signal, and output exports described first error amplification signal; Trsanscondutance amplifier, has in-phase input end, inverting input and an output, and in-phase input end receives described feedback signal, and inverting input receives described reference signal, and output exports described current error amplifying signal.
Described error amplifying circuit comprises in another embodiment: the operational amplifier of dual output, there is in-phase input end, inverting input, in-phase output end and reversed-phase output, wherein, in-phase input end receives described reference signal, inverting input receives described feedback signal, in-phase output end exports described first error amplification signal, and reversed-phase output exports an anti-phase error amplification signal, and described anti-phase error amplification signal is the complementary signal of described first error amplification signal; Differential transconductance, has in-phase input end, inverting input and output.Wherein inverting input receives described first error amplification signal, and in-phase input end receives described anti-phase error amplification signal, output output current error amplification signal.
A second aspect of the present invention, propose a kind of switch power controller, switching signal is produced for the power switch in control switch power supply changeover device, convert an input voltage to an output voltage, it is characterized in that, described switch power controller comprises: feedback circuit, receives described output voltage, generates feedback signal; Error amplifying circuit, couples described feedback circuit, according to described feedback signal and a reference signal, forms the first error amplification signal at the first output, forms current error amplifying signal at the second output; First electric capacity, be couple between the second output of described error amplifying circuit and system reference ground, described current error amplifying signal is converted to a voltage mutual conductance amplifying signal, wherein, when described output voltage changes, changing in the opposite direction of described first error amplification signal and described current error amplifying signal; Ripple signal generator, produce a ripple signal, described ripple signal superposes with described mutual conductance amplifying signal, generates the second error amplification signal; Comparator, receives and compares, at output production burst signal described first error amplification signal and described second error amplification signal; Constant on-time control circuit, receives described pulse signal, according to described pulse signal, exports constant on-time control signal to switch power converter, for the power switch in control switch power supply changeover device at output.
A third aspect of the present invention, propose a kind of method of control switch Power converter system, it is characterized in that, described method comprises: the output voltage according to switch power converter system produces feedback signal; According to described feedback signal and reference signal, produce the first error amplification signal and current error amplifying signal, and current error amplifying signal is converted to voltage mutual conductance amplifying signal; Produce ripple signal and superpose generation second error amplification signal with described voltage mutual conductance amplifying signal; According to the first error amplification signal and the second error amplification signal, produce constant on-time control signal, the power switch in control switch Power converter system.
Compared to existing technology, the present invention when switch power converter system output voltage ripple is less, can improves transient state input response performance, increases system rejection to disturbance ability and control precision.
Accompanying drawing explanation
Figure 1 shows that the system block diagram of the switch power converter system 10 according to one embodiment of the invention.
Fig. 2 shows a physical circuit schematic diagram of the switch power converter system 10 according to one embodiment of the invention.
Fig. 3 shows the circuit diagram of error amplifying circuit 103 according to another embodiment of the present invention.
Fig. 4 is the work wave schematic diagram of Fig. 1 breaker in middle Power converter system 10 according to one embodiment of the invention.
Fig. 5 shows the electrical block diagram of constant on-time circuit 107 according to an embodiment of the invention.
Fig. 6 shows the system block diagram of switch power converter system 60 according to another embodiment of the present invention.
Fig. 7 shows the workflow diagram of the method 700 of a kind of control switch Power converter system according to one embodiment of the invention.
The Reference numeral running through institute's drawings attached identical represents identical parts or feature.
Embodiment
Specific embodiment hereinafter described represents exemplary embodiment of the present invention, and be only in essence example illustrate and unrestricted.In the description, mention that " embodiment " or " embodiment " mean to comprise at least one embodiment of the present invention in conjunction with the special characteristic described by this embodiment, structure or characteristic.Term " in one embodiment " in the description each position occurs all not relating to identical embodiment, neither mutually get rid of other embodiments or various embodiments.All features disclosed in this specification, or the step in disclosed all methods or process, except mutually exclusive feature and/or step, all can combine by any way.
Describe the specific embodiment of the present invention in detail below with reference to the accompanying drawings.The Reference numeral running through institute's drawings attached identical represents identical parts or feature.
Figure 1 shows that the system block diagram of the switch power converter system 10 according to one embodiment of the invention.As shown in Figure 1, switch power converter system 10 comprises switch power converter 101 and system controller.Switch power converter 10 has power switch, turning on and off by power switch, and an input voltage VIN is converted to an output voltage VO UT.In one embodiment, power switch turn on and off generation switching signal SW.System controller comprises feedback circuit 102, error amplifying circuit 103, the first electric capacity 104, ripple signal generator 105, comparator 106, and constant on-time control circuit 107.Wherein, feedback circuit 102 receives output voltage VO UT, generates feedback signal VFB.The input of error amplifying circuit 103 couples feedback circuit 102, according to feedback signal VFB and reference signal VREF, exports a first error amplification signal VEAO1 at the first output, exports a current error amplifying signal IEAO at the second output.First electric capacity 104 is couple between the second output of error amplifying circuit 103 and system reference ground GND, current error amplifying signal IEAO is converted to a voltage mutual conductance amplifying signal VTG, wherein, when output voltage VO UT changes, the first error amplification signal VEAO1 and current error amplifying signal IEAO changes in the opposite direction.Herein, the change direction of the first error amplification signal VEAO1 and current error amplifying signal IEAO points to positive voltage/sense of current or negative voltage/sense of current change, but not the change of voltage/current order of magnitude.Ripple signal generator 105 produces a ripple signal VRAMP, and ripple signal VRAMP superposes with voltage mutual conductance amplifying signal VTG, generates the second error amplification signal VEAO2.Comparator 106 receives and compares the first error amplification signal VEAO1 and the second error amplification signal VEAO2, at output production burst signal Pulse.Constant on-time control circuit 107 return pulse signal Pulse, according to pulse signal Pulse, exports constant on-time control signal PWM to switch power converter 101, for the power switch in control switch power supply changeover device 101 at output.
Wherein in one embodiment, ripple signal VRAMP produces according to switching signal SW.The value of switching signal SW can turn on and off according to the power switch in switch power converter 101, changes between VIN and 0.
The value of the first error amplification signal VEAO1 and the proportional relation of difference of reference signal VREF and feedback signal VFB in one embodiment, that is:
VEAO1＝A(VREF-VFB)
Wherein A can be arbitrary constant.
Voltage mutual conductance amplifying signal VTG is directly proportional to the difference of reference signal VREF to feedback signal VFB relative to the rate of change of time, is inversely proportional to, that is: with the capacitance of the first electric capacity 104
dVTG/dt＝(VFB-VREF)*K/C1
Wherein K can be arbitrary constant, and C1 is the capacitance of the first electric capacity 104.
Fig. 2 shows a physical circuit schematic diagram of the switch power converter system 10 according to one embodiment of the invention.As shown in Figure 2, in the illustrated embodiment, switch power converter 101 is synchronous rectification step-down (Buck) transducer, comprises main switch 201, synchronous rectification switch 202, outputting inductance 203 and output capacitance 204.Have average technical staff in this area can understand, in further embodiments, switch power converter 101 may use rectifier diode to replace synchronous rectification switch 202.In other embodiments, switch power converter 101 may have the known topology of other those skilled in that art, as boosting (Boost) transducer, buck (Buck-Boost) transducer, normal shock (Forward) transducer, flyback (Fly-back) transducer etc.
Feedback circuit 102 comprises the voltage that the resitstance voltage divider 205, feedback signal VFB be made up of resistance R1 and R2 is R1 and R2 common port place.Error amplifying circuit 103 comprises operational amplifier (OPA) 206, trsanscondutance amplifier (OTA) 207.In certain embodiments, error amplifying circuit 103 also may comprise rear class buffer.Operational amplifier 206 has in-phase input end, inverting input and an output, inverting input receiving feedback signals VFB, and in-phase input end receives reference signal VREF, and output exports the first error amplification signal VEAO1.Trsanscondutance amplifier 207 has in-phase input end, inverting input and an output, in-phase input end receiving feedback signals VFB, and inverting input receives reference signal VREF, output output current error amplification signal IEAO.First electric capacity 104 is coupled between the output of trsanscondutance amplifier 207 and system reference ground, for converting current error amplifying signal IEAO to voltage signal, and coating-forming voltage mutual conductance amplifying signal VTG.
Ripple signal generator 105 comprises the RC network be composed in series by resistance Rinj electric capacity Cinj.Wherein the first end of resistance Rinj is couple to the common port of main switch 201 and synchronous rectification switch 202, receiving key signal SW.Second end of the first end coupling resistance Rinj of electric capacity Cinj, the second end output ripple signal VRAMP of electric capacity Cinj, superposes generation second error amplification signal VEAO2 with voltage mutual conductance amplifying signal VTG.
Have mean level technical staff in this area can understand, in other embodiments, ripple signal generator 105 or assembly wherein may have different structures to realize similar function.
Comparator 106 has in-phase input end, inverting input and output, and wherein in the illustrated embodiment, in-phase input end receives the first error amplification signal VEAO1, and inverting input receives the second error amplification signal VEAO2, output output pulse signal Pulse.In one embodiment, comparator 106 can be a hysteresis comparator.
Constant on-time control circuit 107 comprises a timer 208.Timer 208 is couple to the output of comparator 106, according to pulse signal Pulse, produces output signal, as constant on-time control signal PWM at output.In the illustrated embodiment, switch power converter system 10 also has logical circuit 210, be couple to the output of timer 208, constant on-time control signal PWM is converted into main switch control signal HSG and synchronous rectification switch control signal LSG, drives main switch 201 and synchronous rectification switch 202.In other embodiments, constant on-time control signal PWM may directly control main switch 201.
Have average technical staff in this area can understand, in other embodiments, switch power converter system 10 may have and is different from the circuit structure shown in Fig. 2 and assembly.
Fig. 3 shows the circuit diagram of error amplifying circuit 103 according to another embodiment of the present invention.As shown in Figure 3, error amplifying circuit 103 comprises operational amplifier 301 and the differential transconductance 302 of dual output.In the illustrated embodiment, operational amplifier 301 has in-phase input end PIN, inverting input NIN, in-phase output end POUT and reversed-phase output NOUT.Wherein, in-phase input end PIN receives reference signal VREF, inverting input NIN receiving feedback signals VFB.In-phase output end POUT exports the first error amplification signal VEAO1, and reversed-phase output NOUT exports an anti-phase error amplification signal VRE, and wherein anti-phase error amplification signal VRE is the complementary signal of the first error amplification signal VEAO1, i.e. VRE=-VEAO1.Differential transconductance 302 has in-phase input end, inverting input and output.Wherein inverting input receives the first error amplification signal VEAO1, and in-phase input end receives anti-phase error amplification signal VRE, output output current error amplification signal IEAO.
In the illustrated embodiment,
VEAO1＝Av(VREF-VFB)
Wherein Av is the open-loop gain of operational amplifier 301
In like manner, VRE=Av (VFB-VREF)
Then IEAO=Gm* (VRE-VEAO1)=2Gm*Av (VFB-VREF)
Wherein Gm is the transadmittance gain of differential transconductance 302.
Like this, when IEAO is converted to voltage mutual conductance amplifying signal VTG by the first electric capacity 104,
Wherein, C1 is the capacitance of the first electric capacity 104.
In the illustrated embodiment, operational amplifier 301 can be complementary metal oxide semiconductors (CMOS) (CMOS) type operational amplifier, include the first PMOS transistor PM1, second PMOS transistor PM2, first nmos pass transistor NM1, second nmos pass transistor NM2, the first resistance R1 and the second resistance R2 and current source Iss.Together with wherein the first PMOS transistor PM1 is coupled in the source electrode of the second PMOS transistor PM2, the grid of the first PMOS transistor PM1 receives the grid of reference signal VREF, the second PMOS transistor PM2 as inverting input NIN receiving feedback signals VFB as in-phase input end PIN.The drain electrode of the first nmos pass transistor NM1, as reversed-phase output NOUT, couples the drain electrode of the first PMOS transistor PM1, and the drain electrode of the second nmos pass transistor NM2, as in-phase output end POUT, couples the drain electrode of the second PMOS transistor PM2.Resistance R1 and R2 coupled in series are between the drain electrode and the drain electrode of the second nmos pass transistor NM2 of the first nmos pass transistor NM1.The grid of the first nmos pass transistor NM1 and the grid of the second nmos pass transistor NM2 are couple to the common port of resistance R1 and R2 jointly.The source electrode of the first nmos pass transistor NM1 and the source electrode of the second nmos pass transistor NM2 are connected to system reference ground GND.Current source Iss is coupled between power source voltage Vcc and the source electrode of PM1, PM2.
Differential transconductance 302 can be a CMOS trsanscondutance amplifier, comprises the 3rd PMOS PM3, the 4th PMOS PM4, the 3rd NMOS tube NM3, the 4th NMOS tube, the 3rd resistance R3 and the 4th resistance R4.Wherein the 3rd PMOS PM3,3rd NMOS tube NM3 and the 3rd resistance R3 sequential series are in power source voltage Vcc and systematically form the first branch road between GND, 4th PMOS PM4, the 4th NMOS tube NM4 and the 4th resistance R4 sequential series are in power source voltage Vcc and systematically form the second branch road between GND.The grid of the 3rd NMOS tube NM3 receives anti-phase error amplification signal VRE, and the grid of the 4th NMOS tube NM4 receives the first error amplification signal VEAO1.The drain electrode of the 3rd NMOS tube NM3 couples the grid of the 3rd PMOS and the 4th PMOS.The drain electrode place output current error amplification signal IEAO of the 4th NMOS tube.
Have average technical staff in this area can understand, in other embodiments, operational amplifier 301 and differential transconductance 302 can have the circuit structure be different from illustrated embodiment, and realize close function.Such as see in certain embodiments, the PMOS in operational amplifier 301 and differential transconductance 302 can be replaced by positive-negative-positive bipolar transistor (BJT).
Fig. 4 is the work wave schematic diagram of Fig. 1 breaker in middle Power converter system 10 according to one embodiment of the invention.Below in conjunction with Fig. 4, the operation principle of the switch power converter system 10 shown in Fig. 1 is explained.For ease of understanding, in Fig. 4, have ignored the ripple come from feedback signal VFB, and static direct current is biased.Before the T1 moment, system is in steady-working state.Concrete, error amplifying circuit 103 export the first error amplification signal VEAO1 and can be considered constant, VEAO1=A (VREF-VFB).Same, in the steady state, the fluctuation of IEAO1 to the voltage mutual conductance amplifying signal VTG that the first electric capacity 104 discharge and recharge causes is very little, and therefore VTG also can be considered constant and a little more than VEAO1.The ripple signal VRAMP produced from ripple signal generator 105 superposes with voltage mutual conductance amplifying signal VTG, generates the second error amplification signal VEAO2.Second error amplification signal VEAO2 fluctuates up and down near voltage mutual conductance amplifying signal VTG.When VEAO2 drop to same VEAO1 equal time, the Pulse signal on comparator 106 output can generate a short pulse, controls constant on-time control circuit 107 and starts timing, and make switch power converter 100 enter ON time.The ripple signal VRAMP drive second error amplification signal VEAO2 that starts to rise rises.After constant on-time ton terminates, constant on-time control circuit 107 makes system enter turn-off time toff, now ripple signal VRAMP makes VEAO2 start to decline, and again on comparator 106, triggers short pulse, enter the subsequent work cycle when VEAO2 is down to VEAO1.
In the T1 moment, the output current IO UT of switch power converter system 10 is increased to I2 from I1 suddenly, and output voltage VO UT is acutely declined.Now feedback signal VFB follows output voltage VO UT decline, the corresponding rising of the first error amplification signal VEAO1.Meanwhile, current error amplifying signal IEAO declines with feedback signal VFB, suppresses VTG to increase.Like this, after system enters the turn-off time, VEAO2 can accelerate to decline under the acting in conjunction of VRAMP and IEAO, and faster same VEAO1 contacts generation short pulse, shortens the turn-off time toff of system, increases system duty cycle.Owing to creating more short pulses within the unit interval, output voltage VO UT can stop declining fast, rises and returns stable state.
Same, in the T2 moment, the output current of switch power converter system 10 reduces suddenly, makes output voltage VO UT acutely increase.Now feedback signal VFB follows output voltage VO UT rising, the corresponding decline of the first error amplification signal VEAO1.Simultaneously, current error amplifying signal IEAO rises with feedback signal VFB, promote that VTG increases, like this, after system enters the turn-off time, VTG's can the decline of partial offset VRAMP, the fall off rate of VEAO2 is slowed down, delay VEAO2 to contact with VEAO1, to extend the turn-off time TOFF of system, reduce system duty cycle.Because the short pulse quantity produced within the unit interval reduces, output voltage VO UT can stop rising fast, declines and returns stable state.
Thus, compared to existing technology, the switch power converter system 10 of the embodiment of the present invention, transient response performance obtains and significantly improves.
Fig. 5 shows the electrical block diagram of constant on-time circuit 107 according to an embodiment of the invention.As shown in Figure 5, constant on-time circuit 107 comprises a current source 501, timing comparator 502, timer capacitor 503, time switch 504, and trigger 508.Wherein, the first end that current source 501 couples timer capacitor 503 exports chrono-amperometric Itim, the second end ground connection of timer capacitor 503, and switch 504 is in parallel with timer capacitor 503.The in-phase input end of timing comparator 502 is couple to the first end of timer capacitor 503, and inverting input receives a reference voltage signal VREFA.In one embodiment, VREFA=k*VSW, k be less than or equal to arbitrarily 1 arithmetic number, VSW is the average voltage of switching signal SW.The set end (S) of trigger 508 and reset terminal (R) couple output and the return pulse signal Pulse of timing comparator 502 respectively, and output Q is couple to switch 504 and controls it and open or turn off, output
output pwm signal.
In the illustrated embodiment, current source 501 has benchmark branch road and controlled branch road, and benchmark branch road comprises reference resistance 505 and reference current source 506.Controlled branch road has controlled current source 507.Wherein, reference current source 506 couples the first end of reference resistance 505, output reference current Ib, and the first end of reference resistance 505 receives a reference voltage signal Vb simultaneously.Such Ib=Vb/R, R are the resistance of reference resistance 505.Vb=k*VIN in one embodiment, wherein VIN is system input voltage, k be aforementioned be less than or equal to arbitrarily 1 arithmetic number.
Controlled current source 507 exports chrono-amperometric Itim, and the size of chrono-amperometric is subject to the control of reference current Ib.In one embodiment, chrono-amperometric Itim=Ib.
With reference voltage signal VREFA=k*VSW, chrono-amperometric Itim=Ib is example, and within a work period, when Pulse direction switch signal 504 disconnects, chrono-amperometric Itim starts to charge to timer capacitor 503.When voltage on timer capacitor 503 arrives VREFA=k*VSW, the signal saltus step high level that timing comparator 502 exports, by time switch 504 conducting, timer capacitor 503 is discharged.In whole charging process, ON time ton=T*D=Ct*VREFA/Itim=Ct*R*VSW/VIN=Ct*R*D.Wherein T is system duty cycle, and Ct is the capacitance of timer capacitor 503, and D is system duty cycle, and R is the resistance of reference resistance 505.From above formula, in the Time constant turning circuit 107 of the present embodiment, by arranging suitable Ct and R value, the system duty cycle T of hope can be obtained, simultaneity factor operating frequency constant, not affecting by input voltage VIN and output voltage VO UT.
Fig. 6 shows the system block diagram of switch power converter system 60 according to another embodiment of the present invention.Compare the switch power converter system 10 shown in Fig. 1, switch power converter system 60 adds a clamper module 601.Between the homophase that clamper module 601 is coupled in comparator 106 and inverting input, under being in underload in system time, clamper first error amplification signal VEAO1.
When system is under underload, VFB may be greater than VREF for a long time, causes VEAO1 well below VEAO2.In each turn-off time toff, ripple signal VRAMP needs to make VEAO2 long period that declines continuously that VEAO2 just can be made with the equal triggering short pulse of VEAO1.Like this when system generation transient changing, VEAO1 and VEAO2 cannot cross in time, and transient response performance will significantly reduce under underload.
Clamper module 601 receives the first error amplification signal VEAO1 and the second error amplification signal VEAO2, under system is in light-load state by the first error amplification signal VEAO1 clamper in the position being not less than fixed bias Vbias than the second error amplification signal VEAO2, i.e. VEAO1 >=VEAO2-Vbias.
There is in this area mean level technical staff can understand, in other embodiments, clamper module 601 also can by carrying out clamper to the second error amplification signal VEAO2 or voltage mutual conductance amplifying signal VTG, second error amplification signal VEAO2 or voltage mutual conductance amplifying signal VTG is compared VEAO1 not higher than a fixed bias, reaches identical effect.
Like this, when system is in underload, in turn-off time toff, the difference between the first error amplification signal VEAO1 and the second error amplification signal VEAO2 is not all the time higher than Vbias.Fall back in the process of VEAO1 position at the second error amplification signal VEAO2, if there is transient state sudden change, such as load increases suddenly, then VEAO2 and VEAO1 at most only needs to cross over fixed bias Vbias and can produce new pulse, substantially increases transient response performance.
Fig. 7 shows the workflow diagram of the method 700 of a kind of control switch Power converter system according to one embodiment of the invention.As shown in Figure 7, the method comprises: step 701: the output voltage VO UT according to switch power converter system produces feedback signal VFB; Step 702, according to feedback signal VFB and reference signal VREF, produces the first error amplification signal VEAO1 and current error amplifying signal IEAO, and current error amplifying signal IEAO is converted to voltage mutual conductance amplifying signal VTG; Step 703, produces ripple signal VRAMP and superposes generation second error amplification signal VEAO2 with voltage mutual conductance amplifying signal VTG; Step 704: the first error amplification signal VEAO1 and the second error amplification signal VEAO2, produces constant on-time control signal PWM, the power switch in control switch Power converter system.
In one embodiment, step 702 specifically comprises: according to feedback signal VFB and reference signal VREF, produces the first error amplification signal VEAO1, and anti-phase error amplification signal VRE, and wherein VRE is the complementary signal of VEAO1; According to the first error amplification signal VEAO1 and anti-phase error amplification signal VRE, generation current error amplification signal IEAO.
In one embodiment, the method producing constant on-time control signal PWM in step 704 is: according to the first error amplification signal VEAO1 and the second error amplification signal VEAO2, produces a pulse signal Pulse; According to pulse signal Pulse, input voltage VIN and a switching signal SW, produce constant on-time control signal PWM.
Wherein, when pulse signal Pulse producing short pulse, pwm signal becomes high level, produces a chrono-amperometric Itim according to input voltage VIN, and size and the input voltage VIN of this chrono-amperometric Itim are proportional.Chrono-amperometric Itim charges to a timer capacitor, and when the voltage on timer capacitor equals a reference voltage V REFA, pwm signal falls low level after rise, and wherein VREFA is proportional with the mean value of switching signal SW.
In one embodiment, this workflow may further include: step 705: according to the first error amplification signal VEAO1 and the second error amplification signal VEAO2, carry out clamp when system is in underload to the first error amplification signal VEAO1.
Clamper is carried out to the first error amplification signal VEAO1, can by the first error amplification signal VEAO1 clamper in the position comparing the second error amplification signal VEAO2 and be not less than fixed bias Vbias, i.e. VEAO1 >=VEAO2-Vbias.
About foregoing, obvious other remodeling a lot of of the present invention and change are also feasible.Here should be understood that in the protection range contained at the claims of enclosing, the present invention can apply not to be had specifically described technology herein and implement.Certainly it is also to be understood that, because foregoing only relates to preferred embodiment of the present invention, so can also much remodeling be carried out and do not depart from the spirit of the present invention and protection range that the claim of enclosing contains.Due to disclosed be only preferred embodiment, those of ordinary skill in the art can infer different remodeling and not depart from the spirit of the present invention and protection range that are defined by the claim of enclosing.
Claims (12)
1. a switch power converter system, is characterized in that, described switch power converter system comprises:
Switch power converter, has power switch, by turning on and off of described power switch, an input voltage is converted to an output voltage;
Feedback circuit, receives described output voltage, generates feedback signal;
Error amplifying circuit, couples described feedback circuit, according to described feedback signal and a reference signal, forms the first error amplification signal at the first output, forms current error amplifying signal at the second output;
First electric capacity, be couple between the second output of described error amplifying circuit and system reference ground, described current error amplifying signal is converted to a voltage mutual conductance amplifying signal, wherein, when described output voltage changes, changing in the opposite direction of described first error amplification signal and described current error amplifying signal;
Ripple signal generator, produces a ripple signal, and described ripple signal superposes with described voltage mutual conductance amplifying signal, generates the second error amplification signal;
Comparator, receives and compares, at output production burst signal described first error amplification signal and described second error amplification signal; And
Constant on-time control circuit, receives described pulse signal, according to described pulse signal, exports constant on-time control signal to switch power converter, for the power switch in control switch power supply changeover device at output.
2. switch power converter system as claimed in claim 1, it is characterized in that, the value of described first error amplification signal and the proportional relation of difference of described reference signal and described feedback signal, described voltage mutual conductance amplifying signal is directly proportional to the difference of described feedback signal and described reference signal relative to the rate of change of time, is inversely proportional to the capacitance of described first electric capacity.
3. switch power converter system as claimed in claim 1, it is characterized in that, ripple signal generator comprises the RC network be made up of ripple resistance and ripple capacitances in series, the wherein first end receiving key signal of ripple resistance, the first end of ripple electric capacity couples the second end of ripple resistance, and the second end of ripple electric capacity is couple to the first electric capacity.
4. switch power converter system as claimed in claim 1, it is characterized in that, described error amplifying circuit comprises:
Operational amplifier, has in-phase input end, inverting input and an output, and inverting input receives described feedback signal, and in-phase input end receives described reference signal, and output exports described first error amplification signal;
Trsanscondutance amplifier, has in-phase input end, inverting input and an output, and in-phase input end receives described feedback signal, and inverting input receives described reference signal, and output exports described current error amplifying signal.
5. switch power converter system as claimed in claim 1, it is characterized in that, described error amplifying circuit comprises:
The operational amplifier of dual output, there is in-phase input end, inverting input, in-phase output end and reversed-phase output, wherein, in-phase input end receives described reference signal, inverting input receives described feedback signal, in-phase output end exports described first error amplification signal, and reversed-phase output exports an anti-phase error amplification signal, and described anti-phase error amplification signal is the complementary signal of described first error amplification signal;
Differential transconductance, has in-phase input end, inverting input and output.Wherein inverting input receives described first error amplification signal, and in-phase input end receives described anti-phase error amplification signal, output output current error amplification signal.
6. switch power converter system as claimed in claim 5, it is characterized in that, operational amplifier includes the first PMOS transistor, the second PMOS transistor, the first nmos pass transistor, the second nmos pass transistor, the first resistance, the second resistance and current source.Together with wherein the first PMOS transistor is coupled in the source electrode of the second PMOS transistor, the grid of the first PMOS transistor receives reference signal as in-phase input end, the grid of the second PMOS transistor is as inverting input receiving feedback signals, the drain electrode of the first nmos pass transistor is as reversed-phase output, couple the drain electrode of the first PMOS transistor, the drain electrode of the second nmos pass transistor is as in-phase output end, couple the drain electrode of the second PMOS transistor, first resistance and the second resistant series are coupled between the drain electrode of the first nmos pass transistor and the drain electrode of the second nmos pass transistor, the grid of the first nmos pass transistor and the grid of the second nmos pass transistor are couple to the common port of the first resistance and the second resistance jointly, the source electrode of the first nmos pass transistor and the source electrode of the second nmos pass transistor are connected to system reference ground, current source is coupled between the source electrode of supply voltage and the first PMOS transistor,
Differential transconductance comprises the 3rd PMOS, the 4th PMOS, the 3rd NMOS tube, the 4th NMOS tube, the 3rd resistance and the 4th resistance.Wherein the 3rd PMOS, 3rd NMOS tube and the 3rd resistance sequential series in supply voltage and systematically between form the first branch road, 4th PMOS, 4th NMOS tube and the 4th resistance sequential series in supply voltage and systematically between form the second branch road, the grid of the 3rd NMOS tube receives anti-phase error amplification signal, the grid of the 4th NMOS tube receives the first error amplification signal, the drain electrode of the 3rd NMOS tube couples the grid of the 3rd PMOS and the 4th PMOS, the drain electrode place output current error amplification signal of the 4th NMOS tube.
7. switch power converter system as claimed in claim 1, it is characterized in that, described switch power converter system also has clamper module, between the in-phase input end being coupled in described comparator and inverting input, for under being in underload in system time, the first error amplification signal described in clamper.
8. switch power converter system as claimed in claim 8, it is characterized in that, described clamper module receives described first error amplification signal and described second error amplification signal, under system is in light-load state by described first error amplification signal clamper in the position comparing described second error amplification signal and be not less than a fixed bias.
9. a switch power controller, convert an input voltage to an output voltage, it is characterized in that, described switch power controller comprises:
Feedback circuit, receives described output voltage, generates feedback signal;
Error amplifying circuit, couples described feedback circuit, according to described feedback signal and a reference signal, forms the first error amplification signal at the first output, forms current error amplifying signal at the second output;
First electric capacity, be couple between the second output of described error amplifying circuit and system reference ground, described current error amplifying signal is converted to a voltage mutual conductance amplifying signal, wherein, when described output voltage changes, changing in the opposite direction of described first error amplification signal and described current error amplifying signal;
Ripple signal generator, produce a ripple signal, described ripple signal superposes with described mutual conductance amplifying signal, generates the second error amplification signal;
Comparator, receives and compares, at output production burst signal described first error amplification signal and described second error amplification signal;
Constant on-time control circuit, receives described pulse signal, according to described pulse signal, exports constant on-time control signal to switch power converter, for the power switch in control switch power supply changeover device at output.
10. a method for control switch Power converter system, is characterized in that, described method comprises:
Output voltage according to switch power converter system produces feedback signal;
According to described feedback signal and reference signal, produce the first error amplification signal and current error amplifying signal, and current error amplifying signal is converted to voltage mutual conductance amplifying signal;
Produce ripple signal and superpose generation second error amplification signal with described voltage mutual conductance amplifying signal;
According to the first error amplification signal and the second error amplification signal, produce constant on-time control signal, the power switch in control switch Power converter system.
The method of 11. control switch Power converter system according to claim 10, it is characterized in that, described method comprises:
According to described feedback signal and described reference signal, produce the first error amplification signal and anti-phase error amplification signal, wherein said anti-phase error amplification signal is the complementary signal of described first error amplification signal;
According to described first error amplification signal and described anti-phase error amplification signal, produce described current error amplifying signal.
The method of 12. control switch Power converter system according to claim 10, it is characterized in that described method comprises further according to described first error amplification signal and described second error amplification signal, under system is in light-load conditions, clamp is carried out to described first error amplification signal.
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