CN103856061A - Full-range soft switching method of input-series output-paralleled phase-shifted full-bridge convertor - Google Patents

Full-range soft switching method of input-series output-paralleled phase-shifted full-bridge convertor Download PDF

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CN103856061A
CN103856061A CN201410063242.5A CN201410063242A CN103856061A CN 103856061 A CN103856061 A CN 103856061A CN 201410063242 A CN201410063242 A CN 201410063242A CN 103856061 A CN103856061 A CN 103856061A
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phase
bridge
conversion module
full
shifting full
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CN103856061B (en
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郭志强
沙德尚
廖晓钟
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Beijing Institute of Technology BIT
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    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Abstract

The invention relates to a full-range soft switching method of an input-series output-paralleled phase-shifted full-bridge convertor, and belongs to the technical field of isolated type direct current-direct current convertors. The method includes the steps that one series LC network is connected into the position between the center point of a leading bridge arm upper tube and a leading bridge arm lower tube of a first phase-shifted full-bridge conversion module and the center point of a lag bridge arm upper tube and a lag bridge arm lower tube of a second phase-shifted full-bridge conversion module, the other series LC network is connected into the position between the center point of a lag bridge arm upper tube and a lag bridge arm lower tube of the first phase-shifted full-bridge conversion module and the center point of a leading bridge arm upper tube and a leading bridge arm lower tube of the second phase-shifted full-bridge conversion module, and then zero-voltage switching of MOSFETs is achieved. The method can automatically adapt to different input voltages, output voltages and loads. According to the method, full-range soft switching of the phase-shifted full-bridge convertor can be achieved, efficiency of the whole convertor is improved, the method is suitable for the occasion where high-voltage input is converted into low-voltage output, and the requirements for the wide input voltage range, the wide output voltage range and the wide load change range are met.

Description

The gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter
Technical field
The present invention relates to a kind of gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter, belong to isolated DC direct current (DC-DC) converter technical field.
Background technology
High voltage input and low-voltage output extensive use in industry.In order to overcome the restriction of parts selection, the scheme that solves high voltage input and low-voltage output is roughly divided into: the series connection of (1) device; (2) multilevel converter; (3) series topology of converter.Device serial connection technology, because topology is simple, is applied in high voltage direct current transmission by ABB.In order to realize dividing equally of each device voltage, still the design of control system is proposed to very large test.Multilevel converter can adapt to the occasion of high input voltage, but in practical application still taking 3 gentle five level application as main.Along with the increase of level number, the complexity of control strategy sharply increases, and its reliability is reduced.Due to the complexity of first two technology, make converter input serial connection technology obtain people's attention.Converter input serial connection technology makes each converter bear a part of input voltage.2006 at IEEE TransactiononIndustryApplication[commercial Application periodical] deliver " Common-Duty-Ratio Control of Input-Series Connected Modular DC-DC Converters With Active Input Voltage and Load-Current Sharing " literary composition, adopt public duty ratio to realize the stable operation of input series and output parallel converter.2009 at IEEETransaction on Industrial Electronics[industrial electronic] deliver " Control Strategy for Input-Series – Output-Parallel Converters ", adopt the control strategy of initiatively all pressing to realize dividing equally of input series and output parallel phase-shifting full-bridge DC-DC inverter power.The research of input series winding output-parallel converter is very extensive, but is mostly confined to the research to control strategy, seldom the soft switch technique of input series and output parallel converter is studied.
Summary of the invention
The object of the invention is to be difficult for realizing no-voltage when the underloading and to open for solving in the phase-shifted full-bridge converter of input series and output parallel lagging leg the problem of (ZVS), proposed one and be applied under high pressure occasion, the phase-shifted full-bridge converter of input series and output parallel realizes that gamut is soft opens soft universal method.
Described gamut refers to that input voltage, output voltage and the load of phase-shifted full-bridge converter all can change, and the no-voltage that realizes leading-bridge and lagging leg switching tube in excursion is opened (Zerovoltageswitching, ZVS).
The gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter, specifically comprises the steps:
Step 1, comprising in the phase-shifted full-bridge converter of the first phase-shifting full-bridge conversion module and the second phase-shifting full-bridge conversion module, two module input voltages series connection, output voltage parallel connection.
The first phase-shifting full-bridge conversion module and the second phase-shifting full-bridge conversion module comprise eight switching tubes, be respectively pipe, lower pipe on the lagging leg of the first phase-shifting full-bridge conversion module, pipe, lower pipe on the leading-bridge of the first phase-shifting full-bridge conversion module, pipe, lower pipe on the lagging leg of the second phase-shifting full-bridge conversion module, pipe, lower pipe on the leading-bridge of the second phase-shifting full-bridge conversion module.
The mid point of looking for the leading-bridge top tube and down tube of the first phase-shifting full-bridge conversion module to connect.
Step 2, the mid point that finds the lagging leg top tube and down tube of the second phase-shifting full-bridge conversion module to connect.The no-load voltage ratio of the isolating transformer that the second phase-shifting full-bridge conversion module comprises is identical with the first phase-shifting full-bridge conversion module.
Step 3, between the mid point of the second phase-shifting full-bridge conversion module lagging leg top tube and down tube that the mid point of the leading-bridge top tube and down tube of the first phase-shifting full-bridge conversion module obtaining in step 1 and step 2 obtain, access a series LC network, described series LC network is formed by an inductance and a capacitances in series, and the position of inductance and electric capacity can exchange.
Step 4, the mid point that finds the first phase-shifting full-bridge conversion module lagging leg top tube and down tube to connect.
Step 5, the mid point that finds the second phase-shifting full-bridge conversion module leading-bridge top tube and down tube to connect.
Step 6, the mid point of the first phase-shifting full-bridge conversion module lagging leg top tube and down tube that obtain in step 4 and step 5 obtain accessing another series LC network between the mid point of lagging leg top tube and down tube of the second phase-shifting full-bridge conversion module, and the sense value of the inductance of this LC network and the capacitance of electric capacity are identical with the capacitance of electric capacity with the sense value of the inductance of the LC network in step 3.
Add after two series LC networks, eight switching tubes of the first phase-shifting full-bridge conversion module and the second phase-shifting full-bridge conversion module meet following sequential logic:
On the leading-bridge of the first phase-shifting full-bridge conversion module, the gate leve of pipe and pipe under the second phase-shifting full-bridge conversion module leading-bridge drives signal identical; Under the leading-bridge of the first phase-shifting full-bridge conversion module, the gate leve of pipe and pipe on the second phase-shifting full-bridge conversion module leading-bridge drives signal identical; Above-mentioned two groups to drive signal definitions be that leading-bridge drives signal, is respectively duty ratio and is 0.5 pulse width modulation (PWM) signal, and complementary, and two groups drive between signals and have dead band.
On the lagging leg of the first phase-shifting full-bridge conversion module, the gate leve of the lower pipe of pipe and the second phase-shifting full-bridge conversion module lagging leg drives signal identical; The gate leve of the lower pipe of the lagging leg of the first phase-shifting full-bridge conversion module and the upper pipe of the second phase-shifting full-bridge conversion module lagging leg drives signal identical; Above-mentioned two groups to drive signal definitions be that lagging leg drives signal, is also respectively duty ratio and is 0.5 pwm signal, and complementary, and two groups drive between signals and have dead band.
Step 7, on definition the first phase-shifting full-bridge conversion module leading-bridge, pipe drives the rising edge of signal to manage the size that the time between the rising edge that drives signal is phase shifting angle under the first phase-shifting full-bridge conversion module lagging leg.By regulating phase shifting angle size, control the output voltage of phase-shifted full-bridge converter:
The size of phase shifting angle has determined the size of current amplitude in action time of two series LC network both end voltage and two LC networks.Phase shifting angle increases, and output voltage reduces, and current amplitude in series LC network increases; Otherwise phase shifting angle reduces, output voltage increases, and the current amplitude in series LC network reduces.
In the time being output as constant voltage, input voltage raises and causes phase shifting angle to increase, thereby the current amplitude in series LC network increases, and the no-voltage that realizes each MOSFET is opened (ZVS).In the time that output voltage is constant and load reduces, phase shifting angle increases, and now the current amplitude in LC network increases, and the no-voltage that realizes MOSFET is opened (ZVS).When phase-shifting full-bridge underloading, also can realize ZVS.Change and the constant situation of output resistance at output voltage, in the time that output voltage is large, phase shifting angle reduces, and the electric current in series LC network reduces, and the no-voltage that now converter is realized MOSFET by transformer leakage inductance electric current is opened (ZVS).Along with output voltage reduces, power output also reduces, and phase shifting angle increases, and the current amplitude of series LC network increases, and now the soft switch of MOSFET is realized by the electric current in LC network.
Beneficial effect
The inventive method can adapt to different input voltages, output voltage and load automatically.The phase-shifted full-bridge converter obtaining according to the inventive method can be realized the soft switch of gamut, thereby can improve the efficiency of whole converter.Be applicable to the conversion occasion of high input voltage to low pressure output, and can meet the situation of wide input voltage range, wide output voltage range, wide load variations.
Brief description of the drawings
Fig. 1 is the input series and output parallel phase-shifted full-bridge converter topology diagram that adds two LC networks in embodiment;
Fig. 2 is the typical waveform that drives signal, transformer output voltage and current waveform, LC network both end voltage and electric current in embodiment, wherein (a) is large or input voltage is little at output voltage, and in the large situation of bearing power, phase shifting angle is little voltage and current waveform, (b) little at output voltage or input voltage is large, and in the little situation of power output, phase shifting angle is large voltage and current waveform.
Embodiment
Below in conjunction with drawings and Examples, the present invention is further described.
According to the method flow of summary of the invention, this embodiment proposes a kind of input series and output parallel phase-shifted full-bridge converter, comprises eight identical MOSFET(metal oxide semiconductor field effect tubes) Q 1, Q 2, Q 3, Q 4, Q 5, Q 6, Q 7, Q 8, two identical LC network (L r1and C r1, L r2and C r2), two identical input capacitance C d1and C d2, two transformer T r1and T r2, two output inductor L f1and L f2, filter capacitor C owith four rectifier diode D 1, D 2, D 3, D 4.
LC network comprises an inductance and a resistance, is in series.Q 1-Q 8for switching tube.Two input capacitance C d1and C d2play dividing potential drop.Transformer secondary is rectification circuit (is the full-wave rectification of transformer belt mid-point tap, or is the full-bridge rectification of a winding).
The annexation of above-mentioned part is: two input capacitance C d1and C d2in parallel with input voltage after series connection.The voltage that each electric capacity bears is equivalent to 1/2 of input voltage.C d1in parallel with the first phase-shifting full-bridge conversion module, C d2in parallel with the second phase-shifting full-bridge conversion module.
The composition of the first phase-shifting full-bridge conversion module and annexation are: MOSFETQ 1source electrode connect MOSFETQ 2drain electrode, MOSFETQ 3source electrode connect MOSFETQ 4drain electrode, Q 1, Q 2and Q 3, Q 4in parallel; Input voltage V inpositive pole connect respectively MOSFETQ 1drain electrode and MOSFETQ 3drain electrode, MOSFETQ 2source electrode and MOSFETQ 4source electrode be connected to C d1electronegative potential one side.Q 1source electrode and Q 3source electrode be connected to transformer T r1the two ends on former limit.Transformer T r1secondary be two windings, the upper end of two windings is Same Name of Ends; The Same Name of Ends of first winding is connected to diode D 1anode, different name end is connected with the Same Name of Ends of second winding, this tie point is transformer T r1the mid-point tap of secondary winding.Transformer T r1the different name end of second winding of secondary connect diode D 2anode.The negative electrode of diode D1 and D2 is connected, and is connected to inductance L simultaneously f1one end.
The composition of the second phase-shifting full-bridge conversion module and annexation are: MOSFETQ 5source electrode connect MOSFETQ 6drain electrode, MOSFETQ 7source electrode connect MOSFETQ 8drain electrode, Q 5, Q 6and Q 7, Q 8in parallel; MOSFETQ 5drain electrode connect MOSFETQ 7drain electrode, and be connected to C d2high potential one side; MOSFETQ 2source electrode connect MOSFETQ 4source electrode, and be connected to input voltage V innegative pole.Q 5source electrode and Q 7source electrode be connected to transformer T r2the two ends on former limit.Transformer T r2no-load voltage ratio and transformer T r1no-load voltage ratio identical.Transformer T r2secondary be two windings, the upper end of two windings is Same Name of Ends, the Same Name of Ends of first winding is connected to diode D 3anode, its different name end is transformer T r2the mid-point tap of secondary winding, and be connected with the Same Name of Ends of second winding.Transformer T r2the different name end of second winding of secondary connect diode D 4anode.Diode D 3and D 4negative electrode be connected, and be connected to inductance L f2one end.
L f1and L f2the other end positive pole that is output voltage, connect respectively filter capacitor C owith load resistance R o.Filter capacitor C owith load resistance R oparallel connection, C oand R orespectively connection transformer T of the other end r1the mid-point tap of secondary winding and transformer T r2the mid-point tap of secondary winding is the negative pole of output voltage.
Capacitor C r2and inductance L r2form a series LC network, input connects MOSFETQ 1source electrode, output is connected to MOSFETQ 7source electrode.
Capacitor C r1and inductance L r1formed another series LC network, input connects MOSFETQ 3source electrode, output is connected to MOSFETQ 5source electrode.
Capacitor C r1capacitance and capacitor C r2capacitance identical; Inductance L r1inductance value and inductance L r2inductance value identical.The position of inductance and electric capacity can exchange.
In the present embodiment, add the input series and output parallel phase-shifted full-bridge converter topological structure of two LC networks as shown in Figure 1, wherein rectification illustrates (still can adopt full-bridge rectification) as an example of full-wave rectification example.C d1and C d2for input dividing potential drop electric capacity, Q 1-Q 8for MOSFET; C j1-C j8for the junction capacitance of MOSFET; T r1and T r2for isolating transformer; D 1-D 4for rectifier diode, L f1and L f2for output inductor.C ofor output filter capacitor; R ofor load resistance.L r1and L r2for the inductance of series LC network, C r1and C r2for the electric capacity of series LC network.
Figure 2 shows that the MOSFETQ in described circuit 1-Q 8driving logical waveform, the voltage at transformer output voltage and electric current, series LC network two ends and flow through the current waveform of LC network.Wherein, Fig. 2 (a) is large or input voltage is little at output voltage, and bearing power is the situation of big space rate when large, and Fig. 2 (b) is little or input voltage is large at output voltage, and power output hour is the situation of little duty ratio.
Each MOSFETQ 1-Q 8driving signal meet following relation:
MOSFETQ 1and MOSFETQ 6driving signal identical; MOSFETQ 2and MOSFETQ 5driving signal identical; Above-mentioned two groups to drive signals to be respectively duty ratio be 0.5 pwm signal, and complementary.It is that leading-bridge drives signal that this group drives signal definition.MOSFETQ 1and MOSFETQ 2form the leading-bridge of the first phase-shifting full-bridge conversion module; MOSFETQ 5and MOSFETQ 6form the leading-bridge of the second phase-shifting full-bridge conversion module.
MOSFETQ 3and MOSFETQ 8driving signal identical; MOSFETQ 4and MOSFETQ 7driving signal identical; Above-mentioned two groups to drive signals to be also respectively duty ratio be 0.5 pwm signal, and complementary.It is that lagging leg drives signal that this group drives signal definition.MOSFETQ 3and MOSFETQ 4form the lagging leg of the first phase-shifting full-bridge conversion module; MOSFETQ 7and MOSFETQ 8form the lagging leg of the second phase-shifting full-bridge conversion module.
T in Fig. 2 0to t 8for the operation mode of half period.
As interval [t 1, t 2], lagging leg Q 3and Q 8turn-off simultaneously.Now, i p1and i r1while and C j3and C j4resonance, i p2and i r2while and C j7and C j8resonance.Work as t 2time, C j3and C j8voltage be charged to V in/ 2, C j4and C j7voltage be discharged into 0, now Q 4and Q 7body diode conducting.Work as t 3time, Q 4and Q 7no-voltage is opened (ZVS).
At interval [t 5, t 6], leading-bridge switch Q 1and Q 6turn-off i p1and i r2while and C j1and C j2resonance, i p2and i r1while and C j5and C j6resonance.Work as t 6time, C j1and C j6voltage be charged to V in/ 2, C j2and C j5voltage be discharged into 0, now Q 2and Q 5body diode conducting.Work as t 7time, Q 2and Q 5no-voltage is opened (ZVS).The mode of half period switching tube is similar to front half period in addition.
As shown in Figure 2, MOSFETQ 1and MOSFETQ 6drive signal rising edge to MOSFETQ 4and MOSFETQ 7driving the timing definition between signal rising edge is phase shifting angle.Drive signal and lagging leg to drive the output voltage of the big or small control change device of the phase shift of signal by leading-bridge; The size of phase shifting angle has also determined the action time of two LC network both end voltage, thereby has determined the size of current amplitude in two LC networks.
Phase shifting angle increases, and output voltage reduces; Otherwise phase shifting angle reduces, output voltage increases.As found out the increase along with phase shifting angle in 2 in figure, the current amplitude in series LC network increases.Otherwise phase shifting angle reduces, the current amplitude in series LC network reduces.In the time being output as constant voltage, input voltage raises and causes phase shifting angle to increase, thereby the current amplitude in LC network increases, and the no-voltage of each MOSFET is opened (ZVS) and more easily realized.In the time that output voltage is constant and load reduces, phase shifting angle also can increase, and now the current amplitude in series LC network increases, and the no-voltage that is also conducive to MOSFET is opened (ZVS).When phase-shifting full-bridge underloading, be difficult for realizing soft switch, so also can realize ZVS when this invention can ensure phase-shifting full-bridge underloading.Change and the constant situation of output resistance at output voltage, in the time that output voltage increases, phase shifting angle reduces, and the electric current in series LC network reduces.But the no-voltage that now converter still can be realized MOSFET by transformer leakage inductance electric current is opened (ZVS).Along with output voltage reduces, power output also reduces, and phase shifting angle increases, and the current amplitude of series LC network increases.Now the soft switch of MOSFET is realized by the electric current in LC network.Therefore, the present invention can adapt to different input voltages, output voltage and load automatically.The phase-shifted full-bridge converter obtaining according to the inventive method can be realized the soft switch of gamut.

Claims (4)

1. the gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter, is characterized in that: specifically comprise the steps:
Step 1, comprising in the phase-shifted full-bridge converter of the first phase-shifting full-bridge conversion module and the second phase-shifting full-bridge conversion module, the input voltage series connection of the first phase-shifting full-bridge conversion module and the second phase-shifting full-bridge conversion module, output voltage parallel connection;
The first phase-shifting full-bridge conversion module and the second phase-shifting full-bridge conversion module comprise eight switching tubes, be respectively pipe, lower pipe on the lagging leg of the first phase-shifting full-bridge conversion module, pipe, lower pipe on the leading-bridge of the first phase-shifting full-bridge conversion module, pipe, lower pipe on the lagging leg of the second phase-shifting full-bridge conversion module, pipe, lower pipe on the leading-bridge of the second phase-shifting full-bridge conversion module;
The mid point of looking for the leading-bridge top tube and down tube of the first phase-shifting full-bridge conversion module to connect;
Step 2, the mid point that finds the lagging leg top tube and down tube of the second phase-shifting full-bridge conversion module to connect; The no-load voltage ratio of the isolating transformer that the second phase-shifting full-bridge conversion module comprises is identical with the first phase-shifting full-bridge conversion module;
Step 3, between the mid point of the second phase-shifting full-bridge conversion module lagging leg top tube and down tube that the mid point of the leading-bridge top tube and down tube of the first phase-shifting full-bridge conversion module obtaining in step 1 and step 2 obtain, access a series LC network, described series LC network is formed by an inductance and a capacitances in series;
Step 4, the mid point that finds the first phase-shifting full-bridge conversion module lagging leg top tube and down tube to connect;
Step 5, the mid point that finds the second phase-shifting full-bridge conversion module leading-bridge top tube and down tube to connect;
Step 6, the mid point of the first phase-shifting full-bridge conversion module lagging leg top tube and down tube that obtain in step 4 and step 5 obtain accessing another series LC network between the mid point of lagging leg top tube and down tube of the second phase-shifting full-bridge conversion module, and the sense value of LC network inductance and the capacitance of electric capacity are identical with the capacitance of electric capacity with the sense value of LC network inductance in step 3;
Add after two series LC networks, eight switching tubes of the first phase-shifting full-bridge conversion module and the second phase-shifting full-bridge conversion module meet following sequential logic:
On the leading-bridge of the first phase-shifting full-bridge conversion module, the gate leve of pipe and pipe under the second phase-shifting full-bridge conversion module leading-bridge drives signal identical; Under the leading-bridge of the first phase-shifting full-bridge conversion module, the gate leve of pipe and pipe on the second phase-shifting full-bridge conversion module leading-bridge drives signal identical; On the leading-bridge of the first phase-shifting full-bridge conversion module under pipe and the second phase-shifting full-bridge conversion module leading-bridge under the leading-bridge of pipe, the first phase-shifting full-bridge conversion module on pipe and the second phase-shifting full-bridge conversion module leading-bridge pipe be leading-bridge driving signal, be respectively duty ratio and be 0.5 pulse width modulating signal, and complementary, between two groups of driving signals, there is dead band;
On the lagging leg of the first phase-shifting full-bridge conversion module, the gate leve of the lower pipe of pipe and the second phase-shifting full-bridge conversion module lagging leg drives signal identical; The gate leve of the lower pipe of the lagging leg of the first phase-shifting full-bridge conversion module and the upper pipe of the second phase-shifting full-bridge conversion module lagging leg drives signal identical; On the lagging leg of the first phase-shifting full-bridge conversion module, the lower pipe of lagging leg of the lower pipe of pipe and the second phase-shifting full-bridge conversion module lagging leg, the first phase-shifting full-bridge conversion module and the upper pipe of the second phase-shifting full-bridge conversion module lagging leg are that lagging leg drives signal, be respectively duty ratio and be 0.5 pulse width modulating signal, and complementary, between two groups of driving signals, there is dead band;
Step 7, on the first phase-shifting full-bridge conversion module leading-bridge, pipe drives the rising edge of signal to manage the size that the time between the rising edge that drives signal is phase shifting angle under the first phase-shifting full-bridge conversion module lagging leg; Adjusting phase shifting angle size, the output voltage of control phase-shifted full-bridge converter:
In the time being output as constant voltage, input voltage raises and causes phase shifting angle to increase, and the current amplitude in series LC network increases, and the no-voltage that realizes each MOSFET is open-minded; In the time that output voltage is constant and load reduces, phase shifting angle increases, and the current amplitude in LC network increases, and the no-voltage that realizes MOSFET is open-minded; When phase-shifting full-bridge underloading, also no-voltage can be realized open-minded; Change and the constant situation of output resistance at output voltage, in the time that output voltage is large, phase shifting angle reduces, and the electric current in series LC network reduces, and the no-voltage that converter is realized MOSFET by transformer leakage inductance electric current is open-minded; Along with output voltage reduces, power output also reduces, and phase shifting angle increases, and the current amplitude of series LC network increases, and realizes the soft switch of MOSFET.
2. the gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter according to claim 1, it is characterized in that: input voltage, output voltage and the load of phase-shifted full-bridge converter all can change, and it is open-minded in excursion, to realize the no-voltage of leading-bridge and lagging leg switching tube.
3. the gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter according to claim 1, is characterized in that: the position of inductance and electric capacity can exchange.
4. the gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter according to claim 1, is characterized in that: the size of phase shifting angle has determined the size of current amplitude in action time of two series LC network both end voltage and two LC networks.
CN201410063242.5A 2014-02-25 2014-02-25 The gamut soft-switching process of input series and output parallel phase-shifted full-bridge converter Expired - Fee Related CN103856061B (en)

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Cited By (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104716844A (en) * 2015-03-18 2015-06-17 江苏绿城信息技术有限公司 Input-parallel output-parallel modularized direct current converter with soft switch
CN104967309A (en) * 2015-07-09 2015-10-07 哈尔滨工业大学 Series-input voltage equalization control method of independent-output direct current converter
CN105006964A (en) * 2015-07-02 2015-10-28 北京交通大学 Multi-level equalizing resonance zero current soft switch DC-DC converter
CN106877683A (en) * 2017-03-27 2017-06-20 盐城工学院 The converter and its control method of a kind of suitable wide input voltage

Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101345473A (en) * 2008-05-04 2009-01-14 南京航空航天大学 Input-series-output-parallel automatic voltage equalizing DC transformer based on full-bridge topological structure
CN102013826A (en) * 2010-12-01 2011-04-13 北京理工大学 Stable current control method for input-series output-parallel high-frequency link inverter module
CN103269177A (en) * 2013-04-27 2013-08-28 南京航空航天大学 Distributed ISOP inverter and input voltage sharing and output same-amplitude control method thereof
TW201338386A (en) * 2012-03-13 2013-09-16 Univ Kun Shan Interleaved DC-DC zero-voltage switching converter

Patent Citations (4)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN101345473A (en) * 2008-05-04 2009-01-14 南京航空航天大学 Input-series-output-parallel automatic voltage equalizing DC transformer based on full-bridge topological structure
CN102013826A (en) * 2010-12-01 2011-04-13 北京理工大学 Stable current control method for input-series output-parallel high-frequency link inverter module
TW201338386A (en) * 2012-03-13 2013-09-16 Univ Kun Shan Interleaved DC-DC zero-voltage switching converter
CN103269177A (en) * 2013-04-27 2013-08-28 南京航空航天大学 Distributed ISOP inverter and input voltage sharing and output same-amplitude control method thereof

Non-Patent Citations (3)

* Cited by examiner, † Cited by third party
Title
DESHANG SHA ET AL.: "Digital Control Strategy for Input-Series-Output-Parallel Modular DC/DC Converters", 《JOURNAL OF POWER ELECTRONICS》 *
MANGESH BORAGE ET AL.: "A Full-Bridge DC-DC Converter With Zero-Voltage-Switching Over the Entire Conversion Range", 《IEEE TRANSACTIONS ON POWER ELECTRONICS》 *
YUNGTAEK JANG ET AL.: "A New ZVS-PWM Full-Bridge Converter", 《IEEE TRANSACTIONS ON POWER ELECTRONICS》 *

Cited By (6)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN104716844A (en) * 2015-03-18 2015-06-17 江苏绿城信息技术有限公司 Input-parallel output-parallel modularized direct current converter with soft switch
CN105006964A (en) * 2015-07-02 2015-10-28 北京交通大学 Multi-level equalizing resonance zero current soft switch DC-DC converter
CN105006964B (en) * 2015-07-02 2018-05-18 北京交通大学 A kind of more electric mean pressure resonant zero Sofe Switch DC-DC converters
CN104967309A (en) * 2015-07-09 2015-10-07 哈尔滨工业大学 Series-input voltage equalization control method of independent-output direct current converter
CN106877683A (en) * 2017-03-27 2017-06-20 盐城工学院 The converter and its control method of a kind of suitable wide input voltage
CN106877683B (en) * 2017-03-27 2019-03-12 盐城工学院 A kind of converter and its control method of suitable wide input voltage

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