CN103051241A - Self-circulation three-phase dual-voltage-reduction AC/DC (Alternating Current/Direct Current) converter - Google Patents

Abstract

The invention discloses a self-circulation three-phase dual-voltage-reduction AC/DC (Alternating Current/Direct Current) converter, belonging to the field of three-phase AC/DC conversion. The invention particularly relates to a topological structure of the self-circulation three-phase dual-voltage-reduction AC/DC converter, aiming at being applied to medium-power and high-power occasions. Compared with the traditional three-phase bridge type converter, the three-phase dual-voltage-reduction AC/DC converter has the advantages of reducing the content of current harmonic at the AC side under the condition of adopting a same space vector control algorithm, reducing the specification of a filter and achieving the purposes of bidirectional flowing and automatic switching of energy without causing extra switching loss. The three-phase dual-voltage-reduction AC/DC converter comprises a DC-side support capacitor, a three-phase upper bridge arm power tube, a three-phase lower bridge arm power tube, a three-phase upper bridge arm freewheel diode, a three-phase lower bridge arm freewheel diode, a three-phase first direct-connection-resisting filter inductor, a three-phase second direct-connection-resisting filter inductor and a three-phase self-circulation diode. According to the three-phase dual-voltage-reduction AC/DC converter, the direct-connection problem of the bridge arm power tube of the three-phase dual-voltage-reduction AC/DC converter and the problem of extra switching loss under a bias current working mode of a dual-voltage-reduction converter are solved.

Description

From the two step-down AC/DC current transformers of circulation three-phase

Technical field

The present invention relates to three-phase ac-dc conversion field, relate in particular to a kind of from the two step-down converter topological structures of circulation three-phase.

Background technology

Along with the development of new energy technology, urgent all the more to the demand of electronic power convertor.In fields such as wind power generation, electric automobiles, especially in middle high power occasion, three-phase AC/DC current transformer all is widely used.Therefore, optimize the waveform quality of three-phase AC/DC current transformer, improve functional reliability, improve the current transformer topology and wait research work to have great importance.

In recent years, two buck topologies do not exist the advantages such as bridge arm direct pass problem, fly-wheel diode reverse recovery loss be little to obtain increasing application with it.2002, the Liu Jun of Nanjing Aero-Space University, professor Yan Yangguang etc. have proposed to adopt single-phase pair of step-down inverter topology of hysteresis current control, adopt external fast recovery diode to carry out afterflow, the input of the output of upper brachium pontis power tube and lower brachium pontis power tube respectively be connected filter inductance, avoided the straight-through problem of upper and lower bridge arm power tube.People such as Sun Peng big (Pengwei Sun) etc. was applied to three-phase AC/DC current transformer with two buck topologies in 2012, adopted Harmonic Injection Method equivalence SVPWM control strategy, had realized the inverter operation of the two step-down converters of three-phase.

For two step-down converters, it has bias current and without two kinds of mode of operations of bias current, distinguishes corresponding complete period and half period control mode.There are under the bias current mode of operation two BUCK converters of every phase brachium pontis work simultaneously, and be the alternation of two BUCK converters without the essence of bias current mode of operation, so less than the switching loss that the bias current mode of operation is arranged and conduction loss without the bias current mode of operation.And need the masking redundancy switching signal without the half period control mode that the bias current mode of operation adopts, and for different energy flow directions, need the range of signal of shielding different, be difficult for realizing naturally switching of rectification, inversion, and control is comparatively complicated.In addition, half period control meeting causes net to survey the current over-zero distortion because integral element causes the hysteresis of modulation signal and the unicity of inductive current direction, has had a strong impact on waveform quality.

Summary of the invention

Technical problem to be solved by this invention is to provide a kind of high efficiency high reliability three-phase AC/DC current transformer topological circuit, and is high to overcome the prior art harmonic content, has the shortcomings such as zero crossing distortion.

The present invention proposes a kind of from the two step-down converter topological circuits of circulation three-phase, comprise the DC side Support Capacitor, A goes up the brachium pontis power tube mutually, A descends the brachium pontis power tube mutually, A goes up the brachium pontis fly-wheel diode mutually, A descends the brachium pontis fly-wheel diode mutually, A is the first anti-straight-through filter inductance mutually, A is the second anti-straight-through filter inductance mutually, A is from recirculation diode, B goes up the brachium pontis power tube mutually, B descends the brachium pontis power tube mutually, B goes up the brachium pontis fly-wheel diode mutually, B descends the brachium pontis fly-wheel diode mutually, B is the first anti-straight-through filter inductance mutually, B is the second anti-straight-through filter inductance mutually, B is from recirculation diode, C goes up the brachium pontis power tube mutually, C descends the brachium pontis power tube mutually, C goes up the brachium pontis fly-wheel diode mutually, C descends the brachium pontis fly-wheel diode mutually, C is the first anti-straight-through filter inductance mutually, C is the second anti-straight-through filter inductance mutually, C is from recirculation diode, wherein the anodal P of DC side Support Capacitor goes up respectively the upper end of brachium pontis power tube mutually with A, B goes up the upper end of brachium pontis power tube mutually, C goes up the upper end of brachium pontis power tube mutually, A goes up the negative electrode of brachium pontis fly-wheel diode mutually, the negative electrode that B goes up the brachium pontis fly-wheel diode is mutually is connected the brachium pontis fly-wheel diode with C negative electrode connects, the negative pole N of DC side Support Capacitor descends respectively the lower end of brachium pontis power tube mutually with A, B descends the lower end of brachium pontis power tube mutually, C descends the lower end of brachium pontis power tube mutually, A descends the anode of brachium pontis fly-wheel diode mutually, the anode that B descends the brachium pontis fly-wheel diode mutually and C descend the anodic bonding of brachium pontis fly-wheel diode mutually, the lower end E that A goes up the brachium pontis power tube mutually descends respectively the negative electrode of brachium pontis fly-wheel diode mutually with A, A is connected the first anti-straight-through filter inductance from the negative electrode of recirculation diode with A input connects, A descends the upper end M of brachium pontis power tube to go up mutually respectively the anode of brachium pontis fly-wheel diode with A mutually, A is connected the second anti-straight-through filter inductance from the anode of recirculation diode with A output connects, the A mutually output terminals A of the first anti-straight-through filter inductance is connected with the input of A phase the second anti-straight-through filter inductance, the lower end F that B goes up the brachium pontis power tube mutually descends respectively the negative electrode of brachium pontis fly-wheel diode mutually with B, B is connected the first anti-straight-through filter inductance from the negative electrode of recirculation diode with B input connects, B descends the upper end H of brachium pontis power tube to go up mutually respectively the anode of brachium pontis fly-wheel diode with B mutually, B is connected the second anti-straight-through filter inductance from the anode of recirculation diode with B output connects, the B mutually output B of the first anti-straight-through filter inductance is connected with the input of B phase the second anti-straight-through filter inductance, the lower end G that C goes up the brachium pontis power tube mutually descends respectively the negative electrode of brachium pontis fly-wheel diode mutually with C, C is connected the first anti-straight-through filter inductance from the negative electrode of recirculation diode with C input connects, C descends the upper end I of brachium pontis power tube to go up mutually respectively the anode of brachium pontis fly-wheel diode with C mutually, C is connected the second anti-output that leads directly to filter inductance from the anode of recirculation diode and connects with C, the C mutually output C of the first anti-straight-through filter inductance is connected with the input of C phase the second anti-straight-through filter inductance.

Wherein, on the described three-phase under brachium pontis fly-wheel diode and the three-phase brachium pontis fly-wheel diode be external fast recovery diode.

Wherein, described 3-phase power converter both can have been realized the inversion mode of operation of the transmission of energy from the DC side to the AC, can realize again the rectification mode of operation that energy transmits from the AC to the DC side.

A kind of 3-phase power converter topological circuit of the present invention has increased from recirculation diode on the basis of two buck topologies, consists of continuous current circuit with every phase filter inductance, has avoided filter inductance and power tube to consist of continuous current circuit.This topology has kept two buck topology upper and lower bridge arm power tubes without the advantage of straight-through phenomenon, and the power loss of having avoided half period Redundanter schalter signal to cause, can realize naturally switching of current transformer rectification and inversion, having solved three-phase voltage source type bridge-type current transformer bridge arm direct pass problem and two voltage-dropping type current transformer needs the masking redundancy switching signal to reduce the extra switch loss and to net the problem of surveying the current zero-crossing point distortion.

Description of drawings

Fig. 1 is of the present invention from the two step-down converter topological circuit schematic diagrames of circulation three-phase;

Fig. 2 is 3-phase power converter energy in bidirectional flow SVPWM control block diagram of the present invention;

Fig. 3 is key waveforms schematic diagram of the present invention;

Fig. 4 is the fundamental diagram of the present invention when being in switch mode 1;

Fig. 5 is the fundamental diagram of the present invention when being in switch mode 2;

Fig. 6 is the fundamental diagram of the present invention when being in switch mode 3;

Fig. 7 is the fundamental diagram of the present invention when being in switch mode 4.

Embodiment

As shown in Figure 1, a kind of from the two step-down converters of circulation three-phase, comprise DC side Support Capacitor C _In, A goes up brachium pontis power tube S mutually ₁, A descends brachium pontis power tube S mutually ₂, A goes up the brachium pontis sustained diode mutually ₁, A descends the brachium pontis sustained diode mutually ₂, A the first anti-straight-through filtering inductance L mutually _A1, A the second anti-straight-through filtering inductance L mutually _A2, A is from recirculation diode D _Aq, B goes up brachium pontis power tube S mutually ₃, B descends brachium pontis power tube S mutually ₄, B goes up the brachium pontis sustained diode mutually ₃, B descends the brachium pontis sustained diode mutually ₄, B the first anti-straight-through filtering inductance L mutually _B1, B the second anti-straight-through filtering inductance L mutually _B2, B is from recirculation diode D _Bq, C goes up brachium pontis power tube S mutually ₅, C descends brachium pontis power tube S mutually ₆, C goes up the brachium pontis sustained diode mutually ₅, C descends the brachium pontis sustained diode mutually ₆, C the first anti-straight-through filtering inductance L mutually _C1, C the second anti-straight-through filtering inductance L mutually _C2, C is from recirculation diode D _Cq, DC side Support Capacitor C wherein _InAnodal P go up mutually brachium pontis power tube S with A respectively ₁Upper end, B go up mutually brachium pontis power tube S ₃Upper end, C go up mutually brachium pontis power tube S ₅Upper end, A go up mutually the brachium pontis sustained diode ₁Negative electrode, B go up mutually the brachium pontis sustained diode ₃Negative electrode go up mutually the brachium pontis sustained diode with C ₅Negative electrode connect DC side Support Capacitor C _InNegative pole N descend mutually brachium pontis power tube S with A respectively ₂Lower end, B descend mutually brachium pontis power tube S ₄Lower end, C descend mutually brachium pontis power tube S ₆Lower end, A descend mutually the brachium pontis sustained diode ₂Anode, B descend mutually the brachium pontis sustained diode ₄Anode descend mutually the brachium pontis sustained diode with C ₆Anodic bonding, A goes up brachium pontis power tube S mutually ₁Lower end E descend mutually the brachium pontis sustained diode with A respectively ₂Negative electrode, A from recirculation diode D _AqNegative electrode and A the first anti-straight-through filtering inductance L mutually _A1Input connect, A descends brachium pontis power tube S mutually ₂Upper end M go up mutually the brachium pontis sustained diode with A respectively ₁Anode, A from recirculation diode D _AqAnode and A the second anti-straight-through filtering inductance L mutually _A2Output connect, A is the first anti-straight-through filtering inductance L mutually _A1Output terminals A and A the second anti-straight-through filtering inductance L mutually _A2Input connect, B goes up brachium pontis power tube S mutually ₃Lower end F descend mutually the brachium pontis sustained diode with B respectively ₄Negative electrode, B from recirculation diode D _BqNegative electrode and B the first anti-straight-through filtering inductance L mutually _B1Input connect, B descends brachium pontis power tube S mutually ₄Upper end H go up mutually the brachium pontis sustained diode with B respectively ₃Anode, B from recirculation diode D _BqAnode and B the second anti-straight-through filtering inductance L mutually _B2Output connect, B is the first anti-straight-through filtering inductance L mutually _B1Output B and B the second anti-straight-through filtering inductance L mutually _B2Input connect, C goes up brachium pontis power tube S mutually ₅Lower end G descend mutually the brachium pontis sustained diode with C respectively ₆Negative electrode, C from recirculation diode D _CqNegative electrode and C the first anti-straight-through filtering inductance L mutually _C1Input connect, C descends brachium pontis power tube S mutually ₆Upper end I go up mutually the brachium pontis sustained diode with C respectively ₅Anode, C from recirculation diode D _CqAnode and C the second anti-straight-through filtering inductance L mutually _C2Output connect, C is the first anti-straight-through filtering inductance L mutually _C1Output C and C the second anti-straight-through filtering inductance L mutually _C2Input connect.

The electric current and voltage reference direction as shown in Figure 1, i _aBe A cross streams side electric current, i _A1For flowing through mutually the first anti-straight-through filtering inductance L of A _A1Electric current, i _A2For flowing through mutually the second anti-straight-through filtering inductance L of A _A2Electric current, i _AqFor flowing through A from recirculation diode D _AqElectric current, i _bBe B cross streams side electric current, i _B1For flowing through mutually the first anti-straight-through filtering inductance L of B _B1Electric current, i _B2For flowing through mutually the second anti-straight-through filtering inductance L of B _B2Electric current, i _BqFor flowing through B from recirculation diode D _BqElectric current, i _cBe C cross streams side electric current, i _C1For flowing through mutually the first anti-straight-through filtering inductance L of C _C1Electric current, i _C2For flowing through mutually the second anti-straight-through filtering inductance L of C _C2Electric current, i _CqFor flowing through C from recirculation diode D _CqElectric current.

Fig. 2 is 3-phase power converter energy in bidirectional flow SVPWM control block diagram of the present invention, dc voltage error signal given as active current after PI regulates, be converted into the rotation rectangular coordinate system after the coordinate transform of sampling three-phase power network current mirror and carry out the PI adjusting, after the SVPWM computing, obtain the driving signal of each power tube, the positive and negative foundation that is the energy in bidirectional flow switching that active current is given.

Current transformer three-phase working condition is similar, describe as example mutually take A, Fig. 3 be band high-frequency rectification bridge of the present invention without dead band three-phase AC/DC current transformer key waveforms schematic diagram, be respectively A cross streams side current i _a, flow through mutually the first anti-straight-through filtering inductance L of A _A1Current i _A1, flow through mutually the second anti-straight-through filtering inductance L of A _A2Current i _A2With flow through A from recirculation diode D _AqCurrent i _Aq

Then can be divided into four kinds of operation modes in an AC power frequency period,, have mutually as example take A

i _a＝i _a1-i _a2(1)

Ignore high frequency ripple, order

i _a＝I _acosωt (2)

Because grid current THD is very little, ignores the grid current harmonic wave, the A point is with respect to the current potential u of AC mid point O _AOSatisfy

u _AO＝e _a(3)

Because there are voltage difference in positive DC side end N and AC mid point O, i.e. v _ON=v _Cm/ 3+V _DC/ 2, v _CmBe defined as common-mode voltage, so the A point is with respect to the current potential u of positive DC side end N _ANFor

$u_{\mathrm{AN}}=u_{\mathrm{AO}}+u_{\mathrm{ON}}=\frac{V_{\mathrm{DC}}}{2}+e_a+v_{\mathrm{cm}}---\left(4\right)$

Can find out that it is relevant with the HF switch state, v _CmFourier's expression formula is

$v_{\mathrm{cm}}\left(t\right)=\frac{V_{\mathrm{DC}}}{2}+\frac{2V_{\mathrm{DC}}}{\mathrm{\π}}\underset{m=1}{\overset{\∞}{\mathrm{\Σ}}}\frac{1}{m}{J}_0\left(\frac{\mathrm{m\π}}{2}M\right)\sin \frac{\mathrm{m\π}}{2}\cos m{\mathrm{\ω}}_{s}t+\frac{2V_{\mathrm{DC}}}{\mathrm{\π}}\underset{m=1}{\overset{\∞}{\mathrm{\Σ}}}\underset{n=\±3k}{\overset{\±\∞}{\mathrm{\Σ}}}\frac{1}{m}{J}_n\left(\frac{\mathrm{m\π}}{2}M\right)\sin \frac{(m+n)\mathrm{\π}}{2}\cos (m{\mathrm{\ω}}_{s}t+\mathrm{n\ωt})---\left(5\right)$

ω wherein _sBe the switching angle frequency, common-mode voltage does not exist direct current biasing and fundametal compoment, very according to formula (4), u _ANDirect current biasing is V _DC/ 2, fundametal compoment is approximately e _a, its high fdrequency component depends on common-mode voltage.

As shown in Figure 4, switch mode I:

This moment i _aDirection is for just, and size reduces, and flows through inductance L _A1Current i _A1Also be positive direction, its value reduces, because the induced potential of inductance is relevant with the rate of change of electric current, and L _A1Voltage and reference voltage opposite direction, the i.e. u of induction _A1＜0.Work as S ₁During conducting, ignore conduction voltage drop, E point current potential V _EEqual P point current potential V _P, because u _A1＜0, so A point current potential V _ABe higher than V _E, i.e. V _A＞V _P, be added in L _A2On voltage identical with reference direction, and u _A2Equal-u _A1, flow through L this moment _A2Current i _A2Be voltage u _A2To the integration of time, namely

$i_{a2}=\frac{1}{L_{a1}}\∫u_{a2}\mathrm{dt}---\left(6\right)$

i _A2Identical with reference direction, it is worth increase.Work as S ₁During shutoff, because i _A1Can not suddenly change diode D ₂Afterflow, at this moment V _E=V _N, V then _A＞V _NFor middle high power 3-phase power converter system, dc voltage is higher, inductance L _A1The sense value is the milihenry rank, and its induced potential is lower than dc voltage, so V _A＜V _PBecause L _A1And L _A2Voltage satisfy all the time

u _a2＝-u _a1(7)

Can be got by formula (6) (7)

$i_{a2}=-\frac{1}{L_{a1}}{\∫u}_{a1}\mathrm{dt}=-i_{a1}+\mathrm{const}---\left(8\right)$

Wherein const is constant, is got by formula (1)

2i _a1-const＝I _acosωt (9)

Get thus i _A1And i _A2Expression formula

$\left\{\begin{array}{c}{i}_{a1}=\frac{I_a}{2}\cos \mathrm{\ωt}+\frac{I_a}{2}\\ i_{a2}=-\frac{I_a}{2}\cos \mathrm{\ωt}+\frac{I_a}{2}\end{array}\right.---\left(10\right)$

Flow through L _A1And L _A2Electric current and i _aSame-phase, amplitude be its 1/2, and with I _a/ 2 direct current biasings.

Under this mode, from recirculation diode D _AqAll the time have electric current to flow through, its electric current satisfies

$\left\{\begin{array}{cc}{i}_{\mathrm{aq}}=i_{a2}=i_{a1}-i_{s1}& S_1\mathrm{ON}\\ i_{\mathrm{aq}}=i_{a2}=i_{a1}-i_{d2}& S_1\mathrm{OFF}\end{array}\right.---\left(11\right)$

Although so S ₁During shutoff to S ₂Apply and open signal, but circulation flows through D _Aq, S ₂In do not have all the time electric current to flow through.Under the SVPWM control method, S ₁And S ₂Complementary conducting is for two BUCK topologys, S ₂During conducting, i _A2Flow through S ₂, can cause larger switching loss, for of the present invention from the two step-down converters of circulation three-phase, S ₂Do not have electric current to flow through during conducting, can not cause extra switching loss.

As shown in Figure 5, switch mode II:

I under this mode _aDirection is for negative, and size increases, and flows through inductance L _A2Current i _A2Direction is for just, and its value also increases induced potential u _A2Identical with reference direction, work as S ₂During conducting, V _A＞V _M=V _N, because inductive current i _A1Can not suddenly change, it is by diode D _AqSo afterflow is V _M=V _E=V _N, V _A＞V _E, i.e. L _A1Both end voltage u _A1With the reference voltage opposite direction, its value equals u _A2So, i _A1Reduce.

Work as S ₂During shutoff, diode D ₁Afterflow, V _E=V _P, because D _AqConducting, and induced potential u _A2＞0, i.e. V _A＞V _M, u then _A1＜0, i _A1Continue to reduce.Can find out, under the mode II, work as S ₁And S ₂During complementary conducting, u _A1And u _A2Also satisfy formula (7), thereby can release i under this mode _A1And i _A2Also satisfy formula (10).Flow through from recirculation diode D this moment _AqCurrent i _AqSatisfy

$\left\{\begin{array}{cc}{i}_{\mathrm{aq}}=i_{a1}=i_{a2}-i_{s2}& S_2\mathrm{ON}\\ i_{\mathrm{aq}}=i_{a1}=i_{a2}-i_{d1}& S_2\mathrm{OFF}\end{array}\right.---\left(12\right)$

As shown in Figure 6, switch mode III:

I under this mode _aDirection is for negative, and size reduces, and flows through inductance L _A2Current i _A2Direction is for just, and its value also reduces, induced potential u _A2Opposite with reference direction.

Work as S ₂During conducting, V _A＜V _M=V _N, diode D _AqSo conducting is V _M=V _E, V _A＜V _E, L _A1Both end voltage u _A1Identical with the reference voltage direction, so i _A1Increase.

Work as S ₂During shutoff, diode D ₁Afterflow is because u _A2＜0, u then _A1＞0, i _A1Continue to increase.This moment u _A1, u _A2And i _A1, i _A2Satisfy respectively formula (5) and formula (10), i _AqSatisfy formula (12).

As shown in Figure 7, switch mode IV:

I under this mode _aDirection is for just, and size increases, and flows through inductance L _A1Current i _A1Direction is for just, and its value also increases induced potential u _A1Identical with reference direction.Work as S ₁During conducting, V _A＜V _E=V _P, because inductive current i _A2Can not suddenly change, it is by diode D _AqSo afterflow is V _E=V _M, V _A＜V _L, i.e. L _A2Both end voltage u _A2With the reference voltage opposite direction, its value equals u _A1So, i _A2Reduce.

Work as S ₁During shutoff, diode D ₂Afterflow, V _N=V _F, owing to D this moment _Aq3, D _Aq4Conducting, then V _K=V _L, because induced potential u _A1＞0, i.e. V _A＜V _M, u _A2＜0, i _A2Continue to reduce u _A1, u _A2And i _A1, i _A2Satisfy respectively formula (5) and formula (10), i _AqSatisfy formula (12).

Claims (3)

1. one kind from the two step-down converters of circulation three-phase, it is characterized in that comprising DC side Support Capacitor (C _In), A goes up brachium pontis power tube (S mutually ₁), A descends brachium pontis power tube (S mutually ₂), A goes up brachium pontis fly-wheel diode (D mutually ₁), A descends brachium pontis fly-wheel diode (D mutually ₂), A the first anti-straight-through filter inductance (L mutually _A1), A the second anti-straight-through filter inductance (L mutually _A2), A is from recirculation diode (D _Aq), B goes up brachium pontis power tube (S mutually ₃), B descends brachium pontis power tube (S mutually ₄), B goes up brachium pontis fly-wheel diode (D mutually ₃), B descends brachium pontis fly-wheel diode (D mutually ₄), B the first anti-straight-through filter inductance (L mutually _B1), B the second anti-straight-through filter inductance (L mutually _B2), B is from recirculation diode (D _Bq), C goes up brachium pontis power tube (S mutually ₅), C descends brachium pontis power tube (S mutually ₆), C goes up brachium pontis fly-wheel diode (D mutually ₅), C descends brachium pontis fly-wheel diode (D mutually ₆), C the first anti-straight-through filter inductance (L mutually _C1), C the second anti-straight-through filter inductance (L mutually _C2), C is from recirculation diode (D _Cq), DC side Support Capacitor (C wherein _In) anodal P go up mutually brachium pontis power tube (S with A respectively ₁) upper end, B go up mutually brachium pontis power tube (S ₃) upper end, C go up mutually brachium pontis power tube (S ₅) upper end, A go up mutually brachium pontis fly-wheel diode (D ₁) negative electrode, B go up mutually brachium pontis fly-wheel diode (D ₃) negative electrode go up mutually brachium pontis fly-wheel diode (D with C ₅) negative electrode connect DC side Support Capacitor (C _In) negative pole N descend mutually brachium pontis power tube (S with A respectively ₂) lower end, B descend mutually brachium pontis power tube (S ₄) lower end, C descend mutually brachium pontis power tube (S ₆) lower end, A descend mutually brachium pontis fly-wheel diode (D ₂) anode, B descend mutually brachium pontis fly-wheel diode (D ₄) anode descend mutually brachium pontis fly-wheel diode (D with C ₆) anodic bonding, A goes up brachium pontis power tube (S mutually ₁) lower end E descend mutually brachium pontis fly-wheel diode (D with A respectively ₂) negative electrode, A from recirculation diode (D _Aq) negative electrode and A the first anti-straight-through filter inductance (L mutually _A1) input connect, A descends brachium pontis power tube (S mutually ₂) upper end M go up mutually brachium pontis fly-wheel diode (D with A respectively ₁) anode, A from recirculation diode (D _Aq) anode and A the second anti-straight-through filter inductance (L mutually _A2) output connect, A is the first anti-straight-through filter inductance (L mutually _A1) output terminals A and A the second anti-straight-through filter inductance (L mutually _A2) input connect, B goes up brachium pontis power tube (S mutually ₃) lower end F descend mutually brachium pontis fly-wheel diode (D with B respectively ₄) negative electrode, B from recirculation diode (D _Bq) negative electrode and B the first anti-straight-through filter inductance (L mutually _B1) input connect, B descends brachium pontis power tube (S mutually ₄) upper end H go up mutually brachium pontis fly-wheel diode (D with B respectively ₃) anode, B from recirculation diode (D _Bq) anode and B the second anti-straight-through filter inductance (L mutually _B2) output connect, B is the first anti-straight-through filter inductance (L mutually _B1) output B and B the second anti-straight-through filter inductance (L mutually _B2) input connect, C goes up brachium pontis power tube (S mutually ₅) lower end G descend mutually brachium pontis fly-wheel diode (D with C respectively ₆) negative electrode, C from recirculation diode (D _Cq) negative electrode and C the first anti-straight-through filter inductance (L mutually _C1) input connect, C descends brachium pontis power tube (S mutually ₆) upper end I go up mutually brachium pontis fly-wheel diode (D with C respectively ₅) anode, C from recirculation diode (D _Cq) anode and C the second anti-straight-through filter inductance (L mutually _C2) output connect, C is the first anti-straight-through filter inductance (L mutually _C1) output C and C the second anti-straight-through filter inductance (L mutually _C2) input connect.

2. circuit as claimed in claim 1 is characterized in that, on the described three-phase under brachium pontis fly-wheel diode and the three-phase brachium pontis fly-wheel diode be external fast recovery diode.

3. circuit as claimed in claim 1 is characterized in that, described 3-phase power converter both can have been realized the inversion mode of operation of the transmission of energy from the DC side to the AC, can realize again the rectification mode of operation that energy transmits from the AC to the DC side.

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